WO2023019969A1 - 逆变电路及其驱动方法、以及多相逆变电路与逆变器 - Google Patents

逆变电路及其驱动方法、以及多相逆变电路与逆变器 Download PDF

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Publication number
WO2023019969A1
WO2023019969A1 PCT/CN2022/085381 CN2022085381W WO2023019969A1 WO 2023019969 A1 WO2023019969 A1 WO 2023019969A1 CN 2022085381 W CN2022085381 W CN 2022085381W WO 2023019969 A1 WO2023019969 A1 WO 2023019969A1
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Prior art keywords
switch
inverter
unit
sequence
inverter circuit
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PCT/CN2022/085381
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English (en)
French (fr)
Inventor
雷健华
唐朝垠
马辉
秦赓
尹相柱
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深圳市德兰明海科技有限公司
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Publication of WO2023019969A1 publication Critical patent/WO2023019969A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present application relates to the technical field of power electronics, for example, to an inverter circuit and a driving method thereof, as well as a multi-phase inverter circuit and an inverter.
  • the development of industrialization has higher and higher requirements on the size, cost, operating frequency and efficiency of power electronic devices.
  • the pursuit of high frequency, high efficiency, low cost and miniaturization of power electronic devices has become a development concept.
  • the hard-switching inverter will not only produce serious switching loss, but also be accompanied by serious noise pollution and electromagnetic interference.
  • soft-switching technology was born and applied to hard-switching inverters.
  • the soft-switching inverter refers to adding an auxiliary resonant circuit to the hard-switching inverter, using the resonance effect of the inductance and capacitance in the auxiliary circuit to realize zero-voltage switching or zero-current switching, reduce switching loss, reduce noise pollution and electromagnetic interference .
  • the resonant pole type soft-switching inverter has more outstanding performance.
  • This type of inverter usually uses three sets of auxiliary resonant circuits, which are respectively connected to the three-phase inverter
  • the three sets of auxiliary circuits of the inverter can realize independent control, creating soft switching conditions for the main switches on each phase bridge arm of the three-phase inverter, and solving the problem of synchronization between the auxiliary switch and the main switch of the inverter.
  • PWM pulse width modulation
  • the embodiment of the present application aims to provide an inverter circuit and a driving method, a multi-phase inverter circuit and an inverter, which can realize the inverter function through a relatively simple circuit with low cost.
  • an inverter circuit including:
  • a first switch a freewheeling unit, a resonant unit, a bridge arm unit and a control unit;
  • the first switch is respectively connected to the midpoint of the freewheeling unit and the DC power supply
  • the resonance unit is respectively connected to the midpoint of the freewheeling unit and the midpoint of the bridge arm unit
  • the bridge arm unit The midpoint is also used to connect with the load
  • the freewheeling unit is connected in parallel with the bridge arm unit, and both the freewheeling unit and the bridge arm unit are connected to the DC power supply;
  • the control unit is respectively connected to the control end of the first switch and the bridge arm unit, and the control unit is used to control the switching state of the first switch and to control the inverter in the bridge arm unit
  • the switching state of the switch is used to convert the DC power of the DC power supply into AC power, and the AC power is output at the midpoint of the bridge arm unit.
  • the resonant unit includes a resonant inductor and a resonant capacitor
  • the resonant inductor is connected in series with the resonant capacitor, the non-serial end of the resonant inductor is connected to the midpoint of the freewheeling unit, and the non-serial end of the resonant capacitor is connected to the midpoint of the bridge arm unit.
  • the bridge arm unit includes a first inverter switch and a second inverter switch
  • Both the first end of the first inverter switch and the first end of the second inverter switch are connected to the control unit, the second end of the first inverter switch, the second inverter switch
  • the third ends of the switches are all connected to the resonant unit, the third end of the first inverter switch is connected to the positive pole of the DC power supply, and the second end of the second inverter switch is connected to the negative pole of the DC power supply. connect.
  • the freewheeling unit includes a first diode and a second diode
  • the cathode of the first diode is connected to the anode of the DC power supply
  • the anode of the first diode is connected to the cathode of the second diode
  • the anode of the second diode is connected to the anode of the DC power supply.
  • connection point between the first diode and the second diode is the midpoint of the freewheeling unit.
  • the present application provides a driving method for an inverter circuit, which is used to drive the inverter circuit described in any of the above embodiments, and the driving method includes:
  • the driving method further includes an initial sequence
  • the first switch, the first inverter switch, and the second inverter switch are controlled to be turned off, so that the inverter circuit is in the initial state, and the first inverter circuit is executed. a timing.
  • the driving method further includes maintaining timing
  • the present application provides a multi-phase inverter circuit, including at least two inverter circuits described in any one of the above-mentioned embodiments;
  • One end of the first switch in each of the inverter circuits is used to connect to the negative pole of the DC power supply, and the two ends of the freewheeling unit in each of the inverter circuits are respectively connected to the two ends of the DC power supply. connect.
  • any one of the inverter circuits is driven by the driving method described in any one of the above embodiments.
  • the present application provides an inverter, including the inverter circuit described in any one of the above embodiments;
  • the inverter circuit provided by the present application includes a first switch, a freewheeling unit, a resonant unit, a bridge arm unit and a control unit, wherein the first switch is connected to the midpoint of the freewheeling unit and the DC Power supply connection, the resonant unit is connected to the middle of the freewheeling unit and the midpoint of the bridge arm unit, the midpoint of the bridge arm unit is also used to connect to the load, the freewheeling unit and the bridge arm unit are connected in parallel, and both are connected to the DC power supply , the control unit is respectively connected with the first switch and the bridge arm unit, therefore, the control unit can make the inverter circuit convert the DC The direct current of the power supply is converted into alternating current and output from the midpoint of the bridge arm unit, thereby realizing the inverter function.
  • the control unit, and the auxiliary switch only needs to include the first switch, without a transformer as in the prior art, the circuit structure is relatively simple, and the cost is also reduced
  • FIG. 1 is a schematic structural diagram of an inverter circuit provided by an embodiment of the present application
  • FIG. 2 is a schematic diagram of the circuit structure of the inverter circuit provided by the embodiment of the present application.
  • FIG. 3 is a flowchart of a driving method provided in an embodiment of the present application.
  • Figure 4a is a schematic diagram of the first control state of the inverter circuit within one cycle provided by the embodiment of the present application;
  • Fig. 4b is a schematic diagram of the second control state of the inverter circuit in one cycle provided by the embodiment of the present application;
  • Fig. 4c is a schematic diagram of the third control state of the inverter circuit in one cycle provided by the embodiment of the present application.
  • Fig. 4d is a schematic diagram of the fourth control state of the inverter circuit in one cycle provided by the embodiment of the present application.
  • Fig. 4e is a schematic diagram of the fifth control state of the inverter circuit in one cycle provided by the embodiment of the present application.
  • Fig. 4f is a schematic diagram of the sixth control state of the inverter circuit in one cycle provided by the embodiment of the present application.
  • Fig. 4g is a schematic diagram of the seventh control state of the inverter circuit in one cycle provided by the embodiment of the present application.
  • Fig. 4h is a schematic diagram of the eighth control state of the inverter circuit in one cycle provided by the embodiment of the present application.
  • Fig. 4i is a schematic diagram of the ninth control state of the inverter circuit in one cycle provided by the embodiment of the present application.
  • Fig. 4j is a schematic diagram of the tenth control state of the inverter circuit in one cycle provided by the embodiment of the present application;
  • FIG. 4k is a schematic diagram of the eleventh control state of the inverter circuit within one cycle provided by the embodiment of the present application;
  • FIG. 5 is a waveform diagram of each signal in the inverter circuit provided by the embodiment of the present application.
  • FIG. 6 is a schematic structural diagram of a driving device provided in an embodiment of the present application.
  • FIG. 7 is a schematic diagram of a circuit structure of a multi-phase inverter circuit provided by an embodiment of the present application.
  • FIG. 1 is a schematic structural diagram of an inverter circuit provided in an embodiment of the present application.
  • the inverter circuit 100 includes a first switch 10 , a freewheeling unit 20 , a resonance unit 30 , a bridge arm unit 40 and a control unit 50 .
  • the first end of the first switch 10 is connected to the second end of the DC power supply 200
  • the second end of the first switch 10 is connected to the midpoint P1 of the freewheeling unit 20
  • the first end of the resonant unit 30 is connected to the freewheeling unit.
  • the midpoint P1 of 20 is connected, the second end of the resonance unit 30 is connected with the midpoint P2 of the bridge arm unit 40, the midpoint P2 of the bridge arm unit 40 is also connected with the load 300, and the freewheeling unit 20 is connected in parallel with the bridge arm unit 40 , that is, the first end of the freewheeling unit 20 is connected to the first end of the bridge arm unit 40, the second end of the freewheeling unit 20 is connected to the second end of the bridge arm unit 40, and the first end of the freewheeling unit 20 is connected to the first end of the bridge arm unit 40.
  • the second end is also respectively connected to two ends of the DC power supply 200
  • the control unit 50 is respectively connected to the first switch 10 and the bridge arm unit 40 .
  • both the first switch 10 and the inverter switches in the bridge arm unit 40 are controlled by the control unit 50 , and then the control unit 50 controls the switching state of the first switch 10 and controls the inverter switches in the bridge arm unit 40 .
  • the switching state of the switch can convert the DC power provided by the DC power supply 200 into AC power, and output the AC power to the load 300 at the midpoint P2 of the bridge arm unit 40 as the power supply voltage of the load 300 .
  • the switching state of each switch refers to the state of each switch being closed or disconnected.
  • the direct current is converted into alternating current, that is, the inverter function is realized.
  • the inverter circuit 100 only the first switch 10 is used as an auxiliary switch, so the number of auxiliary switches is small, and there is no need to set a transformer as in the prior art, so that the circuit structure becomes simple, thereby reducing costs.
  • circuit structure of the inverter circuit shown in FIG. 2 is taken as an example for illustration.
  • the first switch 10 is a first switch Q1 (IGBT switch tube Q1 in the figure).
  • the gate (ie, G pole) of the IGBT switch Q1 is connected to the control unit 50
  • the emitter (ie, E pole) of the IGBT switch Q1 is connected to the negative pole of the DC power supply 200
  • the collector (ie, C pole) is connected to the midpoint P1 of the freewheeling unit 20.
  • the freewheeling unit 20 includes a first diode D1 and a second diode D2.
  • the anode of the first diode D1 is connected to the cathode of the second diode D2
  • the cathode of the first diode D1 is connected to the anode of the DC power supply 200
  • the anode of the second diode D2 is connected to the anode of the DC power supply 200.
  • the negative electrodes are connected, and the connection point between the first diode D1 and the second diode D2 is the midpoint P1 of the freewheeling unit 20 .
  • both the first diode D1 and the second diode D2 are freewheeling diodes.
  • the resonant unit 30 includes a resonant inductor L1 and a resonant capacitor C1.
  • the resonant inductor L1 is connected in series with the resonant capacitor C1
  • the non-serial connection end of the resonant inductor L1 is connected to the midpoint P1 of the freewheeling unit 20
  • the non-serial connection end of the resonant capacitor C1 is connected to the midpoint P2 of the bridge arm unit 40 .
  • the resonant unit 30 composed of the resonant inductor L1 and the resonant capacitor C1
  • the resistance of the resonant inductor L1 and the resonant capacitor C1 is small, when the inverter circuit is working, the power consumption of the resonant inductor L1 and the resonant capacitor can be approximated as Zero, thereby reducing the power loss of the inverter circuit.
  • the bridge arm unit 40 includes a second switch and a third switch. Both the first end of the second switch and the first end of the third switch are connected to the control unit, the second end of the second switch and the third end of the third switch are both connected to the non-serial end of the resonant capacitor, and the second end of the second switch The third terminal is connected to the positive pole of the DC power supply, and the second terminal of the third switch is connected to the negative pole of the DC power supply.
  • both the second switch and the third switch are IGBT tubes
  • the second switch corresponds to the IGBT switch tube Q2 in FIG. 2
  • the third switch corresponds to the IGBT switch tube Q3 in FIG. 2 .
  • the gates of the IGBT switch Q2 and the IGBT switch Q3 are connected to the control unit 50, the emitter of the IGBT switch Q2 is connected to the collector of the IGBT switch Q3, and the collector of the IGBT switch Q2 is connected to the DC power supply 200 The positive pole is connected, and the emitter of the IGBT switch Q3 is connected to the negative pole of the DC power supply 200 .
  • the connection point between the IGBT switch tube Q2 and the IGBT switch tube Q3 is the midpoint P2 of the bridge arm unit 40 .
  • the first switch, the second switch and the third switch all use IGBT switch tubes as examples.
  • the first switch, the second switch and the third switch can also be any power electronic components, such as field effect transistor MOSFET, thyristor SCR, gate turn-off thyristor GTO, power transistor GTR, etc. It can also be any commonly used switch, such as contactor, relay, time delay switch, photoelectric switch, tact switch, proximity switch, etc., or it can be a variety of combinations of the above types.
  • the first switch, the second switch and the third switch may be the same or different.
  • the gate of the IGBT switch is the first end of the first switch
  • the emitter of the IGBT switch is the second end of the first switch
  • the IGBT switch The collector of is the third terminal of the first switch.
  • the present application provides a driving method for an inverter circuit, the method for driving the inverter circuit in any of the above embodiments includes:
  • the driving method of the inverter circuit further includes an initial sequence
  • the first switch, the first inverter switch and the second inverter switch are controlled to be turned off, so that the inverter circuit is in an initial state, and the first sequence is executed.
  • the driving method of the inverter circuit further includes maintaining timing
  • the maintenance sequence is executed.
  • the first switch is kept disconnected from the first inverter switch, and the After the second inverter switch is closed to keep the resonant current at 0 and the resonant voltage at U3, the fourth sequence is executed.
  • FIG. 3 is a schematic flow chart of the driving method of the inverter circuit provided by the embodiment of the present application.
  • the inverter circuit 100 The method includes:
  • Step 301 In a first sequence, control the first switch to be closed, and control the first inverter switch and the second inverter switch of the bridge arm unit to be turned off.
  • the inverter circuit 100 starts to work from an initial state.
  • Figure 4a is a schematic diagram of the first control state within one cycle provided by the embodiment of the present application
  • Figure 5 is the control signals in the control process provided by the embodiment of the present application waveform diagram.
  • L Q2 represents the switching signal of IGBT switch tube Q2
  • L Q1 represents the switch signal of IGBT switch tube Q1
  • the current passing through the resonant inductor L1 is the resonant current in the resonant unit 30 .
  • the first switch corresponds to the IGBT switch tube Q1 in FIG. 2
  • the first inverter switch of the bridge arm unit corresponds to the IGBT switch tube Q2 in FIG. 2
  • the second inverter switch of the bridge arm unit Corresponding to the IGBT switch tube Q3 in FIG. 2 as an example, description will be made.
  • the control unit 50 controls the IGBT switch Q1 and the IGBT switch Q2 to be turned off, so that the inverter circuit 100 is in the initial state.
  • a first sequence may be performed.
  • the control unit 50 controls the IGBT switch Q1 to close, and keeps the IGBT switch Q2 and IGBT switch Q3 disconnected.
  • the time period from t1 to t2 since the resonant inductor L1 reduces the rate of rise of the current flowing through itself, the resonant inductor L1 can realize the zero-current soft turn-on of the IGBT switch tube Q1.
  • Step 302 In the second sequence, keep the first switch closed and the first inverter switch open, and control the second inverter switch to close.
  • the control unit 50 controls the IGBT switch Q3 to close, and keeps the IGBT switch Q1 closed and the IGBT switch Q2 turned off. Since the load current I0 all flows through the resonant inductor L1 at the beginning of the second sequence, the current on the IGBT switch Q3 is zero, and the IGBT switch Q3 realizes zero-current and zero-voltage turn-on.
  • the resonant inductance L1 charges the resonant capacitor C1
  • U C1 continues to increase
  • I L1 begins to decrease
  • the current flowing through the IGBT switch Q3 begins to increase
  • its increasing rate is the same as I L1 decreases
  • U C1 U2 (U2>E)
  • U2 is the voltage value at both ends of the resonant capacitor
  • Step 303 In the third sequence, keep the first inverter switch off and the second inverter switch on, and control the first switch to turn off.
  • the control unit 50 controls the IGBT switch Q1 to turn off, and keeps the IGBT switch Q3 closed and the IGBT switch Q2 turned off.
  • the control unit 50 controls the IGBT switch Q1 to turn off, and keeps the IGBT switch Q3 closed and the IGBT switch Q2 turned off.
  • the second diode D2 starts to conduct, the IGBT switch Q1 is short-circuited, the current flowing through the IGBT switch Q1 is zero, and the IGBT switch Q1 is turned off at the beginning of the third sequence , IGBT switch tube Q1 can realize zero-current soft shutdown.
  • the circuit continues to resonate, the resonant capacitor C1 reversely charges the resonant inductance L1, U C1 begins to decrease, and I L1 increases in reverse.
  • U C1 decreases to zero
  • I L1 reversely increases to a maximum value, and at this time, the current value flowing through the second diode D2 is a maximum value.
  • the resonant inductor L1 reversely charges the resonant capacitor C1.
  • the IGBT switch Q1 by turning off the IGBT switch Q1 during the freewheeling period of the second diode D2, the IGBT switch Q1 can be turned off with zero current.
  • I L1 reversely decreases to zero, and U C1 increases to reverse maximum value.
  • I L1 reversely decreases to zero
  • the second diode D2 is naturally turned off
  • the first diode D1 starts to conduct
  • the resonant capacitor C1 is The resonant inductance L1 is charged
  • U C1 decreases
  • I L1 increases.
  • I L1 decreases to be equal to the bus voltage (that is, the voltage value E of the DC power supply 200 )
  • I L1 reaches the maximum value, and at this time, the current value flowing through the first diode D1 is the maximum value. After that, I L1 starts to decrease.
  • the control unit 50 controls the IGBT switch Q1 and the IGBT switch Q2 to keep disconnected, and controls the IGBT switch Q3 to keep closed.
  • the first diode D1 is turned off naturally, and the load current I0 is all freewheeling through the IGBT switch tube Q3, and the resonant current I L1 is kept at 0, and the resonant voltage U C1 is kept at U3.
  • the duration of the maintenance sequence can be set according to actual needs, and the execution of the fourth sequence starts at the end of the maintenance sequence.
  • Step 304 In the fourth sequence, keep the first inverter switch off and the second inverter switch on, and control the first switch to be on.
  • the control unit 50 controls the IGBT switch Q1 to close, and keeps the IGBT switch Q3 closed and the IGBT switch Q2 turned off. Since the resonant inductance L1 reduces the rate of rise of the current flowing through the IGBT switch Q1, the IGBT switch Q1 realizes zero-current soft turn-on.
  • Step 305 In the fifth sequence, keep the first switch closed and the first inverter switch open, and control the second inverter switch to open.
  • the control unit 50 controls the IGBT switch Q3 to turn off, and keeps the IGBT switch Q1 closed and the IGBT switch Q2 turned off.
  • the body diode DQ3 of the IGBT switch Q3 starts to conduct freewheeling.
  • the IGBT switch Q3 is turned off, and the IGBT switch Q3 can be softly turned off with zero voltage and zero current.
  • the resonant capacitor C1 continues to charge the resonant inductance L1, and I L1 continues to increase.
  • U C1 decreases to zero in the opposite direction, I L1 increases to the maximum.
  • the current flowing through the IGBT switch tube The current value of Q1 is the maximum value. Thereafter, the resonant inductor L1 is discharged, and the resonant capacitor C1 is charged.
  • I L1 decreases to I0.
  • the second diode D2 is naturally turned off.
  • the load current I0 charges the resonant capacitor C1
  • the load current I0 Constant so the terminal voltage of the resonant inductor L1 is zero, and U C1 increases gradually.
  • Step 306 In the sixth sequence, keep the first inverter switch and the second inverter switch off, and control the first switch to turn off.
  • the control unit 50 controls the IGBT switch Q1 to turn off, and keeps the IGBT switch Q2 and IGBT switch Q3 off.
  • the IGBT switch Q1 can be turned off softly with zero current.
  • the resonant capacitor C1 reversely charges the resonant inductor L1, I L1 reversely increases, U C1 decreases, the current flowing through the second diode D2 gradually increases, and the current flowing through the first and second diodes The current of pole tube D1 decreases gradually, and the rate of its decrease is the same as the rate of reverse increase of I L1 .
  • I L1 decreases to E
  • I L1 reaches the maximum value, after that, the resonant inductance L1 discharges, I L1 decreases, and U C1 continues to decrease.
  • the above-mentioned embodiment describes the complete control process of the driving method within one PWM period. By repeating the above-mentioned process continuously, the DC power input by the DC power supply 200 can be continuously converted into AC output.
  • the resonance effect of the resonant unit 30 can make the current change rate of the first switch at the moment of turn-on smaller than its allowable current change rate, which is beneficial to the first switch in the inverter circuit 100.
  • Zero current turn-on is realized in the full load range, thereby achieving the purpose of reducing switching loss. It should be understood that when the current change rate of the first switch at the turn-on moment is smaller than its allowable current change rate, the current of the first switch at the turn-on moment can be approximately considered to be zero.
  • the second switch can be turned off during the body diode freewheeling period of the second switch to realize the zero current disconnection of the second switch; the third switch can be turned off during the body diode freewheeling period of the third switch , enabling the zero-current disconnection of the third switch.
  • the second switch or the third switch when the second switch or the third switch is turned off, by making the maximum value Ipmax of the resonance current in the resonance unit satisfy: I0max ⁇ Ipmax ⁇ 2I0max, wherein I0max is the maximum value of the load current, Not only can the second switch or the third switch realize zero current disconnection in the full load range, but also can further reduce the switching loss.
  • the structure of the inverter circuit 100 is relatively simple, which is conducive to simplifying the control strategy, and can also reduce the volume of the inverter including the inverter circuit 100, and can also reduce the volume of the inverter including the inverter circuit 100.
  • the cost of the inverter is relatively simple, which is conducive to simplifying the control strategy, and can also reduce the volume of the inverter including the inverter circuit 100, and can also reduce the volume of the inverter including the inverter circuit 100. The cost of the inverter.
  • the first inverter switch and the second inverter switch in the bridge arm unit 40 correspond to the second switch (IGBT switch Q2) and the third switch (IGBT switch Q3) respectively. ) as an example.
  • the first inverter switch and the second inverter switch in the bridge arm unit 40 may also correspond to the third switch (IGBT switch Q3) and the second switch (IGBT switch Q2), respectively. Its working process is similar to the above-mentioned embodiment, which is within the scope of easy understanding of those skilled in the art, and will not be repeated here.
  • the IGBT switch Q3 should be kept off. That is, in the embodiment of the present application, if the first inverter switch in the bridge arm unit 40 is kept turned off in any PWM period, the bridge arm unit should be kept open in the PWM period adjacent to the PWM period. The second inverter switch in 40 is turned off.
  • FIG. 6 is a schematic structural diagram of a driving device provided by an embodiment of the present application.
  • the driving device 600 is used to drive the inverter circuit 100 shown in FIG. 1 or FIG. 2 .
  • the drive device 600 includes a first switch control unit 601, a second switch control unit 602, a third switch control unit 603, a fourth switch control unit 604, a fifth switch control unit 605 and a sixth switch control unit 606.
  • the content of the device embodiment may refer to the method embodiment on the premise that the content does not conflict with each other, so details are not repeated here.
  • the embodiment of the present application also provides a non-volatile computer-readable storage medium, the computer-readable storage medium stores computer-executable instructions, and when the computer-executable instructions are executed by the processor, the processor executes any one of the implementation The driving method in the example.
  • the embodiment of the present application also provides a computer program product.
  • the computer program product includes a computer program stored on a computer-readable storage medium.
  • the computer program includes program instructions.
  • the embodiment of the present application also provides a multi-phase inverter circuit, including at least two inverter circuits as in any one of the above embodiments.
  • One end of the first switch in each inverter circuit is connected to the negative pole of the DC power supply, and both ends of the freewheeling unit in each inverter circuit are respectively connected to both ends of the DC power supply.
  • FIG. 7 takes a three-way inverter circuit as an example for illustration.
  • one of them is an inverter circuit 100a.
  • the sources of the IGBT switch Q11 of the first inverter circuit 100 a , the IGBT switch Q12 of the second inverter circuit and the IGBT switch Q13 of the third inverter circuit are all connected to the negative pole of the DC power supply 200 .
  • the first end of the freewheeling unit of the first inverter circuit, the first end of the freewheeling unit of the second inverter circuit, and the first end of the freewheeling unit of the third inverter circuit are all connected to the DC power supply 200
  • the positive pole is connected to the first connection point P1
  • Both of the second ends are connected to the negative pole of the DC power supply 200 at the second connection point P2.
  • each inverter circuit can be driven by the driving method in any of the above embodiments.
  • the control unit 50 controls the IGBT switch Q11 to be closed, and controls the IGBT switch Q21 and the IGBT switch Q31 to be disconnected,
  • the second sequence is executed to make the current flowing through the inductor L11 0.
  • An embodiment of the present application also provides an inverter, including the inverter circuit in any of the above embodiments, or including the inverter circuit in any of the above embodiments and the driving method in any of the above embodiments, or including the above The multi-phase inverter circuit in any one of the embodiments.

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Abstract

本申请公开了一种逆变电路及其驱动方法、以及多相逆变电路与逆变器，该逆变电路包括第一开关（10）、续流单元（20）、谐振单元（30）、桥臂单元（40）与控制单元（50），第一开关（10）分别与直流电源（200）以及续流单元（20）的中点连接，谐振单元（30）分别与续流单元（20）的中点以及桥臂单元（40）的中点连接，桥臂单元（40）的中点还用于与负载（300）连接，续流单元（20）与桥臂单元（40）并联连接，且均与直流电源（200）连接，控制单元（50）分别与第一开关（10）及桥臂单元（40）的控制端连接，控制单元（50）用于控制第一开关（10）的开关状态，并用于控制桥臂单元（40）中的逆变开关的开关状态，以将直流电源（200）的直流电转换成交流电，且交流电在桥臂单元（40）的中点输出。通过上述方式，能够通过较为简单的电路实现逆变功能，且成本较低。

Description

逆变电路及其驱动方法、以及多相逆变电路与逆变器
相关申请的交叉参考
本申请要求于2021年08月16日提交中国专利局，申请号为202110938748.6，申请名称为“逆变电路及其驱动方法、以及多相逆变电路与逆变器”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本申请涉及电力电子技术领域，例如涉及一种逆变电路及其驱动方法、以及多相逆变电路与逆变器。
背景技术
工业化的发展对电力电子装置的体积、成本、工作频率和效率的要求越来越高。追求电力电子装置的高频、高效、低成本和小型化已经成为一种发展理念。高频工作时，硬开关逆变器不仅会产生严重的开关损耗，并且伴随着严重的噪声污染和电磁干扰。为此，软开关技术诞生，并被应用到硬开关逆变器中。软开关逆变器是指在硬开关逆变器中添加辅助谐振电路，利用辅助电路中电感和电容的谐振作用，实现零电压开关或零电流开关，减小开关损耗，降低噪声污染和电磁干扰。
同时，相比于谐振直流环节软开关逆变器，谐振极型软开关逆变器拥有更加突出的优良性能，该类型逆变器通常采用三组辅助谐振电路，分别接在三相逆变器的每一相上，逆变器的三组辅助电路可实现独立控制，为三相逆变器各相桥臂上的主开关创造软开关条件，解决了辅助开关和逆变器主开关在同步操作上的冲突问题，可方便的采用常规的脉宽调制(PWM)策略进行输出电压控制。
然而，在现有技术中的谐振极型软开关逆变器中，在该逆变器中需设置较多的辅助开关，且还需设置变压器，不仅会导致电路变得复杂，还会导致逆变器的成本增加。
发明内容
本申请实施例旨在提供一种逆变电路及驱动方法、多相逆变电路与逆变器，能够通过较为简单的电路实现逆变功能，且成本较低。
为实现上述目的，第一方面，本申请提供一种逆变电路，包括：
第一开关、续流单元、谐振单元、桥臂单元与控制单元；
所述第一开关分别与所述续流单元的中点以及直流电源连接，所述谐振单元分别与所述续流单元的中点以及所述桥臂单元的中点连接，所述桥臂单元的中点还用于与负载连接，所述续流单元与所述桥臂单元并联连接，且所述续流单元及所述桥臂单元均与所述直流电源连接；
所述控制单元分别与所述第一开关及所述桥臂单元的控制端连接，所述控制单元用于控制所述第一开关的开关状态，并用于控制所述桥臂单元中的逆变开关的开关状态，以将所述直流电源的直流电转换成交流电，且所述交流电在所述桥臂单元的中点输出。
在一实施例中，所述谐振单元包括谐振电感与谐振电容；
所述谐振电感与所述谐振电容串联连接，所述谐振电感的非串联端与所述续流单元的中点连接，所述谐振电容的非串联端与所述桥臂单元的中点连接。
在一实施例中，所述桥臂单元包括第一逆变开关及第二逆变开关；
所述第一逆变开关的第一端与所述第二逆变开关的第一端均与所述控制单元连接，所述第一逆变开关的第二端、所述第二逆变开关的第三端均与所述谐振单元连接，所述第一逆变开关的第三端与所述直流电源的正极连接，所述第二逆变开关的第二端与所述直流电源的负极连接。
在一实施例中，所述续流单元包括第一二极管与第二二极管；
所述第一二极管的阴极与所述直流电源的正极连接，所述第一二极管的阳极与所述第二二极管的阴极连接，所述第二二极管的阳极与所述直流电源的负极连接；
所述第一二极管与所述第二二极管之间的连接点为所述续流单 元的中点。
第二方面，本申请提供一种逆变电路的驱动方法，用于驱动上述任一实施例中所述的逆变电路，所述的驱动方法包括：
在第一时序中，控制所述桥臂单元的第一逆变开关及第二逆变开关断开，并在所述第一时序开始的时刻，并在所述第一时序开始的时刻控制所述第一开关闭合，以使I L1＝I0，执行第二时序；其中，I L1为所述谐振单元中的谐振电流，I0为负载电流；
在所述第二时序中，保持所述第一开关闭合以及所述第一逆变开关断开，并在所述第二时序开始的时刻控制所述第二逆变开关闭合，以使I L1＝0，U C1＝U2，执行第三时序；其中，U C1为所述谐振单元中的谐振电压，U2为所述谐振单元的正向电压最大值；
在所述第三时序中，保持所述第一逆变开关断开以及所述第二逆变开关闭合，并在所述第三时序开始的时刻控制所述第一开关断开，以使I L1＝0，且U C1＝U3，执行第四时序；其中，-E<U3<0，E为所述直流电源的电压值；
在所述第四时序中，保持所述第一逆变开关断开以及所述第二逆变开关闭合，并在所述第四时序开始的时刻控制所述第一开关闭合，以使I L1＝I0，执行第五时序；
在所述第五时序中，保持所述第一开关闭合以及所述第一逆变开关断开，并在所述第五时序开始的时刻控制所述第二逆变开关断开，以使I L1＝0，且U C1＝U2，执行第六时序；
在所述第六时序中，保持所述第一逆变开关断开以及所述第二逆变开关断开，并在所述第六时序开始的时刻控制所述第一开关断开，以使I L1＝0，且U C1＝U0，并使得所述逆变电路恢复到初始状态；其中，U0为所述逆变电路处于初始状态时所述谐振单元的初始电压值。
在一实施例中，所述的驱动方法还包括初始时序；
在所述初始时序中，控制所述第一开关、所述第一逆变开关及所述第二逆变开关处于断开，以使所述逆变电路处于所述初始状态，执行所述第一时序。
在一实施例中，所述的驱动方法还包括维持时序；
在所述第三时序中，当所述I L1＝0，且U C1＝U3，执行所述维持时序，在所述维持时序中，保持所述第一开关与所述第一逆变开关断开，并保持所述第二逆变开关闭合，以使所述谐振电流维持为0，及使所述谐振电压维持为U3后，执行所述第四时序。
第三方面，本申请提供一种多相逆变电路，包括至少两路上述任一实施例中所述的逆变电路；
各所述逆变电路中的所述第一开关的一端均用于与所述直流电源的负极连接，各所述逆变电路中的续流单元的两端分别与所述直流电源的两端连接。
在一实施例中，任意一路所述逆变电路采用上述任一实施例中所述的驱动方法进行驱动。
第三方面，本申请提供一种逆变器，包括上述任一实施例中所述的逆变电路；
或者，包括上述任一实施例中所述的逆变电路及上述任一实施例中所述的驱动方法；
或者，包括上述任一实施例中所述的多相逆变电路。
本申请实施例的有益效果是：本申请提供的逆变电路包括第一开关、续流单元、谐振单元、桥臂单元与控制单元，其中，第一开关分别与续流单元的中点以及直流电源连接，谐振单元分别与续流单元的中间以及桥臂单元的中点连接，桥臂单元的中点还用于与负载连接，续流单元与桥臂单元并联连接，且均与直流电源连接，控制单元分别与第一开关以及桥臂单元连接，因此，控制单元通过控制第一开关中的开关的开关状态，以及控制桥臂单元中的开关的开关状态，能够使该逆变电路将直流电源的直流电转换成交流电，并从桥臂单元的中点输出，从而实现了逆变功能，同时，在该逆变电路中，只需设置辅助开关、续流单元、谐振单元、桥臂单元及控制单元，且辅助开关仅需包括第一开关，而无需像现有技术一样设置变压器，电路结构较为简单，也降低了成本。
附图说明
一个或多个实施例通过与之对应的附图进行示例性说明，这些示例性说明并不构成对实施例的限定，附图中具有相同参考数字标号的元件表示为类似的元件，除非有特别申明，附图中的图不构成比例限制。
图1为本申请实施例提供的逆变电路的结构示意图；
图2为本申请实施例提供的逆变电路的电路结构示意图；
图3为本申请实施例提供的驱动方法的流程图；
图4a为本申请实施例提供的逆变电路在一个周期内的第一个控制状态的示意图；
图4b为本申请实施例提供的逆变电路在一个周期内的第二个控制状态的示意图；
图4c为本申请实施例提供的逆变电路在一个周期内的第三个控制状态的示意图；
图4d为本申请实施例提供的逆变电路在一个周期内的第四个控制状态的示意图；
图4e为本申请实施例提供的逆变电路在一个周期内的第五个控制状态的示意图；
图4f为本申请实施例提供的逆变电路在一个周期内的第六个控制状态的示意图；
图4g为本申请实施例提供的逆变电路在一个周期内的第七个控制状态的示意图；
图4h为本申请实施例提供的逆变电路在一个周期内的第八个控制状态的示意图；
图4i为本申请实施例提供的逆变电路在一个周期内的第九个控制状态的示意图；
图4j为本申请实施例提供的逆变电路在一个周期内的第十个控制状态的示意图；
图4k为本申请实施例提供的逆变电路在一个周期内的第十一个控制状态的示意图；
图5为本申请实施例提供的逆变电路中各信号的波形图；
图6为本申请实施例提供的驱动装置的结构示意图；
图7为本申请实施例提供的多相逆变电路的电路结构示意图。
具体实施方式
为使本申请实施例的目的、技术方案和优点更加清楚，下面将结合本申请实施例中的附图，对本申请实施例中的技术方案进行清楚、完整地描述，显然，所描述的实施例是本申请一部分实施例，而不是全部的实施例。基于本申请中的实施例，本领域普通技术人员在没有作出创造性劳动前提下所获得的所有其他实施例，都属于本申请保护的范围。
请参照图1，图1为本申请实施例提供的逆变电路的结构示意图。如图1所示，该逆变电路100包括第一开关10、续流单元20、谐振单元30、桥臂单元40与控制单元50。其中，第一开关10的第一端与直流电源200的第二端连接，第一开关10的第二端与续流单元20的中点P1连接，谐振单元30的第一端与续流单元20的中点P1连接，谐振单元30的第二端与桥臂单元40的中点P2连接，桥臂单元40的中点P2还与负载300连接，续流单元20与桥臂单元40并联连接，即续流单元20的第一端与桥臂单元40的第一端连接，续流单元20的第二端与桥臂单元40的第二端连接，且续流单元20的第一端与第二端还分别与直流电源200的两端连接，控制单元50分别与第一开关10以及桥臂单元40连接。
具体地，第一开关10与桥臂单元40中的逆变开关均受控于控制单元50，继而，控制单元50通过控制第一开关10的开关状态，以及控制桥臂单元40中各逆变开关的开关状态，能够实现将直流电源200所提供的直流电转换为交流电，并将该交流电在桥臂单元40的中点P2处输出至负载300，用以作为负载300的供电电压。其中，各开关的开关状态指的是各开关闭合或断开的状态。
在上述过程，实现了将直流电转换为交流电，即实现了逆变功能。 同时，在该逆变电路100中，充当辅助开关的仅为第一开关10，所以辅助开关的数量较少，且无需如现有技术中一样设置变压器，使电路结构也变得简单，从而降低了成本。
为了更好的理解本申请，以图2所示的逆变电路的电路结构为例进行说明。
如图2所示，第一开关10为第一开关Q1(图中为IGBT开关管Q1)。其中，IGBT开关管Q1的门极(即G极)与控制单元50连接，IGBT开关管Q1的发射极(即E极)与直流电源200的负极连接，IGBT开关管Q1的集电极(即C极)与续流单元20的中点P1连接。
可选地，续流单元20包括第一二极管D1与第二二极管D2。其中，第一二极管D1的阳极与第二二极管D2的阴极连接，第一二极管D1的阴极与直流电源200的正极连接，第二二极管D2的阳极与直流电源200的负极连接，且第一二极管D1与第二二极管D2之间的连接点即为续流单元20的中点P1。在一个实施例中，第一二极管D1及第二二极管D2均为续流二极管。
可选地，谐振单元30包括谐振电感L1与谐振电容C1。其中，谐振电感L1与谐振电容C1串联连接，谐振电感L1的非串联连接端与续流单元20的中点P1连接，谐振电容C1的非串联连接端与桥臂单元40的中点P2连接。具体的，通过采用谐振电感L1及谐振电容C1组成的谐振单元30，由于谐振电感L1和谐振电容C1的电阻较小，逆变电路在工作时，谐振电感L1及谐振电容的功耗可以近似为零，从而降低逆变电路的功率损耗。
在一实施例中，桥臂单元40包括第二开关与第三开关。第二开关的第一端与第三开关的第一端均与控制单元连接，第二开关的第二端、第三开关的第三端均与谐振电容的非串联端连接，第二开关的第三端与直流电源的正极连接，第三开关的第二端与直流电源的负极连接。
在一实施例中，所述第二开关及所述第三开关均为IGBT管，第二开关对应图2中的IGBT开关管Q2，第三开关对应图2中的IGBT 开关管Q3。
其中，IGBT开关管Q2与IGBT开关管Q3的门极均与控制单元50连接，IGBT开关管Q2的发射极与IGBT开关管Q3的集电极连接，IGBT开关管Q2的集电极与直流电源200的正极连接，IGBT开关管Q3的发射极与直流电源200的负极连接。其中，IGBT开关管Q2与IGBT开关管Q3之间的连接点即为桥臂单元40的中点P2。
需要说明的是，在上述逆变电路100中，第一开关、第二开关与第三开关均以IGBT开关管为例。而在其他的实施例中，第一开关、第二开关与第三开关还可以为任意的电力电子元器件，例如场效应晶体管MOSFET、晶闸管SCR、门极可关断晶闸管GTO、电力晶体管GTR等类型，也可以是任意的常用开关，例如接触器、继电器、延时开关、光电开关、轻触开关、接近开关等类型，也可以是上述类型的多种组合形式。同时，第一开关、第二开关与第三开关可以相同，也可以不同。
以第一开关为例进行说明，若第一开关为IGBT开关管，则IGBT开关管的门极为第一开关的第一端，IGBT开关管的发射极为第一开关的第二端，IGBT开关管的集电极为第一开关的第三端。
上述逆变电路中，只需采用一个第一开关、一个谐振电容、一个谐振电感及两个辅助二极管，即可将直流电转化成交流电，结构简单，有利于简化控制策略，减小逆变器体积和降低逆变器成本。
在一实施例中，本申请提供一种逆变电路的驱动方法，该方法用于驱动上述任一实施例中的逆变电路的驱动方法包括：
在第一时序中，控制第一开关闭合，以及控制桥臂单元的第一逆变开关及第二逆变开关断开，以使I L1＝I0，执行第二时序；其中，I L1为谐振单元中的谐振电流，I0为负载电流；
在第二时序中，保持第一开关闭合以及第一逆变开关断开，并控制第二逆变开关闭合，以使I L1＝0，U C1＝U2，执行第三时序；其中，U C1为谐振单元中的谐振电压，U2为谐振单元的正向电压最大值；
在第三时序中，保持第一逆变开关断开以及第二逆变开关闭合，并控制第一开关断开，以使I L1＝0，且U C1＝U3(-E<U3<0)，执行第四时序；其中，E为直流电源的电压值；
在第四时序中，保持第一逆变开关断开以及第二逆变开关闭合，并控制第一开关闭合，以使I L1＝I0，执行第五时序；
在第五时序中，保持第一开关闭合以及第一逆变开关断开，并控制第二逆变开关断开，以使I L1＝0，且U C1＝U2，执行第六时序；
在第六时序中，保持第一逆变开关断开以及第二逆变开关断开，并控制第一开关断开，以使I L1＝0，且U C1＝U0，并使得逆变电路恢复到初始状态；其中，U0为逆变电路处于初始状态时谐振单元的初始电压值。
在一实施例中，逆变电路的驱动方法还包括初始时序；
在初始时序中，控制第一开关、第一逆变开关及第二逆变开关处于断开，以使逆变电路处于初始状态，执行第一时序。
在一实施例中，逆变电路的驱动方法还包括维持时序；
在第三时序中，当I L1＝0，且U C1＝U3(-E<U3<0)，执行维持时序，在维持时序中，保持第一开关与第一逆变开关断开，并保持第二逆变开关闭合，以使谐振电流维持为0，及使谐振电压维持为U3后，执行第四时序。
以下是逆变电路的驱动方法的具体实施例，请参阅图3，图3为本申请实施例提供的逆变电路的驱动方法的流程示意图，该方法用于驱动如图1或图2所示的逆变电路100。该方法包括：
步骤301：在第一时序中，控制第一开关闭合，以及控制桥臂单元的第一逆变开关及第二逆变开关断开。
在一实施例中，逆变电路100从初始状态开始工作。请一并参阅图4a与图5，其中，图4a为本申请实施例提供的在一个周期内的第一个控制状态的示意图，图5为本申请实施例提供的在控制过程中各 控制信号的波形图。在图5中，L Q2表示IGBT开关管Q2的开关信号；L Q1表示IGBT开关管Q1的开关信号；U C1表示谐振电容C1两端的电压，即谐振单元30中的谐振电压；I L1表示流过谐振电感L1的电流，即谐振单元30中的谐振电流。
同时，在此实施例中，以第一开关对应图2中的IGBT开关管Q1、桥臂单元的第一逆变开关对应图2中的IGBT开关管Q2以及桥臂单元的第二逆变开关对应图2中的IGBT开关管Q3为例进行说明。
由图5可知，在初始时序，对应的是0-t1这一段时间，控制单元50控制IGBT开关管Q1与IGBT开关管Q2均断开，从而使逆变电路100处于初始状态。此时，如图4a所示，负载电流I0(图未示)通过IGBT开关管Q2的体二极管D Q2续流，则I L1＝0，且U C1＝U0(0<U0<E),其中，E为直流电源200的电压值，U0为逆变电路处于初始状态时谐振电容两端的初始电压值。继而，可执行第一时序。
在第一时序(t1到t2时间段)中，结合图4b所示，控制单元50控制IGBT开关管Q1闭合，并保持IGBT开关管Q2与IGBT开关管Q3断开。在t1到t2时间段内：由于谐振电感L1减小了流过其本身的电流的上升率，所以谐振电感L1能够实现IGBT开关管Q1的零电流软开通。在IGBT开关管Q1闭合后，谐振电感L1和谐振电容C1开始谐振，谐振电感L1和谐振电容C1同时被充电，I L1跟U C1均逐渐增大，流过体二极管D Q2的电流逐渐减小。直至t2时刻，I L1增加至I0(即I L1＝I0)，且U C1增加至U1，则开始执行第二时序。
步骤302：在第二时序中，保持第一开关闭合以及第一逆变开关断开，并控制第二逆变开关闭合。
在第二时序(t2到t3时间段)中，结合图4c可知，控制单元50控制IGBT开关管Q3闭合，并保持IGBT开关管Q1闭合以及IGBT开关管Q2断开。由于第二时序开始的时刻，负载电流I0全部从谐振电感L1流过，则IGBT开关管Q3上的电流为零，IGBT开关管Q3实现零电流与零电压开通。在t2到t3时间段内：谐振电感L1对谐振电容C1进行充电，U C1继续增大，I L1开始减小，流过IGBT开关管Q3 的电流开始增大，其增大速率与I L1减小速率相同。直至t3时刻，I L1减小到零，U C1增大到正向最大值U2，即I L1＝0，且U C1＝U2(U2>E)，其中，U2为谐振电容两端的电压值的最大值，此时，开始执行第三时序。
步骤303：在第三时序中，保持第一逆变开关断开以及第二逆变开关闭合，并控制第一开关断开。
在第三时序(t3到t5时间段)中，如图4d所示，控制单元50控制IGBT开关管Q1断开，并保持IGBT开关管Q3闭合以及IGBT开关管Q2断开。在t3到t4时间段内：第二二极管D2开始导通，IGBT开关管Q1被短路，流过IGBT开关管Q1的电流为零，则在第三时序开始的时刻关断IGBT开关管Q1，IGBT开关管Q1可实现零电流软关断。从t3时刻开始，电路继续谐振，谐振电容C1对谐振电感L1反向充电，U C1开始减小，I L1反向增大。当U C1减小到零时，I L1反向增大到最大值，此时，流过第二二极管D2的电流值为最大值。此后，谐振电感L1对谐振电容C1反向充电。
在该实施例中，通过在第二二极管D2导通续流期间关断IGBT开关管Q1，则IGBT开关管Q1可实现零电流关断。
直至t4时刻，I L1反向减小到零，U C1增大到反向最大值。此时，结合图4e所示，在t4到t5时间段内：I L1反向减小到零，第二二极管D2自然关断，第一二极管D1开始导通，谐振电容C1对谐振电感L1充电，U C1减小，I L1增大。当U C1减小到等于母线电压(即直流电源200的电压值E)时，I L1达到最大值，此时，流过第一二极管D1的电流值为最大值。此后，I L1开始减小。
进一步地，在一实施例中，请参阅图5，在t5时刻，IL1再次减小到零，且U C1增大至U3，即I L1＝0，且U C1＝U3(-E<U3<0)。此时，开始执行维持时序。
在维持时序(即t5-t6时间段)中，控制单元50控制IGBT开关管Q1与IGBT开关管Q2保持断开，并控制IGBT开关管Q3保持闭合。结合图4f可得，第一二极管D1自然关断，负载电流I0全部经IGBT 开关管Q3续流，以及，使谐振电流I L1维持为0，及使谐振电压U C1维持为U3。并且，维持时序的持续时间可以根据实际需要来设定，并在维持时序结束的时刻开始执行第四时序。
步骤304：在第四时序中，保持第一逆变开关断开以及第二逆变开关闭合，并控制第一开关闭合。
在第四时序(即t6到t7时间段)中，结合图4g所示，控制单元50控制IGBT开关管Q1闭合，并保持IGBT开关管Q3闭合以及IGBT开关管Q2断开。因为谐振电感L1减小了流过IGBT开关管Q1的电流上升率，所以IGBT开关管Q1实现了零电流软开通。在t6到t7时间段内：IGBT开关管Q1闭合后，谐振电感L1和谐振电容C1开始谐振，谐振电容C1对谐振电感L1充电，I L1增大，U C1减小，且流过IGBT开关管Q3的电流开始减小，其减小速率与I L1增大速率相同。直至t7时刻，I L1增大至等于负载电流I0时，U C1减小到U4，流过IGBT开关管Q3的电流减小到零，即I L1＝I0，且U C1＝U4(-E<U3<U4<0)，此时，开始执行第五时序。
步骤305：在第五时序中，保持第一开关闭合以及第一逆变开关断开，并控制第二逆变开关断开。
在第五时序(即t7-t10时间段)中，结合图4h所示，控制单元50控制IGBT开关管Q3断开，并保持IGBT开关管Q1闭合以及IGBT开关管Q2断开。IGBT开关管Q3的体二极管DQ3开始导通续流，此时关断IGBT开关管Q3，则IGBT开关管Q3可实现零电压零电流软关断。在t7到t8时间段内：谐振电容C1继续对谐振电感L1充电，I L1继续增大，当U C1反向减小到等于零时，I L1增大到最大，此时，流过IGBT开关管Q1的电流值为最大值。此后，谐振电感L1放电，且谐振电容C1充电。
直至t8时刻，I L1减小到I0。结合图4i所示，在t8到t9时间段内：第二二极管D2自然关断，此时因为IGBT开关管Q2处于断开状态，所以负载电流I0对谐振电容C1充电，因为负载电流I0恒定，所以谐振电感L1的端电压为零，且U C1逐渐增大。
直至t9时刻，U C1增大到等于母线电压E。结合图4j所示，在t9到t10时间段内：IGBT开关管Q2的体二极管D Q2导通续流，谐振电感L1和谐振电容C1再次发生谐振，谐振电感L1放电，谐振电容C1充电，从而I L1减小，U C1增大。直至t10时刻，I L1减小到零，U C1增大到最大值U2，即I L1＝0，且U C1＝U2，此时，负载电流I0全部经第一二极管D1续流，开始执行第六时序。
步骤306：在第六时序中，保持第一逆变开关断开以及第二逆变开关断开，并控制第一开关断开。
在第六时序(即t10到t11时间段)中，结合图4k所示，控制单元50控制IGBT开关管Q1关断，并保持IGBT开关管Q2与IGBT开关管Q3关断。在第六时序开始的时刻，由于负载电流I0全部经IGBT开关管Q2的体二极管D Q2续流，则IGBT开关管Q1可实现零电流软关断。在t10到t11时间段内：谐振电容C1对谐振电感L1反向充电，I L1反向增大，U C1减小，流过第二二极管D2的电流逐渐增大，流过第一二极管D1的电流逐渐减小，其减小的速率与I L1反向增大的速率相同。当U C1减小到E时，I L1达到最大值，此后，谐振电感L1放电，I L1减小，U C1继续减小。
直至t11时刻，I L1减小到零，第二二极管D2自然关断。此时U C1减小到U0，负载电流I0全部经IGBT开关管Q2的体二极管D Q2续流，即I L1＝0，且U C1＝U0。从而，逆变电路100又开始进入了初始状态。
上述实施例描述了该驱动方法在一个PWM周期内的完整控制过程，通过不断重复上述过程，即可以实现不断将直流电源200所输入的直流电转换为交流电输出。
此外，当逆变电路100中的第一开关需要切换时，通过谐振单元30的谐振作用，能够使得第一开关在开通瞬间的电流变化率小于其允许的电流变化率，有利于第一开关在全负载范围内实现零电流开通，从而，达到降低开关损耗的目的。应理解，当第一开关在开通瞬间的电流变化率小于其允许的电流变化率，则可近似认为第一开关在开通瞬间的电流为零。
其次，由上述实施例可知，在第二开关的体二极管续流期间断开第二开关，能够实现第二开关的零电流断开；在第三开关的体二极管续流期间断开第三开关，能够实现第三开关的零电流断开。并且，在一实施方式中，在第二开关或第三开关断开时，通过使谐振单元中的谐振电流的最大值Ipmax满足：I0max≤Ipmax≤2I0max,其中，I0max为负载电流的最大值，既能够实现第二开关或第三开关在全负载范围内实现零电流断开，又能够进一步降低开关损耗。
同时，该逆变电路100的结构较为简单，有利于简化控制策略，并且，还能够减小由包括该逆变电路100的逆变器的体积，并且，也能够降低包括该逆变电路100的逆变器的成本。
需要说明的是，在上述实施例中，是以桥臂单元40中的第一逆变开关与第二逆变开关分别对应第二开关(IGBT开关管Q2)与第三开关(IGBT开关管Q3)为例。而在另一实施例中，也可以以桥臂单元40中的第一逆变开关与第二逆变开关分别对应第三开关(IGBT开关管Q3)与第二开关(IGBT开关管Q2)，其工作过程与上述实施例类似，其在本领域技术人员容易理解的范围内，这里不再赘述。
其次，在此实施例中，是以一个PWM周期中保持IGBT开关管Q2断开为例，那么，在下一个PWM周期，应为保持IGBT开关管Q3断开。亦即，在本申请的实施例中，若在任意一个PWM周期中保持桥臂单元40中的第一逆变开关断开，则在与该PWM周期相邻的PWM周期中应保持桥臂单元40中的第二逆变开关断开。
图6是本申请实施例提供一种驱动装置的结构示意图，该驱动装置600用于对图1或图2所示的逆变电路100进行驱动。如图6所示，驱动装置600包括第一开关控制单元601、第二开关控制单元602、第三开关控制单元603、第四开关控制单元604、第五开关控制单元605与第六开关控制单元606。
第一开关控制单元601用于在第一时序中，控制第一开关闭合，以及控制桥臂单元的第一逆变开关及第二逆变开关断开，以使I L1＝I0，执行第二时序；其中，I L1为谐振单元中的谐振电流，I0为负载电流。 第二开关控制单元602用于在第二时序中，保持第一开关闭合以及第一逆变开关断开，并控制第二逆变开关闭合，以使I L1＝0，U C1＝U2，执行第三时序；其中，U C1为谐振单元中的谐振电压，U2为谐振单元的正向电压最大值。第三开关控制单元603用于在第三时序中，保持第一逆变开关断开以及第二逆变开关闭合，并控制第一开关断开，以使I L1＝0，且U C1＝U3(-E<U3<0)，执行第四时序；其中，E为直流电源的电压值。第四开关控制单元604用于在第四时序中，保持第一逆变开关断开以及第二逆变开关闭合，并控制第一开关闭合，以使I L1＝I0，执行第五时序。第五开关控制单元605用于在第五时序中，保持第一开关闭合以及第一逆变开关断开，并控制第二逆变开关断开，以使I L1＝0，且U C1＝U2，执行第六时序。第六开关控制单元606用于在第六时序中，保持第一逆变开关断开以及第二逆变开关断开，并控制第一开关断开，以使I L1＝0，且U C1＝U0，并使得逆变电路恢复到初始状态；其中，U0为逆变电路处于初始状态时谐振单元的初始电压值。
由于装置实施例和方法实施例是基于同一构思，在内容不互相冲突的前提下，装置实施例的内容可以引用方法实施例的，在此不赘述。
本申请实施例还提供一种非易失性计算机可读存储介质，该计算机可读存储介质存储有计算机可执行指令，当计算机可执行指令被处理器执行时，使处理器执行如上任一实施例中的驱动方法。
本申请实施例还提供了一种计算机程序产品，计算机程序产品包括存储在计算机可读存储介质上的计算机程序，计算机程序包括程序指令，当程序指令被计算机执行时，使计算机执行如上任一实施例中的驱动方法。
本申请实施例还提供一种多相逆变电路，包括至少两路如上任一实施例中的逆变电路。各逆变电路中的第一开关的一端均与直流电源的负极连接，各逆变电路中的续流单元的两端分别与直流电源的两端连接。
请参照图7，图7以三路逆变电路为例进行说明。
如图7所示，其中一路为逆变电路100a。其中，第一路逆变电路100a的IGBT开关管Q11、第二路逆变电路的IGBT开关管Q12以及第三路逆变电路的IGBT开关管Q13的源极均与直流电源200的负极连接。第一路逆变电路的续流单元的第一端、第二路逆变电路的续流单元的第一端以及第三路逆变电路的续流单元的第一端均与直流电源200的正极连接于第一连接点P1，第一路逆变电路的续流单元的第二端、第二路逆变电路的续流单元的第二端以及第三路逆变电路的续流单元的第二端均与直流电源200的负极连接于第二连接点P2。
其中，在一实施例中，每一路逆变电路均可通过上述任一实施例中的驱动方法进行驱动。例如，通过该驱动方法中的步骤301驱动逆变电路100a时，亦即，在第一时序中，控制单元50控制IGBT开关管Q11闭合，并控制IGBT开关管Q21与IGBT开关管Q31断开，以使流过电感L11的电流为0，执行第二时序。
本申请实施例还提供一种逆变器，包括上述任一实施例中的逆变电路，或者包括上述任一实施例中的逆变电路以及上述任一实施例中的驱动方法，或者包括上述任一实施例中的多相逆变电路。
最后应说明的是：以上实施例仅用以说明本申请的技术方案，而非对其限制；在本申请的思路下，以上实施例或者不同实施例中的技术特征之间也可以进行组合，步骤可以以任意顺序实现，并存在如上所述的本申请的不同方面的许多其它变化，为了简明，它们没有在细节中提供；尽管参照前述实施例对本申请进行了详细的说明，本领域的普通技术人员应当理解：其依然可以对前述各实施例所记载的技术方案进行修改，或者对其中部分技术特征进行等同替换；而这些修改或者替换，并不使相应技术方案的本质脱离本申请各实施例技术方案的范围。

Claims (10)

  1. 一种逆变电路，其特征在于，包括：
    第一开关、续流单元、谐振单元、桥臂单元与控制单元；
    所述第一开关分别与所述续流单元的中点以及直流电源连接，所述谐振单元分别与所述续流单元的中点以及所述桥臂单元的中点连接，所述桥臂单元的中点还用于与负载连接，所述续流单元与所述桥臂单元并联连接，且所述续流单元及所述桥臂单元均与所述直流电源连接；
    所述控制单元分别与所述第一开关及所述桥臂单元的控制端连接，所述控制单元用于控制所述第一开关的开关状态，并用于控制所述桥臂单元中的逆变开关的开关状态，以将所述直流电源的直流电转换成交流电，且所述交流电在所述桥臂单元的中点输出。
  2. 根据权利要求1所述的逆变电路，其特征在于，
    所述谐振单元包括谐振电感与谐振电容；
    所述谐振电感与所述谐振电容串联连接，所述谐振电感的非串联端与所述续流单元的中点连接，所述谐振电容的非串联端与所述桥臂单元的中点连接。
  3. 根据权利要求1所述的逆变电路，其特征在于，
    所述桥臂单元包括第一逆变开关及第二逆变开关；
    所述第一逆变开关的第一端与所述第二逆变开关的第一端均与所述控制单元连接，所述第一逆变开关的第二端、所述第二逆变开关的第三端均与所述谐振单元连接，所述第一逆变开关的第三端与所述直流电源的正极连接，所述第二逆变开关的第二端与所述直流电源的负极连接。
  4. 根据权利要求1-3任意一项所述的逆变电路，其特征在于，
    所述续流单元包括第一二极管与第二二极管；
    所述第一二极管的阴极与所述直流电源的正极连接，所述第一二 极管的阳极与所述第二二极管的阴极连接，所述第二二极管的阳极与所述直流电源的负极连接；
    所述第一二极管与所述第二二极管之间的连接点为所述续流单元的中点。
  5. 一种逆变电路的驱动方法，其特征在于，用于驱动如权利要求1-4任意一项所述的逆变电路，所述的驱动方法包括：
    在第一时序中，控制所述桥臂单元的第一逆变开关及第二逆变开关断开，并在所述第一时序开始的时刻，并在所述第一时序开始的时刻控制所述第一开关闭合，以使I L1＝I0，执行第二时序；其中，I L1为所述谐振单元中的谐振电流，I0为负载电流；
    在所述第二时序中，保持所述第一开关闭合以及所述第一逆变开关断开，并在所述第二时序开始的时刻控制所述第二逆变开关闭合，以使I L1＝0，U C1＝U2，执行第三时序；其中，U C1为所述谐振单元中的谐振电压，U2为所述谐振单元的正向电压最大值；
    在所述第三时序中，保持所述第一逆变开关断开以及所述第二逆变开关闭合，并在所述第三时序开始的时刻控制所述第一开关断开，以使I L1＝0，且U C1＝U3，执行第四时序；其中，-E<U3<0，E为所述直流电源的电压值；
    在所述第四时序中，保持所述第一逆变开关断开以及所述第二逆变开关闭合，并在所述第四时序开始的时刻控制所述第一开关闭合，以使I L1＝I0，执行第五时序；
    在所述第五时序中，保持所述第一开关闭合以及所述第一逆变开关断开，并在所述第五时序开始的时刻控制所述第二逆变开关断开，以使I L1＝0，且U C1＝U2，执行第六时序；
    在所述第六时序中，保持所述第一逆变开关断开以及所述第二逆变开关断开，并在所述第六时序开始的时刻控制所述第一开关断开，以使I L1＝0，且U C1＝U0，并使得所述逆变电路恢复到初始状态；其中，U0为所述逆变电路处于初始状态时所述谐振单元的初始电压值。
  6. 根据权利要求5所述的逆变电路的驱动方法，其特征在于，还包括初始时序；
    在所述初始时序中，控制所述第一开关、所述第一逆变开关及所述第二逆变开关处于断开，以使所述逆变电路处于所述初始状态，执行所述第一时序。
  7. 根据权利要求5或6所述的逆变电路的驱动方法，其特征在于，还包括维持时序；
    在所述第三时序中，当所述I L1＝0，且U C1＝U3，执行所述维持时序，在所述维持时序中，保持所述第一开关与所述第一逆变开关断开，并保持所述第二逆变开关闭合，以使所述谐振电流维持为0，及使所述谐振电压维持为U3后，执行所述第四时序。
  8. 一种多相逆变电路，其特征在于，包括至少两路如权利要求1-4任意一项所述的逆变电路；
    各所述逆变电路中的所述第一开关的一端均用于与所述直流电源的负极连接，各所述逆变电路中的续流单元的两端分别与所述直流电源的两端连接。
  9. 根据权利要求8所述的多相逆变电路，其特征在于，
    任意一路所述逆变电路采用如权利要求5-7任意一项所述的驱动方法进行驱动。
  10. 一种逆变器，其特征在于，包括如权利要求1-4任意一项所述的逆变电路；
    或者，包括如权利要求1-4任意一项所述的逆变电路及如权利要求5-7任意一项所述的驱动方法；
    或者，包括如权利要求8-9任意一项所述的多相逆变电路。
PCT/CN2022/085381 2021-08-16 2022-04-06 逆变电路及其驱动方法、以及多相逆变电路与逆变器 WO2023019969A1 (zh)

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