WO2022222763A1 - 相位平衡器及基站天线 - Google Patents

相位平衡器及基站天线 Download PDF

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Publication number
WO2022222763A1
WO2022222763A1 PCT/CN2022/085596 CN2022085596W WO2022222763A1 WO 2022222763 A1 WO2022222763 A1 WO 2022222763A1 CN 2022085596 W CN2022085596 W CN 2022085596W WO 2022222763 A1 WO2022222763 A1 WO 2022222763A1
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WIPO (PCT)
Prior art keywords
branch line
line
branch
phase
phase balancer
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PCT/CN2022/085596
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English (en)
French (fr)
Inventor
刘晴宇
曾骏
曾志
邬烈锋
黄平娥
Original Assignee
摩比天线技术（深圳）有限公司
摩比科技（深圳）有限公司
摩比通讯技术（吉安）有限公司
摩比科技(西安)有限公司
深圳市晟煜智慧科技网络有限公司
西安摩比天线技术工程有限公司
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Publication of WO2022222763A1 publication Critical patent/WO2022222763A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q23/00—Antennas with active circuits or circuit elements integrated within them or attached to them

Definitions

  • the present invention relates to the technical field of mobile communication base station antennas, and in particular, to a phase balancer and a base station antenna.
  • mobile communication network plays an increasingly important role in human life, and it needs to be used almost anytime, anywhere. Therefore, as an indispensable part of mobile communication network, the use scenarios of antennas are becoming more and more abundant, and its size and performance The requirements are becoming more and more stringent. For example, in the 1710-2690MHz frequency band, the side lobe is required to be greater than 16dB or even 18dB, and the downtilt angle variation range is required to be 0.8° or even 0.5°.
  • a set of preset phases is usually designed first, and then the phase of each radiating element of the antenna array is adjusted to the same phase, and then the phase of the center frequency of the frequency band is adjusted to the preset phase.
  • the phases of each radiating element of the antenna array are in phase, that is, the electrical length from the antenna array port to each radiating element is the same, the corresponding phase curves overlap, and the preset phase changes ideally linearly with frequency. In this way, as long as the pattern meets the design requirements when the center frequency is adjusted to the preset phase, the patterns of all frequency points in the frequency band will meet the design requirements. However, it is difficult for the radiating elements and the feeding network of the antenna array to meet the theoretical phase linearity in practice.
  • each radiating element there is mutual coupling between adjacent radiating elements, and the boundaries of each radiating element may be different. Therefore, different radiating elements may have different boundaries.
  • the reflection coefficient of the antenna array will also be different, so that when the phase of each radiating element in the antenna array is adjusted to the same phase based on the center frequency point, other frequency points cannot be in phase, and the corresponding phase curves cannot overlap, that is, the phase of each radiating element is in phase.
  • the slopes are different.
  • the preset phase fluctuates too much with the frequency, the radiation performance of the antenna will deteriorate, such as high side lobes, large variation range of downtilt angle, wave width divergence and gain reduction.
  • the purpose of the present invention is to provide a phase balancer and a base station antenna, which can change the phase slope to achieve phase balance, thereby improving the radiation performance of the base station antenna.
  • the present invention provides a phase balancer, comprising a main line and a plurality of branch lines, the plurality of branch lines are respectively connected in parallel with the main line, and the ends of the plurality of branch lines are short-circuited and/or open circuit, the two ends of the main line are respectively set as the input port and the output port of the phase balancer; when the signal enters from the input port, it reaches the end of the branch line one by one through the main line.
  • the end of each branch line forms a reflected signal that returns to the main line along the branch line and continues to travel along the main line, and the signal finally reaches the output port after multi-path superposition.
  • the end of at least one of the branch lines is a short circuit, and the end of at least one of the branch lines is an open circuit.
  • At least one branch line combination is connected in parallel with the main line, and the branch line combination includes at least one first branch line and at least one second branch line; the first branch line and all The second branch lines are respectively arranged on both sides of the main line, and the first branch line and the second branch line have a common line intersection on the main line.
  • the end of the first branch line is short-circuited, and the end of the second branch line is open-circuited;
  • the ends of the first branch line and the second branch line are short-circuited;
  • the ends of the first branch line and the second branch line are open.
  • the length of the branch line is close to a quarter wavelength of the high-end frequency of the working frequency band.
  • the length of the branch line is one-fifth wavelength to one-third wavelength of the high-end frequency of the working frequency band.
  • the branch line combination includes a first branch line and a second branch line, the end of the first branch line is short-circuited, and the end of the second branch line is open circuit;
  • the signal on the first branch line has the largest current at the short-circuit, and is four-pointed away from the short-circuit The current at one wavelength is the smallest;
  • the signal on the second branch line has the smallest current at the open circuit, and the current is the largest at a quarter wavelength away from the open circuit;
  • the current of the first branch line at the line intersection is between the minimum and the maximum; so The current of the second branch line at the line intersection is between the maximum and the minimum; the current amplitude of the first branch line at the line intersection is smaller than the current amplitude of the second branch line at the line intersection;
  • the current of the first branch line at the line intersection is between the maximum and the minimum; so The current of the second branch line at the line intersection is between the minimum and the maximum; the current amplitude of the first branch line at the line intersection is greater than the current amplitude of the second branch line at the line intersection.
  • the shape of the branch line is a straight line, a broken line or an arc shape.
  • the line width of the branch line is 0.1-0.5 mm.
  • the phase balancer is arranged on a double-sided circuit board.
  • the phase balancer is applied to a one-to-two power splitter board, a Butler board or a phase shifter of a double-sided printed circuit board structure.
  • the present invention also provides a base station antenna including the phase balancer described in any one of the above.
  • the phase balancer of the present invention includes a main line and a plurality of branch lines intersecting with the main line, the ends of the plurality of branch lines are short-circuited and/or open, and the two ends of the main line are respectively the input port and the output port of the phase balancer ;
  • the signal enters from the input port of the phase balancer, it reaches the end of the branch line one by one through the main line, and forms a reflected signal at the end of each branch line to return to the main line along the branch line and continue along the main line.
  • the signal finally reaches the output port of the phase balancer after multipath superposition. Since the electrical lengths of the same path are different for different frequencies, the signals returning from the branch line to the main line at different frequencies are different.
  • the phase slope is changed to achieve phase balance.
  • the phase balancer of the invention can be flexibly applied to various components of the base station antenna, can improve the radiation performance of the base station antenna, and solve the problem that the base station antenna has high side lobes due to different phase slopes, a large variation range of the downtilt angle, the wave width is divergent and the gain is reduced. And other issues.
  • phase balancer 1 is a schematic structural diagram of a phase balancer provided by an embodiment of the present invention.
  • Fig. 2 is the initial phase schematic diagram of two-way signal
  • Fig. 3 is the phase schematic diagram after the two-way signals are adjusted to the same phase according to the conventional method
  • Fig. 4 is the phase schematic diagram after the two-way signals are adjusted to the same phase according to the conventional method after the balanced phase of the phase balancer of the present invention
  • FIG. 5 is a schematic structural diagram of a phase balancer provided in an embodiment of the present invention applied to a one-to-two power splitter;
  • Fig. 6 is the phase schematic diagram of the one-to-two power splitting board shown in Fig. 5;
  • FIG. 7 is a schematic structural diagram of a phase balancer provided in an embodiment of the present invention applied to a Butler plate;
  • FIG. 8 is a schematic structural diagram of a phase balancer provided in an embodiment of the present invention applied to a phase shifter.
  • references in this specification to "one embodiment”, “an embodiment”, “example embodiment”, etc. mean that the described embodiment may include specific features, structures or characteristics, but not every Embodiments must contain these specific features, structures or characteristics. Furthermore, such expressions are not referring to the same embodiment. Further, when a particular feature, structure or characteristic is described in conjunction with an embodiment, whether or not explicitly described, it has been shown that it is within the knowledge of those skilled in the art to incorporate such feature, structure or characteristic into other embodiments .
  • FIG. 1 shows a structure of a phase balancer provided by an embodiment of the present invention.
  • the phase balancer 100 includes a main line 10 and a plurality of branch lines 20.
  • the plurality of branch lines 20 are connected in parallel to the main line 10, respectively.
  • the ends of line 20 are shorted and/or open.
  • at least one end of the branch line 20 is a short circuit, and at least one end of the branch line 20 is an open circuit.
  • the length of the branch line 20 is close to one-quarter wavelength of the high-end frequency of the working frequency band, and more preferably, the length of the branch line 20 is one-fifth wavelength to one-third wavelength of the high-end frequency of the working frequency band.
  • Two ends of the main line 10 are respectively set as the input port 31 and the output port 32 of the phase balancer 100 .
  • the signal enters from the input port 31 of the phase balancer 100, it reaches the ends of the branch lines 20 one by one through the main line 10, and a reflected signal is formed at the end of each branch line 20 to return to the main line 10 along the branch line 20 and along the branch line 20.
  • the main line 10 continues to move forward, and the signal finally reaches the output port 32 of the phase balancer 100 after multipath superposition.
  • the electrical length corresponding to the same path is different for different frequencies, the signals returning from the branch line 20 to the main line 10 at different frequencies are different, and the phase of the signal that finally reaches the output port 32 of the phase balancer 100 after multi-path superposition changes The amount is different, that is, the phase slope has changed.
  • first branch lines 21 and four second branch lines 22 are connected in parallel on the main line 10 .
  • the signal After the signal enters from the input port 31 , it reaches the main line 10 and the branch line 20 through the main line 10 .
  • the first line intersection 40 ie, the leftmost line intersection
  • part of the signal enters the first first branch line 21 (ie, the leftmost first branch line) and the first second branch line 22 (ie, the first branch line The second branch line on the far left) and return to the first line intersection 40, after which the superimposed signal continues along the main line 10 to the second line intersection 40 of the main line 10 and the branch line 20, entering the second line The first branch line 21 and the second second branch line 22 . . . and so on, finally reach the output port 32 .
  • the phase balancer 100 of the present invention can change the phase slope of the signal, so that the phase slope of the signal changes after the multipath superposition of the phase balancer 100, so as to achieve phase balance, and the phase balancer 100 can be flexibly applied to the base station antenna component to solve the problem of Due to the different signal phase slopes of the radiating elements, the base station antenna has high side lobes, a large variation range of the downtilt angle, a divergent wave width, and a decrease in gain.
  • the phase balancer 100 is arranged on the double-sided circuit board 200 .
  • the phase balancer 100 can also be arranged on a single-sided circuit board.
  • the line width of the branch line 20 is preferably 0.1-0.5 mm. More preferably, the line width of the branch line 20 is close to 0.3mm.
  • the shape of the branch line 20 is any shape such as a straight line, a broken line or an arc.
  • the branch line 20 is in the shape of a zigzag line.
  • At least one branch line combination is connected in parallel with the main line 10 of the phase balancer 100.
  • the branch line combination includes at least one first branch line 21 and at least one second branch line 22, namely The number of branch lines in each branch line combination is greater than or equal to 2.
  • the first branch line 21 and the second branch line 22 are respectively provided on both sides of the main line 10, and the first branch line 21 and the second branch line 22 have a common line intersection 40 on the main line 10.
  • the end of the first branch line 21 is short-circuited, and the end of the second branch line 22 is open-circuited.
  • first branch line 21 and the second branch line 22 may both be short-circuited; alternatively, the ends of the first branch line 21 and the second branch line 22 are both open circuits.
  • a branch line with a short circuit at the end can also be called a short circuit branch line, and a branch line with an open end at the end can also be called an open circuit branch line.
  • the branch line combination includes a first branch line 21 and a second branch line 22 , the end of the first branch line 21 is short-circuited, and the end of the second branch line 22 is open-circuited.
  • the first branch line 21 and the second branch line 22 are respectively provided on both sides of the main line 10 , and the first branch line 21 and the second branch line 22 have a common line intersection 40 on the main line 10 .
  • the phase balancer 100 is printed on the double-sided circuit board 200, and the two ends of the main line 10 of the phase balancer 100 are respectively set as the input port 31 and the output port 32. The signal enters from the input port 31 and passes through the input port 31.
  • the main line 10 reaches the first line intersection 40 (ie, the leftmost line intersection) of the main line 10 and the branch line 20, and part of the signal enters the first branch line combination (ie, the leftmost branch line combination).
  • the first branch line 21 and the second branch line 22 return to the first line intersection 40, and then the superimposed signal continues along the main line 10 to reach the second line intersection 40 of the main line 10 and the branch line 20, and enters the first line.
  • the first branch line 21 and the second branch line 22 in the combination of the two branch lines, and so on, finally reach the output port 32 .
  • the lengths of the first branch line 21 and the second branch line 22 are close to a quarter wavelength of the high-end frequency of the working frequency band, more preferably, the lengths of the first branch line 21 and the second branch line 22 are the working frequency band One-fifth to one-third wavelength of the high-end frequencies.
  • the microwave signal on the transmission line is related to the electrical length of the corresponding path.
  • the signal reduction factor on the first branch line 21 is a cosine function related to the electrical length of the corresponding path
  • the signal on the second branch line 22 is related to the cosine function.
  • the simplification factor is then -j times the sine function related to the electrical length of the corresponding path.
  • the signal on the first branch line 21 has the largest current (-j) at the short-circuit, the impedance is zero, and the reflection coefficient is -1; the current is the smallest (0) at a quarter wavelength away from the short-circuit, and the impedance is infinite , the reflection coefficient is 1.
  • the signal on the second branch line 22 has the smallest current at the open circuit, the impedance is infinite, and the reflection coefficient is 1; at a quarter wavelength away from the open circuit, the current is the largest, the impedance is zero, and the reflection coefficient is -1.
  • the current of the first branch line 21 at the line intersection 40 is between the minimum between the maximum.
  • the current of the second branch line 22 at the line intersection 40 is between a maximum and a minimum.
  • the current amplitude of the first branch line 21 at the line intersection 40 is smaller than the current amplitude of the second branch line 22 at the line intersection 40 .
  • the current of the first branch line 21 at the line intersection 40 is between the maximum between the minimum.
  • the current of the second branch line 22 at the line intersection 40 is between a minimum and a maximum.
  • the current amplitude of the first branch line 21 at the line intersection 40 is greater than the current amplitude of the second branch line 22 at the line intersection 40 .
  • the current characteristics and impedance characteristics of the signals of the first branch line 21 and the second branch line 22 at the line intersection 40 are different. Therefore, when the branch line combination consists of two short-circuit branch lines, two open-circuit branch lines, and When a short-circuit branch line and an open-circuit branch line are formed, the current characteristics and impedance characteristics of the superimposed signals generated at the line intersection 40 in the three cases are different, and their effects on the power distribution and impedance transformation of the line intersection 40 are different, and a short circuit
  • the parallel connection of a branch line and an open branch line can compromise the different characteristics of the short-circuit branch line and the open-circuit branch line, balance the power distribution and impedance transformation of the parallel point, and make the overall performance more in line with the design requirements.
  • Figures 2 to 4 show the phase diagrams of the two-way signals in three cases.
  • Figure 2 is a schematic diagram of the initial phases of the two-channel signals.
  • the initial phases of the two-channel signals 1 and 2 are at the frequency point f1, and the phase difference between f2 and f3 increases with the increase of the frequency.
  • Figure 3 is a schematic diagram of the phase of the two signals after they are adjusted to the same phase according to the conventional method.
  • the signals 1-1 and 2-1 are in phase at the frequency point f2, that is, the phase difference is Zero, the phase difference between frequency point f1 and frequency point f3 is the same, and the sum of this phase difference is the same as before adjusting to the same phase.
  • Fig. 4 is the phase schematic diagram of the two-way signals after the balanced phase of the phase balancer of the present invention is adjusted to the same phase according to the conventional method, and the two-way signals 1 and 2 after the phase balance are adjusted to the same-phase signal 1- 2 and 2-2 are in phase at the frequency point f2, that is, the phase difference is zero, and the phase difference at the frequency points f1 and f3 is the same, but due to the phase balance, the sum of the phase differences is smaller than that shown in Figure 3. .
  • the phase balancer 100 of the present invention can be applied to the one-to-two power splitting board 300, the Butler board 400 or the phase shifter 500 of the double-sided printed circuit board structure.
  • FIG. 5 is a schematic structural diagram of a phase balancer provided in an embodiment of the present invention applied to a one-to-two power splitter board.
  • the one-to-two power splitter board 300 includes a power splitter main circuit 40 , a first power splitter branch 50 and a second power splitter Power divider branch 60 .
  • the phase balancer 100 is applied to the first power splitter branch 50 of the one-to-two power splitter board 300 of the double-sided printed circuit board structure.
  • the phase balancer 100 includes a combination of two branch lines, each branch line.
  • the combination includes a first branch line 21 and a second branch line 22, the end of the first branch line 21 is short-circuited, and the end of the second branch line 22 is open.
  • the lengths of each of the first branch line 21 and the second branch line 22 are close to two-quarter wavelengths of the high-end frequency of the working frequency band.
  • the HFSS (High-Frequency Structure Simulator) simulation phase diagram of the first power splitter branch 50 and the second power splitter branch 60 corresponding to the one-to-two power splitter board 300 is shown in FIG. 6 . It can be seen that under the action of the phase balancer 100, the phase slopes of the first power splitter branch 50 and the second power splitter branch 60 corresponding to the one-to-two power splitter board 300 are significantly reduced, specifically about 175° at 1710MHz. , 2200MHz is about 180°, and 2690MHz is about 180°.
  • FIG. 7 is a schematic diagram of the structure of the phase balancer provided in the embodiment of the present invention applied to the Butler board.
  • the phase balancer 100 shown in FIG. 1 is applied to the Butler board 400 of the double-sided printed circuit board structure.
  • the Butler board There are two phase balancers 100 on the 400, and the phase slope between ports 1 and 3, 2 and 4 on the Butler plate 400 is reduced by the action of the two phase balancers 100, so as to realize the optimization of pattern shaping .
  • FIG. 8 is a schematic structural diagram of the phase balancer provided in an embodiment of the present invention applied to a phase shifter.
  • the phase balancer 100 shown in FIG. 1 is applied to a phase shifter 500 with a double-sided printed circuit board structure.
  • the present invention also provides a base station antenna, which includes the phase balancer 100 shown in FIGS. 1 to 8 .
  • the phase balancer of the present invention includes a main line and a plurality of branch lines intersecting with the main line, the ends of the plurality of branch lines are short-circuited and/or open, and the two ends of the main line are respectively Input port and output port; when the signal enters from the input port of the phase balancer, it reaches the end of the branch line one by one through the main line, and a reflected signal is formed at the end of each branch line to return to the main line along the branch line and along the main line.
  • the line continues to move forward, and the signal finally reaches the output port of the phase balancer after multipath superposition. Since the electrical lengths of the same path are different for different frequencies, the signals returning from the branch line to the main line at different frequencies are different.
  • the phase slope is changed to achieve phase balance.
  • the phase balancer of the invention can be flexibly applied to various components of the base station antenna, can improve the radiation performance of the base station antenna, and solve the problem that the base station antenna has high side lobes due to different phase slopes, a large variation range of the downtilt angle, the wave width is divergent and the gain is reduced. And other issues.

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Abstract

本发明提供了一种相位平衡器，包括主线路和多个支线路，所述多个支线路分别并联在所述主线路上，所述多个支线路的末端为短路和/或开路，所述主线路的两端分别设置为所述相位平衡器的输入端口和输出端口；当信号从所述输入端口进入后，经所述主线路依次逐个到达所述支线路的末端，在每个所述支线路的末端形成反射信号沿着所述支线路返回到所述主线路并沿所述主线路继续前行，所述信号经过多径叠加后最终到达所述输出端口。本发明还提供一种包括有所述相位平衡器的基站天线。借此，本发明能够改变相位斜率，实现相位平衡，从而提高基站天线的辐射性能。

Description

相位平衡器及基站天线 技术领域
本发明涉及移动通信基站天线技术领域，尤其涉及一种相位平衡器及基站天线。
背景技术
当下移动通信网络在人类生活中扮演得角色越来越重要，几乎随时随地都需要用到，因此作为移动通信网络中不可或缺的一部分，天线的使用场景也越来越丰富，其尺寸和性能要求越来越严苛，比如在1710-2690MHz频段内旁瓣要求大于16dB甚至18dB，下倾角变化范围要求0.8°甚至0.5°。
当天线方向图有赋形要求时，通常先设计一组预置相位，接着将天线阵列每个辐射单元的相位调至同相，然后再将频带中心频点的相位调至预置相位。理想地，天线阵列每个辐射单元的相位同相，即从天线阵列端口到每个辐射单元的电长度相同，对应的相位曲线重合，预置相位随频率呈理想线性变化。如此，只要中心频点调至预置相位时方向图符合设计要求，那么频带内所有频点的方向图都将会符合设计要求。然而，实际上天线阵列的辐射单元和馈电网络自身都难以满足理论上的相位线性度，加上相邻辐射单元之间存在互耦，每个辐射单元的边界可能会不同，因此不同辐射单元的反射系数也会不同，使得天线阵列中每个辐射单元的相位在以中心频点为准调至同相时，其他频点并不能同相，对应的相位曲线不能重合，即每个辐射单元的相位斜率不同。当预置相位随频率变化波动过大时天线辐射性能会出现恶化，如旁瓣高，下倾角变化范围大、波宽发散以及增益降低等。显然，频带越宽，辐射单元实际相位偏离预置相位越严重，对天线旁瓣，下倾角变化范围、波宽以及增益的影响随之加剧。
因此，为了改善天线辐射单元的相位斜率差异，提高天线旁瓣，下倾角变化范围、波宽以及增益等性能指标，需要一种能够改变信号相位斜率，实现相位平衡的方法。
综上可知，现有技术在实际使用上显然存在不便与缺陷，所以有必要加以改进。
发明内容
针对上述的缺陷，本发明的目的在于提供一种相位平衡器及基站天线，其能够改变相位斜率，实现相位平衡，从而提高基站天线的辐射性能。
为了实现上述目的，本发明提供一种相位平衡器，包括主线路和多个支线路，所述多个支线路分别并联在所述主线路上，所述多个支线路的末端为短路和/或开路，所述主线路的两端分别设置为所述相位平衡器的输入端口和输出端口；当信号从所述输入端口进入后，经所述主线路依次逐个到达所述支线路的末端，在每个所述支线路的末端形成反射信号沿着所述支线路返回到所述主线路并沿所述主线路继续前行，所述信号经过多径叠加后最终到达所述输出端口。
根据本发明所述的相位平衡器，所述多个支线路中至少有一个所述支线路的末端为短路，至少有一个所述支线路的末端为开路。
根据本发明所述的相位平衡器，所述主线路上并联有至少一个支线路组合，所述支线路组合包括至少一个第一支线路和至少一个第二支线路；所述第一支线路和所述第二支线路分别设于所述主线路的两侧，所述第一支线路和所述第二支线路在所述主线路上具有共同的线路交点。
根据本发明所述的相位平衡器，所述第一支线路的末端短路，所述第二支线路的末端开路；或者
所述第一支线路和所述第二支线路的末端短路；或者
所述第一支线路和所述第二支线路的末端开路。
根据本发明所述的相位平衡器，所述支线路的长度接近工作频段高端频率的四分之一波长。
根据本发明所述的相位平衡器，所述支线路的长度为工作频段高端频率的五分之一波长到三分之一波长。
根据本发明所述的相位平衡器，所述支线路组合包括一个第一支线路和一个第二支线路，所述第一支线路的末端短路，所述第二支线路的末端开路；
当所述第一支线路和所述第二支线路的长度均等于工作频段高端频率的四分之一波长时；所述第一支线路上的信号在短路处电流最大，在距离短路处四分之一波长处电流最小；所述第二支线路上的信号则在开路处电流最小，在距离开路处四分之一波长处电流最大；
当所述第一支线路和所述第二支线路的长度均小于工作频段高端频率的四分之一波长时，所述第一支线路在线路交点的电流介于最小和最大之间；所述第二支线路在线路交点的电流介于最大和最小之间；所述第一支线路在线路交点的电流幅度小于所述第二支线路在线路交点的电流幅度；
当所述第一支线路和所述第二支线路的长度均大于工作频段高端频率的四分之一波长时，所述第一支线路在线路交点的电流介于最大和最小之间；所述第二支线路在线路交点的电流介于最小和最大之间；所述第一支线路在线路交点的电流幅度大于所述第二支线路在线路交点的电流幅度。
根据本发明所述的相位平衡器，所述支线路的形状为直线形、折线形或者弧线形。
根据本发明所述的相位平衡器，所述支线路的线宽为0.1～0.5mm。
根据本发明所述的相位平衡器，所述相位平衡器设置在双面线路板上。
根据本发明所述的相位平衡器，所述相位平衡器应用在双面印制线路板结构的一分二功分板、巴特勒板或者移相器上。
本发明还提供一种基站天线，包括有如任一项所述的相位平衡器。
本发明相位平衡器包括主线路以及与所述主线路相交的多个支线路，多个支线路的末端为短路和/或开路，主线路的两端分别为相位平衡器的输入端口和输出端口；当信号从相位平衡器的输入端口进入后，经主线路依次逐个到达支线路的末端，在每个支线路的末端形成反射信号沿着支线路返回到主线路并沿主线路继续前行，信号经过多径叠加后最终到达相位平衡器的输出端口。由于同一路径对不同频率来说对应的电长度不同，因此不同频率从支线路返回到主线路的信号不同，经过多径叠加后最终到达相位平衡器的输出端口的信号的相位改变量不同，即相位斜率发生了变化，可实现相位平衡。本发明相位平衡器可灵活应用到基站天线的各种部件中，能够提高基站天线的辐射性能，解决基站天线因相位斜率不同而造成旁瓣高，下倾角变化范围大、波宽发散以及增益降低等问题。
附图说明
图1是本发明实施例提供的一种相位平衡器的结构示意图；
图2是两路信号的初始相位示意图；
图3是两路信号按常规方法调至同相后的相位示意图；
图4是两路信号经本发明相位平衡器的平衡相位后按常规方法调至同相后的相位示意图；
图5是本发明实施例提供的相位平衡器应用在一分二功分板的结构示意图；
图6是图5所示的一分二功分板的相位示意图；
图7是本发明实施例提供的相位平衡器应用在巴特勒板的结构示意图；
图8是本发明实施例提供的相位平衡器应用在移相器的结构示意图。
具体实施方式
为了使本发明的目的、技术方案及优点更加清楚明白，以下结合附图及实施例，对本发明进行进一步详细说明。应当理解，此处所描述的具体实施例仅仅用以解释本发明，并不用于限定本发明。
需要说明的，本说明书中针对“一个实施例”、“实施例”、“示例实施例”等的引用，指的是描述的该实施例可包括特定的特征、结构或特性，但是不是每个实施例必须包含这些特定特征、结构或特性。此外，这样的表述并非指的是同一个实施例。进一步，在结合实施例描述特定的特征、结构或特性时，不管有没有明确的描述，已经表明将这样的特征、结构或特性结合到其它实施例中是在本领域技术人员的知识范围内的。
此外，在说明书及后续的权利要求当中使用了某些词汇来指称特定组件或部件，所属领域中具有通常知识者应可理解，制造商可以用不同的名词或术语来称呼同一个组件或部件。本说明书及后续的权利要求并不以名称的差异来作为区分组件或部件的方式，而是以组件或部件在功能上的差异来作为区分的准则。在通篇说明书及后续的权利要求书中所提及的“包括”和“包含”为一开放式的用语，故应解释成“包含但不限定于”。以外，“连接”一词在此系包含任何直接及间接的电性连接手段。间接的电性连接手段包括通过其它装置进行连接。
图1示出了本发明实施例提供的相位平衡器的结构，所述相位平衡器100包括主线路10和多个支线路20，多个支线路20分别并联在主线路10上，多个支线路20的末端为短路和/或开路。优选的是，所述多个支线路20中，至少有一个支线路20的末端为短路，至少有一个支线路20的末端为开路。优选的是， 支线路20的长度接近工作频段高端频率的四分之一波长，更好的是，支线路20的长度为工作频段高端频率的五分之一波长到三分之一波长。所述主线路10的两端分别设置为相位平衡器100的输入端口31和输出端口32。当信号从相位平衡器100的输入端口31进入后，经主线路10依次逐个到达支线路20的末端，在每个支线路20的末端形成反射信号沿着支线路20返回到主线路10并沿主线路10继续前行，信号经过多径叠加后最终到达相位平衡器100的输出端口32。由于同一路径对不同频率来说对应的电长度不同，因此不同频率从支线路20返回到主线路10的信号不同，经过多径叠加后最终到达相位平衡器100的输出端口32的信号的相位改变量不同，即相位斜率发生了变化。
如图1所示，主线路10上并联有四个第一支线路21和四个第二支线路22，当信号从输入端口31进入后，经主线路10到达主线路10和支线路20的第一个线路交点40(即最左侧的线路交点)，部分信号分别进入第一个第一支线路21(即最左侧的第一支线路)和第一个第二支线路22(即最左侧的第二支线路)并返回到第一个线路交点40，之后叠加信号沿着主线路10继续前行到达主线路10和支线路20的第二个线路交点40，进入第二个第一支线路21和第二个第二支线路22…，以此类推，最后到达输出端口32。
本发明相位平衡器100能够改变信号相位斜率，使信号经过相位平衡器100的多径叠加作用后相位斜率发生变化，实现相位平衡，可将相位平衡器100灵活应用到基站天线部件中，以解决因辐射单元的信号相位斜率不同而造成基站天线旁瓣高，下倾角变化范围大、波宽发散以及增益降低等问题。
优选的是，所述相位平衡器100设置在双面线路板200上。当然，所述相位平衡器100也可设置在单面线路板上。
所述支线路20的特性阻抗越大，即线宽越窄，对线路交点40(即并联点)的阻抗变换影响越小。因此，所述支线路20的线宽优选为0.1～0.5mm。更好的是，所述支线路20的线宽接近0.3mm。
优选的是，所述支线路20的形状为直线形、折线形或者弧线形等任意形状。如图1所示的优选实施例中，支线路20的形状为折线形。
优选的是，所述相位平衡器100的主线路10上并联有至少一个支线路组合，如图1所示，支线路组合包括至少一个第一支线路21和至少一个第二支线路22，即每个支线路组合中支线路的数量大于或等于2。第一支线路21和第二支线路 22分别设于主线路10的两侧，第一支线路21和第二支线路22在主线路10上具有共同的线路交点40。本实施例中，第一支线路21的末端短路，第二支线路22的末端开路。当然，第一支线路21和第二支线路22的末端也可以均为短路；或者，第一支线路21和第二支线路22的末端均为开路。末端为短路的支线路又可称为短路支线路，末端为开路的支线路又可称为开路支线路。
本发明优选实施例中，所述支线路组合包括一个第一支线路21和一个第二支线路22，第一支线路21的末端短路，第二支线路22的末端开路。第一支线路21和第二支线路22分别设于主线路10的两侧，第一支线路21和第二支线路22在主线路10上具有共同的线路交点40。如图1所示，相位平衡器100印制在双面线路板200上，相位平衡器100的主线路10的两端分别设置为输入端口31和输出端口32，信号从输入端口31进入，经主线路10到达主线路10和支线路20的第一个线路交点40(即最左侧的线路交点)，部分信号分别进入第一个支线路组合(即最左侧的支线路组合)中的第一支线路21和第二支线路22并返回到第一个线路交点40，之后叠加信号沿着主线路10继续前行到达主线路10和支线路20的第二个线路交点40，进入第二个支线路组合中的第一支线路21和第二支线路22…，以此类推，最后到达输出端口32。
优选的是，第一支线路21和第二支线路22的长度接近工作频段高端频率的四分之一波长，更好的是，第一支线路21和第二支线路22的长度为工作频段高端频率的五分之一波长到三分之一波长。
以第一个支线路组合为例，其他支线路组合同理。当第一支线路21和第二支线路22的长度均等于工作频段高端频率的四分之一波长时。理想地，传输线上的微波信号与对应路径的电长度有关，比较而言，第一支线路21上的信号简化因子是与对应路径的电长度有关的余弦函数，第二支线路22上的信号简化因子则是与对应路径的电长度有关的正弦函数的-j倍。具体来说，第一支线路21上的信号在短路处电流最大(-j)，阻抗为零，反射系数为-1；在距离短路处四分之一波长处电流最小(0)，阻抗无穷大，反射系数为1。第二支线路22上的信号则在开路处电流最小，阻抗无穷大，反射系数为1；在距离开路处四分之一波长处电流最大，阻抗为零，反射系数为-1。
当第一支线路21和第二支线路22的长度均略微小于工作频段高端频率的四分之一波长时，如五分之一波长，第一支线路21在线路交点40的电流介于 最小和最大之间。第二支线路22在线路交点40的电流介于最大和最小之间。第一支线路21在线路交点40的电流幅度小于第二支线路22在线路交点40的电流幅度。
当第一支线路21和第二支线路22的长度均略微大于工作频段高端频率的四分之一波长时，如三分之一波长，第一支线路21在线路交点40的电流介于最大和最小之间。第二支线路22在线路交点40的电流介于最小和最大之间。第一支线路21在线路交点40的电流幅度大于第二支线路22在线路交点40的电流幅度。
由此可见，第一支线路21和第二支线路22在线路交点40的信号的电流特性、阻抗特性不同，因此当支线路组合分别由两个短路支线路组成，两个开路支线路组成以及一个短路支线路和一个开路支线路组成时，三种情况下在线路交点40产生的叠加信号的电流特性、阻抗特性不同，其对线路交点40的功率分配、阻抗变换的作用不同，而且一个短路支线路和一个开路支线路并联能够折中短路支线路、开路支线路的不同特性，平衡并联点的功率分配和阻抗变换，使整体性能更符合设计要求。
值得提醒的是，当支线路20的长度接近工作频段高端频率的四分之一波长时，高端频率在线路交点40的信号多径叠加变化程度大于低端频率，因此支线路组合越多，相位斜率变化越大。
图2～4所示为三种情况下两路信号的相位示意图。
图2是两路信号的初始相位示意图，两路信号1和2的初始相位在频点f1，f2和f3的相位差随着频率的增加而增大，理想地，当f2＝(f1+f3)/2时，频点f1，f2和频点f3的相位差呈等差序列。
图3是两路信号按常规方法调至同相后的相位示意图，按常规方法将两路信号1和2调至同相后的信号1-1和2-1在频点f2同相，即相位差为零，在频点f1和频点f3的相位差相同，此相位差之和与调至同相前相同。
图4是两路信号经本发明相位平衡器的平衡相位后按常规方法调至同相后的相位示意图，将经过相位平衡后的两路信号1和2按常规方法调至同相后的信号1-2和2-2在频点f2同相，即相位差为零，在频点f1和f3的相位差相同，但由于经过了相位平衡，此相位差之和与图3所示相比变小了。
优选的是，本发明相位平衡器100可应用在双面印制线路板结构的一分二 功分板300、巴特勒板400或者移相器500上。
图5是本发明实施例提供的相位平衡器应用在一分二功分板的结构示意图，一分二功分板300包括功分器主路40、第一功分器支路50和第二功分器支路60。所述相位平衡器100应用在双面印制线路板结构的一分二功分板300的第一功分器支路50上，相位平衡器100上包括两个支线路组合，每个支线路组合包括一个第一支线路21和一个第二支线路22，第一支线路21的末端短路，第二支线路22的末端开路。每个第一支线路21和第二支线路22的长度均接近工作频段高端频率的四分之二波长。一分二功分板300对应的第一功分器支路50和第二功分器支路60的HFSS(High-Frequency Structure Simulator，高频结构仿真器)仿真相位图如图6所示，可见在相位平衡器100的作用下，一分二功分板300对应的第一功分器支路50和第二功分器支路60的相位斜率明显减小了，具体为1710MHz约175°，2200MHz约180°，2690MHz约180°。
图7是本发明实施例提供的相位平衡器应用在巴特勒板的结构示意图，将图1所示的相位平衡器100应用在双面印制线路板结构的巴特勒板400上，巴特勒板400上设有两个相位平衡器100，通过两个相位平衡器100的作用减小了巴特勒板400上的端口1和3，2和4之间的相位斜率，以实现方向图赋形优化。
图8是本发明实施例提供的相位平衡器应用在移相器的结构示意图，将图1所示的相位平衡器100应用在双面印制线路板结构的移相器500上，移相器500上设有三个相位平衡器100，通过三个相位平衡器100减小了移相器500上的端口1、5、6和2、3、4之间的相位斜率，以实现方向图赋形优化。
本发明还提供一种基站天线，包括有如图1～图8所示的相位平衡器100。
综上所述，本发明相位平衡器包括主线路以及与所述主线路相交的多个支线路，多个支线路的末端为短路和/或开路，主线路的两端分别为相位平衡器的输入端口和输出端口；当信号从相位平衡器的输入端口进入后，经主线路依次逐个到达支线路的末端，在每个支线路的末端形成反射信号沿着支线路返回到主线路并沿主线路继续前行，信号经过多径叠加后最终到达相位平衡器的输出端口。由于同一路径对不同频率来说对应的电长度不同，因此不同频率从支线路返回到主线路的信号不同，经过多径叠加后最终到达相位平衡器的输出端口的信号的相位改变量不同，即相位斜率发生了变化，可实现相位平衡。本发明相位平衡器可灵活应用到基站天线的各种部件中，能够提高基站天线的辐射性 能，解决基站天线因相位斜率不同而造成旁瓣高，下倾角变化范围大、波宽发散以及增益降低等问题。
当然，本发明还可有其它多种实施例，在不背离本发明精神及其实质的情况下，熟悉本领域的技术人员当可根据本发明作出各种相应的改变和变形，但这些相应的改变和变形都应属于本发明所附的权利要求的保护范围。

Claims (12)

  1. 一种相位平衡器，其特征在于，包括主线路和多个支线路，所述多个支线路分别并联在所述主线路上，所述多个支线路的末端为短路和/或开路，所述主线路的两端分别设置为所述相位平衡器的输入端口和输出端口；当信号从所述输入端口进入后，经所述主线路依次逐个到达所述支线路的末端，在每个所述支线路的末端形成反射信号沿着所述支线路返回到所述主线路并沿所述主线路继续前行，所述信号经过多径叠加后最终到达所述输出端口。
  2. 根据权利要求1所述的相位平衡器，其特征在于，所述多个支线路中至少有一个所述支线路的末端为短路，至少有一个所述支线路的末端为开路。
  3. 根据权利要求1所述的相位平衡器，其特征在于，所述主线路上并联有至少一个支线路组合，所述支线路组合包括至少一个第一支线路和至少一个第二支线路；所述第一支线路和所述第二支线路分别设于所述主线路的两侧，所述第一支线路和所述第二支线路在所述主线路上具有共同的线路交点。
  4. 根据权利要求3所述的相位平衡器，其特征在于，所述第一支线路的末端短路，所述第二支线路的末端开路；或者
    所述第一支线路和所述第二支线路的末端短路；或者
    所述第一支线路和所述第二支线路的末端开路。
  5. 根据权利要求4所述的相位平衡器，其特征在于，所述支线路的长度接近工作频段高端频率的四分之一波长。
  6. 根据权利要求5所述的相位平衡器，其特征在于，所述支线路的长度为工作频段高端频率的五分之一波长到三分之一波长。
  7. 根据权利要求4所述的相位平衡器，其特征在于，所述支线路组合包括一个第一支线路和一个第二支线路，所述第一支线路的末端短路，所述第二支线路的末端开路；
    当所述第一支线路和所述第二支线路的长度均等于工作频段高端频率的四分之一波长时；所述第一支线路上的信号在短路处电流最大，在距离短路处四分之一波长处电流最小；所述第二支线路上的信号则在开路处电流最小，在距离开路处四分之一波长处电流最大；
    当所述第一支线路和所述第二支线路的长度均小于工作频段高端频率的四分之一波长时，所述第一支线路在线路交点的电流介于最小和最大之间；所述 第二支线路在线路交点的电流介于最大和最小之间；所述第一支线路在线路交点的电流幅度小于所述第二支线路在线路交点的电流幅度；
    当所述第一支线路和所述第二支线路的长度均大于工作频段高端频率的四分之一波长时，所述第一支线路在线路交点的电流介于最大和最小之间；所述第二支线路在线路交点的电流介于最小和最大之间；所述第一支线路在线路交点的电流幅度大于所述第二支线路在线路交点的电流幅度。
  8. 根据权利要求1所述的相位平衡器，其特征在于，所述支线路的形状为直线形、折线形或者弧线形。
  9. 根据权利要求1所述的相位平衡器，其特征在于，所述支线路的线宽为0.1～0.5mm。
  10. 根据权利要求1所述的相位平衡器，其特征在于，所述相位平衡器设置在双面线路板上。
  11. 根据权利要求10所述的相位平衡器，其特征在于，所述相位平衡器应用在双面印制线路板结构的一分二功分板、巴特勒板或者移相器上。
  12. 一种基站天线，其特征在于，包括有如权利要求1～12任一项所述的相位平衡器。
PCT/CN2022/085596 2021-04-22 2022-04-07 相位平衡器及基站天线 WO2022222763A1 (zh)

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Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2001018959A1 (fr) * 1999-09-02 2001-03-15 Fujitsu Limited Egaliseur a amplitude variable
CN106384891A (zh) * 2016-11-25 2017-02-08 京信通信技术(广州)有限公司 相位平衡单元及功分器电路相位平衡装置
CN113161745A (zh) * 2021-04-22 2021-07-23 摩比天线技术（深圳）有限公司 相位平衡器及基站天线

Family Cites Families (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH10322146A (ja) * 1997-05-21 1998-12-04 Mitsubishi Electric Corp 増幅器モジュール
US10855332B2 (en) * 2017-12-06 2020-12-01 Mitsubishi Electric Corporation Signal transmission system
CN214849055U (zh) * 2021-04-22 2021-11-23 摩比天线技术（深圳）有限公司 相位平衡器及基站天线

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2001018959A1 (fr) * 1999-09-02 2001-03-15 Fujitsu Limited Egaliseur a amplitude variable
CN106384891A (zh) * 2016-11-25 2017-02-08 京信通信技术(广州)有限公司 相位平衡单元及功分器电路相位平衡装置
CN113161745A (zh) * 2021-04-22 2021-07-23 摩比天线技术（深圳）有限公司 相位平衡器及基站天线

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
EOM SOON-YOUNG, PARK HAN-KYU: "New switched-network phase shifter with broadband characteristics", MICROWAVE AND OPTICAL TECHNOLOGY LETTERS, vol. 38, no. 4, 20 August 2003 (2003-08-20), US , pages 255 - 257, XP055978187, ISSN: 0895-2477, DOI: 10.1002/mop.11030 *
ZHEN-YU ZHANG; YONG-XIN GUO; LING CHUEN ONG; CHIA M Y W: "A New Wide-band Planar Balun on a Single-Layer PCB", IEEE MICROWAVE AND WIRELESS COMPONENTS LETTERS, vol. 15, no. 6, 1 June 2005 (2005-06-01), pages 416 - 418, XP001232146, ISSN: 1531-1309, DOI: 10.1109/LMWC.2005.850486 *

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