WO2020103831A1 - 一种开关电源 - Google Patents

一种开关电源

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Publication number
WO2020103831A1
WO2020103831A1 PCT/CN2019/119499 CN2019119499W WO2020103831A1 WO 2020103831 A1 WO2020103831 A1 WO 2020103831A1 CN 2019119499 W CN2019119499 W CN 2019119499W WO 2020103831 A1 WO2020103831 A1 WO 2020103831A1
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WIPO (PCT)
Prior art keywords
switch tube
circuit
current
switch
capacitor
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PCT/CN2019/119499
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English (en)
French (fr)
Inventor
涂大锐
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中兴通讯股份有限公司
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Publication of WO2020103831A1 publication Critical patent/WO2020103831A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the embodiments of the present application relate to but are not limited to power electronic conversion technology, such as a switching power supply.
  • the embodiments of the present application provide a switching power supply, which can achieve current sharing.
  • An embodiment of the present application provides a switching power supply, including: a first switch tube circuit configured to convert an input first DC current into a first AC current; an N-way parallel resonant cavity circuit configured to convert the first The AC current is converted into a second AC current; where the i-th parallel resonant cavity circuit includes an i-th resonant capacitor connected in series, an i-th winding coupled with a resonant inductor, and an i-th transformer, i is greater than or equal to 1 and less than Or an integer equal to N, where N is an integer greater than or equal to 2; the second switch tube circuit is configured to rectify and convert the second alternating current into a second direct current.
  • FIG. 1 is a schematic structural diagram of a switching power supply according to an embodiment of this application.
  • FIG. 2 is a schematic diagram of a coupled resonance inductor provided by an embodiment of the present application.
  • FIG. 3 is a schematic circuit diagram of a switching power supply realized by an uncoupled resonance inductor provided by an embodiment of the present application;
  • FIG. 4 is a schematic diagram of an implementation circuit of a switching power supply according to an embodiment of the present application.
  • FIG. 5 is a schematic diagram of another switching power supply implementation circuit provided by an embodiment of the present application.
  • FIG. 6 is a schematic diagram of yet another circuit for implementing a switching power supply according to an embodiment of the present application.
  • an embodiment of the present application proposes a switching power supply, including a first switching tube circuit 101, an N-way resonant cavity circuit 102, and a second switching tube circuit 103.
  • the first switch circuit 101 is configured to convert the input first DC current into a first AC current.
  • the N-way parallel resonant cavity circuit 102 is configured to convert the first AC current into a second AC current; wherein, the i-th parallel resonant cavity circuit includes an i-th resonance capacitor connected in series and a i-th Windings and the i-th transformer, i is an integer greater than or equal to 1 and less than or equal to N, and N is an integer greater than or equal to 2.
  • the second switch tube circuit 103 is configured to rectify and convert the second alternating current into a second direct current.
  • the coupled resonant inductor includes: a magnetic core and N windings, the N windings are wound on the center column or side column of the magnetic core, and N windings Since the magnetic fields generated by the current changes are superimposed on each other, the number of turns of the N windings is the same.
  • the coupled resonant inductor plays a role of current sharing. In the absence of the coupled resonant inductor, the resonant cavity will be prone to uneven current.
  • the following analysis will be carried out: 3 Taking N as 2 as an example, a circuit schematic diagram of a switching power supply implemented by an uncoupled resonant inductor according to an embodiment of the present application is given. As shown in FIG. 3, when there is no deviation between the resonant inductance 1 and the resonant inductance 2, there is no deviation between the two currents. In the actual circuit, there are deviations in the component parameters.
  • the following situations may exist: (1) When 1 is 5% upward and resonance inductor 2 is 5% downward, the current deviation between i 1 and i 2 is about 20%; (2) 10% is above resonance inductor 1 and 10% is below resonance inductor 2 (most In the case of bad conditions), the current deviation between i 1 and i 2 is about 40%.
  • the uneven current is a physical quantity that characterizes the difference between the currents flowing through the two resonant inductors.
  • FIG. 2 The structure of the coupled resonant inductance is shown in FIG. 2. Since the two windings of the coupled resonant inductance are in the same direction as above, the magnetic flux generated by the two windings is superimposed when the current flows as shown in FIG. In the case where the current of one of the windings increases, such as when the current i 1 of the winding 1 increases, the winding 2 hinders the increase of the magnetic flux, because the characteristic of the inductance is to hinder the change of the magnetic flux in the magnetic circuit, thus hindering the increase of i 1 . Similarly, when i 1 decreases, winding 2 impedes the reduction of i 1 .
  • L 1 is the self-inductance coefficient of winding 1
  • M is the mutual inductance coefficient
  • i 2 is the current of winding 2
  • L 2 is the self-inductance coefficient of the winding 2.
  • the voltage across winding 1 is the voltage across winding 1
  • the voltage across winding 2 is the voltage across winding 2
  • u cr1 denote the terminal voltage of the first resonant capacitor of the first resonant cavity circuit
  • C cr1 is the capacitance value of the first resonant capacitor
  • i cr1 the current of the first resonant capacitor of the first resonant cavity circuit
  • u L1 represents the first The voltage across the resonant inductance of the 1st resonant cavity circuit
  • i L1 represents the current of the resonant inductance of the 1st resonant cavity circuit.
  • i cr1 equal to i L1; represents a terminal voltage of the second resonant circuit second capacitor resonant cavity path by u cr2,
  • C cr2 is the capacitance of the capacitor of the second harmonic, i cr2 second resonator circuit path
  • Current of the second resonant capacitor i L2 represents the current of the resonant inductor of the second resonant cavity circuit
  • u L2 represents the voltage across the resonant inductor of the second resonant cavity circuit, due to the resonant inductance of the second resonant cavity circuit ( That is, the second winding of the coupled resonant inductor) and the second resonant capacitor are connected in series, so i cr2 is equal to i L2 .
  • the coupling structure for the i cr1 resonant inductor tends to decrease, for i cr2 tends to increase, thereby suppressing the cavity of the first current path resonator circuit, increasing the second current path cavity resonator circuit, the final Form a closed-loop negative feedback, so that the two currents are the same.
  • FIG. 4 shows the implementation circuit diagram of a switching power supply provided by the embodiment of the present application when N is 2 as an example
  • FIG. 5 shows the embodiment of the present application when N is 3 as an example Provide another schematic diagram of the realization of the switching power supply circuit. As shown in FIGS.
  • the first switch tube circuit 101 includes: a first switch tube VT1, a second switch tube VT2, a third switch tube VT3, and a fourth switch tube VT4; wherein, the first switch tube VT1 The first end of the first DC current is connected to the first end of the third switching tube VT3, and the second end of the first switching tube VT1 is connected to the first end of the second switching tube VT2 And the first end of the N-channel parallel resonant cavity circuit; the second end of the second switching tube VT2 is connected to the second end of the fourth switching tube VT4 and the second end of the first DC current The second end of the third switching tube VT3 is connected to the first end of the fourth switching tube VT4 and the second end of the N-way parallel resonant cavity circuit.
  • the second switch tube circuit 103 includes: a fifth switch tube VT5, a sixth switch tube VT6, a seventh switch tube VT7, and an eighth switch tube VT8; wherein, the first end of the fifth switch tube VT5 is connected to the The first end of the second direct current and the first end of the seventh switch VT7, the second end of the fifth switch VT5 is connected to the third end of the N-way parallel resonant cavity circuit and the first The first end of the six switch VT6; the second end of the sixth switch VT6 is connected to the second end of the second direct current and the second end of the eighth switch VT8; the seventh switch The second end of VT7 is connected to the first end of the eighth switching tube VT8 and the fourth end of the N-way parallel resonant cavity circuit.
  • the first switch tube circuit and the second switch tube circuit in the embodiments of the present application may also adopt other implementation methods, and the implementation methods are not used to limit the protection scope of the embodiments of the present application.
  • a schematic circuit diagram of yet another switching power supply provided by an embodiment of the present application is provided. As shown in FIG.
  • the first switch tube circuit 101 includes: a first switch tube VT1, a second switch tube VT2, a first capacitor C1 and a second capacitor C2; wherein, the first end of the first switch tube VT1 is connected The first end of the first direct current and the first end of the first capacitor C1, the second end of the first switch VT1 is connected to the first end of the second switch VT2 and the N way The first end of the parallel resonant cavity circuit; the second end of the second switching tube VT2 is connected to the second end of the second capacitor C2 and the second end of the first direct current; the first capacitor C1 The second end of is connected to the first end of the second capacitor C2 and the second end of the N-way parallel resonant cavity circuit.
  • the second switch tube circuit 103 includes: a third capacitor C3, a fourth capacitor C4, a seventh switch tube VT7, and an eighth switch tube VT8; wherein, the first end of the third capacitor C3 is connected to the second DC current The first end and the first end of the seventh switch VT7, the second end of the third capacitor C3 is connected to the third end of the N-way parallel resonant cavity circuit and the first end of the fourth capacitor C4 End; the second end of the fourth capacitor C4 is connected to the second end of the second direct current and the second end of the eighth switching tube VT8; the second end of the seventh switching tube VT7 is connected to the The first end of the eighth switching tube VT8 and the fourth end of the N-way parallel resonant cavity circuit.
  • the current of the resonant cavity circuit is divided into N parts, i 1 , i 2 ,..., I N , due to the current It is divided into N parts, so the current stress of the resonant capacitor is greatly reduced, which also reduces the heating of the resonant capacitor. Similarly, the heat of the transformer is also reduced.
  • the first end of the i-th resonance capacitor is connected to the first end of the N-way parallel resonant cavity circuit, and the second end of the i-th resonance capacitor is connected to the first end of the i-th winding coupled to the resonance inductor;
  • the second end of the i-th winding of the coupled resonant inductor is connected to the first end of the primary side of the i-th transformer;
  • the second end of the primary side of the i-th transformer is connected to the second end of the N-way parallel resonant cavity circuit, the i-th transformer
  • the first end of the secondary side is connected to the third end of the N-way parallel resonant cavity circuit, and the second end of the i-th transformer is connected to the fourth end of the N-way parallel resonant cavity circuit.
  • the N-channel resonant cavity circuit of the embodiment of the present application shares a switching tube, and the switching tubes can be connected in parallel, which simplifies the driving circuit of the switching tube;
  • the embodiment of the present application is divided into N-channel resonant cavity circuits, and the current of each resonant cavity circuit is reduced to 1 / N, the line loss is lower, and the heat generation is smaller;
  • the N-way resonant cavity circuit of the present application has N sets of resonant capacitors and transformers, which dissipate heat and facilitate design;
  • the embodiment of the present application implements the resonant cavity circuit based on the coupled resonant inductor, greatly The uneven current of the N-way resonator circuit is reduced.
  • computer storage media includes both volatile and nonvolatile implemented in any method or technology for storing information such as computer readable instructions, data structures, program modules, or other data Sex, removable and non-removable media.
  • Computer storage media include but are not limited to RAM, ROM, EEPROM, flash memory or other memory technologies, CD-ROM, digital versatile disk (DVD) or other optical disk storage, magnetic cartridges, magnetic tape, magnetic disk storage or other magnetic storage devices, or may Any other medium for storing desired information and accessible by a computer.
  • the communication medium generally contains computer readable instructions, data structures, program modules, or other data in a modulated data signal such as a carrier wave or other transmission mechanism, and may include any information delivery medium .
  • Embodiments of the present application include: a first switch tube circuit configured to convert an input first DC current into a first AC current; an N-channel parallel resonant cavity circuit configured to convert a first AC current into a second AC current;
  • the i-th parallel resonant cavity circuit includes an i-th resonant capacitor connected in series, an i-th winding coupled with a resonant inductor, and an i-th transformer.
  • I is an integer greater than or equal to 1 and less than or equal to N, and N is greater than Or an integer equal to 2;
  • the second switch tube circuit is configured to rectify and convert the second alternating current into the second direct current.
  • the embodiment of the present application implements a resonant cavity circuit based on a coupled resonant inductor, and realizes current sharing.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

一种开关电源，包括：第一开关管电路（101），设置为将输入的第一直流电流转换成第一交流电流；N路并联的谐振腔电路（102），设置为将该第一交流电流转换成第二交流电流；其中，第i路并联的谐振腔电路包括串联连接的第 i谐振电容、耦合谐振电感的第i个绕组和第i变压器，i为大于或等于1，且小于或等于 N的整数，N为大于或等于2的整数；第二开关管电路（103），设置为将第二交流电流进行整流转换成第二直流电流。

Description

一种开关电源
本申请要求在2018年11月19日提交中国专利局、申请号为201811374396.0的中国专利申请的优先权，该申请的全部内容通过引用结合在本申请中。
技术领域
本申请实施例涉及但不限于电力电子变换技术，例如一种开关电源。
背景技术
对于大功率开关电源来说，因其功率大，如果采用单个电路拓扑，势必会造成开关管电流应力大，磁件体积大且散热困难，因此，将单个电路拓扑分成多个并联的拓扑，同时让多个电路拓扑实现均流，是一种主要的解决方法。
在并联拓扑里，对采用脉冲频率调制(Pulse Frequency Modulation，PFM)控制的谐振转换电路来说，通过调频方法不容易实现均流，而调占空比又会失去软开关的优点，因此，均流成为谐振转换并联电路的一大难点。
发明内容
本申请实施例提供了一种开关电源，可以实现均流。
本申请实施例提供了一种开关电源，包括：第一开关管电路，设置为将输入的第一直流电流转换成第一交流电流；N路并联的谐振腔电路，设置为将所述第一交流电流转换成第二交流电流；其中，第i路并联的谐振腔电路包括串联连接的第i谐振电容、耦合谐振电感的第i个绕组和第i变压器，i为大于或等于1，且小于或等于N的整数，N为大于或等于2的整数；第二开关管电路，设置为将所述第二交流电流进行整流转换成第二直流电流。
附图说明
图1为本申请一个实施例提出的开关电源的结构示意图；
图2为本申请一实施例提供的耦合谐振电感的示意图；
图3为本申请一实施例提供的非耦合谐振电感实现的开关电源的电路示意图；
图4为本申请一实施例提供的一种开关电源的实现电路的示意图；
图5为本申请一实施例提供的另一种开关电源的实现电路的示意图；
图6为本申请一实施例提供的又一种开关电源的实现电路的示意图。
具体实施方式
在附图的流程图示出的步骤可以在诸如一组计算机可执行指令的计算机系统中执行。并且，虽然在流程图中示出了逻辑顺序，但是在某些情况下，可以以不同于此处的顺序执行所示出或描述的步骤。
参见图1，本申请一个实施例提出了一种开关电源，包括第一开关管电路101、N路并联的谐振腔电路102和第二开关管电路103。
第一开关管电路101，设置为将输入的第一直流电流转换成第一交流电流。
N路并联的谐振腔电路102，设置为将所述第一交流电流转换成第二交流电流；其中，第i路并联的谐振腔电路包括串联连接的第i谐振电容、耦合谐振电感的第i个绕组和第i变压器，i为大于或等于1，且小于或等于N的整数，N为大于或等于2的整数。
第二开关管电路103，设置为将所述第二交流电流进行整流转换成第二直流电流。
在本申请另一个实施例中，如图2所示，耦合谐振电感包括：磁芯和N个绕组，所述N个绕组绕制在所述磁芯的中柱或者边柱上，N个绕组由于电流变化所产生的磁场相互叠加，所述N个绕组的匝数相同。
在本申请实施例中，耦合谐振电感起到均流的作用，在没有耦合谐振电感的情况下，谐振腔将极容易出现不均流，下面进行分析：在谐振电感不耦合的情况下，图3以N为2时为例给出本申请实施例非耦合谐振电感实现的开关电源的电路示意图。如图3所示，在谐振电感1和谐振电感2都没有偏差的情况下，两者电流完全无偏差。实际电路中，元件参数都存在偏差，假设谐振电感1的电感量上偏，谐振电感2的电感量下偏(一般厂家制造误差在±10％)，会存在以下情况：(1)在谐振电感1上偏5％，谐振电感2下偏5％的情况下，i 1和i 2电流偏差在20％左右；(2)在谐振电感1上偏10％，谐振电感2下偏10％(最恶劣情况)的情况下，i 1和i 2电流偏差在40％左右。
可见，随着谐振电感的电感量偏差加大，谐振电流不均流情况也随之更加恶劣。
两个谐振电感耦合在一起之后，产生的结果如下：
(1)两个谐振电感耦合之后，谐振电感之间的电感量偏差大幅减小，不均流度大幅减少，不均流度是表征流过两个谐振电感的电流的差值大小的物理量。
(2)耦合谐振电感结构如图2所示，由于耦合谐振电感的两个绕组方向如上，因此，在电流流向如图2所示的情况下，两个绕组产生的磁通量叠加。在其中一个绕组的电流增加的情况下，比如绕组1的电流i 1增加的时候，绕组2是阻碍此磁通量增加的，因为电感的特性就是阻碍磁路中磁通量变化，因此阻碍了i 1的增加。同理，在i 1减小的情况下，绕组2阻碍了i 1的减小。
下面将详细分析耦合谐振电感的均流原理。
绕组1的电流i 1增加的时候，绕组1产生的磁通量
Figure PCTCN2019119499-appb-000001
增加；其中，L 1为绕组1的自感系数，M为互感系数，i 2为绕组2的电流，那么绕组2产生的磁通量
Figure PCTCN2019119499-appb-000002
小于绕组1产生的磁通量
Figure PCTCN2019119499-appb-000003
其中，L 2为绕组2的自感系数。
绕组1两端的电压为
Figure PCTCN2019119499-appb-000004
绕组2两端的电压为
Figure PCTCN2019119499-appb-000005
假设绕组1和绕组2的匝数相同，那么L 1＝L 2＝L，进而得到
Figure PCTCN2019119499-appb-000006
一般情况下
Figure PCTCN2019119499-appb-000007
对于理想变压器M＝1。
那么由上面的公式可以得出，当i 1＞i 2的时候，由于绕组1和绕组2的开关频率相同，谐振腔电路工作在一区，谐振腔电路电流近似为正弦，在同一时刻，电流大的电流变化率也大，则
Figure PCTCN2019119499-appb-000008
u 1＞u 2。
用u cr1表示第1路谐振腔电路的第一谐振电容的端电压，C cr1为第一谐振电容的电容值，i cr1第1路谐振腔电路的第一谐振电容的电流，u L1表示第1路谐振腔电路的谐振电感两端的电压，i L1表示第1路谐振腔电路的谐振电感的电流，由于第1路谐振腔电路的谐振电感(即耦合谐振电感的第1个绕组)和第一谐振电容串联，因此i cr1等于i L1；用u cr2表示第2路谐振腔电路的第二谐振电容的端电压，C cr2为第二谐电容的电容值，i cr2第2路谐振腔电路的第二谐振电容的电流，i L2表示第2路谐振腔电路的谐振电感的电流，u L2表示第2路谐振腔电路的谐振电感两端的电压，由于第2路谐振腔电路的谐振电感(即耦合谐振电感的第2个绕组)和第二谐振电容串联，因此i cr2等于i L2。假设两个谐振腔电路其它参数相同，谐振电容的电容值不同，由于谐振电容的偏差C cr1<C cr2导致初始时刻i L1＞i L2， 那么根据上面的推导u L1＞u L2。两个谐振腔电路的输入电压相等，假设忽略励磁电感的偏差，输出电压也被钳位的相等，那么，u L1+u cr1＝u L2+u cr2；
那么u cr1＜u cr2，又
Figure PCTCN2019119499-appb-000009
第1路谐振腔电路的第一谐振电容电压和第2路谐振腔电路的第二谐振电容电压是同频同相大小不同的近似正弦，则
Figure PCTCN2019119499-appb-000010
已知C cr1<C cr2，则
Figure PCTCN2019119499-appb-000011
即i cr1小于i cr2。
因此，耦合谐振电感结构对于i cr1有减小的趋势，对于i cr2有增大的趋势，从而抑制第1路谐振腔电路的谐振腔电流，增加第2路谐振腔电路的谐振腔电流，最终形成一个闭环负反馈，使得二者的电流相同。
因此，通过上面的分析可知，耦合谐振电感能减小谐振腔电流的偏差。在本申请另一个实施例中，图4以N为2时为例给出本申请实施例提供的一种开关电源的实现电路示意图，图5以N为3时为例给出本申请实施例提供的另一种开关电源的实现电路示意图。如图4和图5所示，第一开关管电路101包括：第一开关管VT1、第二开关管VT2、第三开关管VT3和第四开关管VT4；其中，所述第一开关管VT1的第一端连接所述第一直流电流的第一端和所述第三开关管VT3的第一端，所述第一开关管VT1的第二端连接所述第二开关管VT2的第一端和所述N路并联的谐振腔电路的第一端；所述第二开关管VT2的第二端连接所述第四开关管VT4的第二端和所述第一直流电流的第二端；所述第三开关管VT3的第二端连接所述第四开关管VT4的第一端和所述N路并联的谐振腔电路的第二端。
所述第二开关管电路103包括：第五开关管VT5、第六开关管VT6、第七开关管VT7和第八开关管VT8；其中，所述第五开关管VT5的第一端连接所述第二直流电流的第一端和所述第七开关管VT7的第一端，所述第五开关管VT5的第二端连接所述N路并联的谐振腔电路的第三端和所述第六开关管VT6的第一端；所述第六开关管VT6的第二端连接所述第二直流电流的第二端和所述第八开关管VT8的第二端；所述第七开关管VT7的第二端连接所述第八开关管VT8的第一端和所述N路并联的谐振腔电路的第四端。
本申请实施例中的第一开关管电路和第二开关管电路还可以采用其他的实现方式，实现方式不用于限定本申请实施例的保护范围，例如，图6以N为2时为例给出本申请实施例提供的又一种开关电源的电路示意图。如图6所示，第一开关管电路101包括：第一开关管VT1、第二开关管VT2、第一电容C1 和第二电容C2；其中，所述第一开关管VT1的第一端连接所述第一直流电流的第一端和所述第一电容C1的第一端，所述第一开关管VT1的第二端连接所述第二开关管VT2的第一端和所述N路并联的谐振腔电路的第一端；所述第二开关管VT2的第二端连接所述第二电容C2的第二端和所述第一直流电流的第二端；所述第一电容C1的第二端连接所述第二电容C2的第一端和所述N路并联的谐振腔电路的第二端。
第二开关管电路103包括：第三电容C3、第四电容C4、第七开关管VT7和第八开关管VT8；其中，所述第三电容C3的第一端连接所述第二直流电流的第一端和所述第七开关管VT7的第一端，所述第三电容C3的第二端连接所述N路并联的谐振腔电路的第三端和所述第四电容C4的第一端；所述第四电容C4的第二端连接所述第二直流电流的第二端和所述第八开关管VT8的第二端；所述第七开关管VT7的第二端连接所述第八开关管VT8的第一端和所述N路并联的谐振腔电路的第四端。
在本申请实施例中，在第一开关管VT1和第四开关管VT4导通的情况下，谐振腔电路的电流分为N部分，分别为i 1，i 2，…，i N，由于电流被分成了为N份，因此大大降低了谐振电容的电流应力，也就减小了谐振电容的发热，同理也降低了变压器的发热。
在本申请实施例中，第i谐振电容的第一端连接N路并联的谐振腔电路的第一端，第i谐振电容的第二端连接耦合谐振电感的第i个绕组的第一端；耦合谐振电感的第i个绕组的第二端连接第i变压器的初级侧的第一端；第i变压器的初级侧的第二端连接N路并联的谐振腔电路的第二端，第i变压器的次级侧的第一端连接N路并联的谐振腔电路的第三端，第i变压器的次级侧的第二端连接N路并联的谐振腔电路的第四端。
本申请实施例的N路谐振腔电路共用开关管，开关管可以并联，简化了开关管的驱动电路；本申请实施例分成了N路谐振腔电路，每路谐振腔电路电流减小为1/N，线路损耗更低，发热更小；本申请实施例N路谐振腔电路内有N组谐振电容和变压器，分散了散热，利于设计；本申请实施例基于耦合谐振电感实现谐振腔电路，大大减小了N路谐振腔电路的不均流度。
本领域普通技术人员可以理解，上文中所公开方法中的全部或某些步骤、系统、装置中的功能模块/单元可以被实施为软件、固件、硬件及其适当的组合。在硬件实施方式中，在以上描述中提及的功能模块/单元之间的划分不一定对应 于物理组件的划分；例如，一个物理组件可以具有多个功能，或者一个功能或步骤可以由若干物理组件合作执行。某些组件或所有组件可以被实施为由处理器，如数字信号处理器或微处理器执行的软件，或者被实施为硬件，或者被实施为集成电路，如专用集成电路。这样的软件可以分布在计算机可读介质上，计算机可读介质可以包括计算机存储介质(或非暂时性介质)和通信介质(或暂时性介质)。如本领域普通技术人员公知的，术语计算机存储介质包括在用于存储信息(诸如计算机可读指令、数据结构、程序模块或其他数据)的任何方法或技术中实施的易失性和非易失性、可移除和不可移除介质。计算机存储介质包括但不限于RAM、ROM、EEPROM、闪存或其他存储器技术、CD-ROM、数字多功能盘(DVD)或其他光盘存储、磁盒、磁带、磁盘存储或其他磁存储装置、或者可以用于存储期望的信息并且可以被计算机访问的任何其他的介质。此外，本领域普通技术人员公知的是，通信介质通常包含计算机可读指令、数据结构、程序模块或者诸如载波或其他传输机制之类的调制数据信号中的其他数据，并且可包括任何信息递送介质。
本申请实施例包括：第一开关管电路，设置为将输入的第一直流电流转换成第一交流电流；N路并联的谐振腔电路，设置为将第一交流电流转换成第二交流电流；其中，第i路并联的谐振腔电路包括串联连接的第i谐振电容、耦合谐振电感的第i个绕组和第i变压器，i为大于或等于1，且小于或等于N的整数，N为大于或等于2的整数；第二开关管电路，设置为将第二交流电流进行整流转换成第二直流电流。本申请实施例基于耦合谐振电感实现谐振腔电路，实现了均流。

Claims (6)

  1. 一种开关电源，包括：
    第一开关管电路，设置为将输入的第一直流电流转换成第一交流电流；
    N路并联的谐振腔电路，设置为将所述第一交流电流转换成第二交流电流；
    其中，第i路并联的谐振腔电路包括串联连接的第i谐振电容、耦合谐振电感的第i个绕组和第i变压器，i为大于或等于1，且小于或等于N的整数，N为大于或等于2的整数；
    第二开关管电路，设置为将所述第二交流电流进行整流，以转换成第二直流电流。
  2. 根据权利要求1所述的开关电源，其中，所述耦合谐振电感包括：一个磁芯和N个绕组；所述N个绕组绕制在所述磁芯的中柱或者边柱上，所述N个绕组由于电流变化所产生的磁场相互叠加，所述N个绕组的匝数相同。
  3. 根据权利要求1所述的开关电源，其中，所述第一开关管电路包括：第一开关管、第二开关管、第三开关管和第四开关管；
    所述第一开关管的第一端连接所述第一直流电流的第一端和所述第三开关管的第一端，所述第一开关管的第二端连接所述第二开关管的第一端和所述N路并联的谐振腔电路的第一端；
    所述第二开关管的第二端连接所述第四开关管的第二端和所述第一直流电流的第二端；
    所述第三开关管的第二端连接所述第四开关管的第一端和所述N路并联的谐振腔电路的第二端。
  4. 根据权利要求1所述的开关电源，其中，所述第一开关管电路包括：第一开关管、第二开关管、第一电容和第二电容；
    所述第一开关管的第一端连接所述第一直流电流的第一端和所述第一电容的第一端，所述第一开关管的第二端连接所述第二开关管的第一端和所述N路并联的谐振腔电路的第一端；
    所述第二开关管的第二端连接所述第二电容的第二端和所述第一直流电流的第二端；
    所述第一电容的第二端连接所述第二电容的第一端和所述N路并联的谐振腔电路的第二端。
  5. 根据权利要求1所述的开关电源，其中，所述第二开关管电路包括：第五开关管、第六开关管、第七开关管和第八开关管；
    所述第五开关管的第一端连接所述第二直流电流的第一端和所述第七开关管的第一端，所述第五开关管的第二端连接所述N路并联的谐振腔电路的第三端和所述第六开关管的第一端；
    所述第六开关管的第二端连接所述第二直流电流的第二端和所述第八开关管的第二端；
    所述第七开关管的第二端连接所述第八开关管的第一端和所述N路并联的谐振腔电路的第四端。
  6. 根据权利要求1所述的开关电源，其中，所述第二开关管电路包括：第三电容、第四电容、第七开关管和第八开关管；
    所述第三电容的第一端连接所述第二直流电流的第一端和所述第七开关管的第一端，所述第三电容的第二端连接所述N路并联的谐振腔电路的第三端和所述第四电容的第一端；
    所述第四电容的第二端连接所述第二直流电流的第二端和所述第八开关管的第二端；
    所述第七开关管的第二端连接所述第八开关管的第一端和所述N路并联的谐振腔电路的第四端。
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