WO2019208008A1 - Dispositif de conversion de puissance - Google Patents

Dispositif de conversion de puissance Download PDF

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Publication number
WO2019208008A1
WO2019208008A1 PCT/JP2019/010462 JP2019010462W WO2019208008A1 WO 2019208008 A1 WO2019208008 A1 WO 2019208008A1 JP 2019010462 W JP2019010462 W JP 2019010462W WO 2019208008 A1 WO2019208008 A1 WO 2019208008A1
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Prior art keywords
switching circuit
circuit
output
input
power
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PCT/JP2019/010462
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English (en)
Japanese (ja)
Inventor
信太朗 田中
大内　貴之
裕二 曽部
琢磨 小野
高橋　直也
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日立オートモティブシステムズ株式会社
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Publication of WO2019208008A1 publication Critical patent/WO2019208008A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac

Definitions

  • the present invention relates to a power conversion device.
  • An automobile that travels using such electric energy is provided with a high-voltage battery that supplies electric power to a motor for driving wheels.
  • a power conversion device that steps down the output power from the high-voltage battery and supplies the necessary power to low-voltage electric devices mounted on the automobile, such as air conditioners and audio, various ECUs (Electronic Control Units), etc., is provided.
  • Such a power converter converts input DC power into DC power of a different voltage, and is also called a DC-DC converter.
  • a DC-DC converter has a switching circuit capable of switching operation, and performs voltage conversion of DC power by controlling on / off of the switching circuit. Specifically, the input DC power is temporarily converted into AC power using a switching circuit, and the AC power is transformed (stepped up or stepped down) using a transformer. Then, the transformed AC power is converted into DC power again using an output circuit such as a rectifier circuit. As a result, a DC output having a voltage different from the input voltage can be obtained.
  • the switching circuit is configured by using a semiconductor switch element such as a MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor) and an IGBT (Insulated Gate Bipolar Transistor).
  • MOSFET Metal-Oxide-Semiconductor Field-Effect Transistor
  • IGBT Insulated Gate Bipolar Transistor
  • the loss generated in the DC-DC converter includes a switching loss generated by a switching operation, a resistance loss (copper loss) generated in a transformer and a semiconductor switch element, and the like.
  • the following patent document 1 is known regarding high efficiency of a power converter.
  • the switching timing of the two synchronous rectification switches of the rectifying / smoothing circuit is controlled based on the output current, and stored in the rectifying / smoothing circuit so as to act equivalent to the increase in the output current at light load.
  • a power supply device that performs zero volt switching by returning the energy returned to the full bridge circuit and increasing the current flowing through the full bridge circuit is disclosed.
  • Patent Document 1 requires a current detector that detects an output current, and thus has a problem of increasing the size and cost as compared with a conventional power converter.
  • the power conversion device includes an input switching circuit that converts first DC power input from an input power source into AC power, a transformer that performs voltage conversion of the AC power, and the AC that is voltage-converted by the transformer.
  • An output switching circuit that converts electric power into second DC power and outputs the output; a control circuit that controls the input switching circuit and the output switching circuit; a reactor component provided between the input switching circuit and the transformer;
  • the input switching circuit includes a pair of input switch elements connected in series between the positive and negative electrodes of the input power source and controlled to be switched by the control circuit, and the output switching circuit is controlled by the control circuit.
  • An output switch element that is switching-controlled, and in parallel with the output switch element A snubber circuit provided, and the control circuit supplies a current to the snubber circuit in a circulation period in which a circulation current circulating through the input switching circuit, the reactor component, and the transformer flows without passing through the input power supply.
  • the input switching circuit is controlled so that the circulating current increases due to the current flowing, and the input switching circuit is shifted to a dead time period in which both of the pair of input switch elements are off after the circulating period. Control the circuit.
  • FIG. 3 is a timing chart showing how the voltage and current of each part change with time during the operation of the DC-DC converter according to the first embodiment of the present invention. It is a figure which shows the switching state and direction of an electric current of each switch element in period # 1 of the DC-DC converter which concerns on the 1st Embodiment of this invention. It is a figure which shows the switching state of each switch element, and direction of an electric current in period # 2 of the DC-DC converter which concerns on the 1st Embodiment of this invention.
  • FIG. 1 is a diagram showing a configuration of a vehicle power source according to an embodiment of the present invention.
  • the vehicle power source according to the present embodiment is mounted on a vehicle 1000 and uses a DC-DC converter 100 to perform power conversion between the high voltage battery V1 and the low voltage battery V2. It is a system.
  • the low-voltage side of the DC-DC converter 100 that is, the side connected to the low-voltage battery V2 is referred to as “L side”, and is connected to the high-voltage side of the DC-DC converter 100, ie, the high-voltage battery V1.
  • the side that is on is called the “H side”.
  • One end of the low voltage battery V2 is connected to one end on the L side of the DC-DC converter 100, and the other end of the low voltage battery V2 is connected to the other end on the L side of the DC-DC converter 100.
  • One end of the auxiliary equipment 400 such as an air conditioner is connected to one end on the L side of the DC-DC converter 100 and one end of the low-voltage battery V2, and the other end of the auxiliary equipment 400 is connected to the other side on the L side of the DC-DC converter 100.
  • One end and the other end of the low-voltage battery V2 are connected.
  • One end of the HV system device 300 is connected to one end on the H side of the DC-DC converter 100 and one end of the high voltage battery V1, and the other end of the HV system device 300 is connected to the other end on the H side of the DC-DC converter 100 and the high voltage.
  • the other end of the battery V1 is connected.
  • One end of the high voltage battery V1 is connected to one end on the H side of the DC-DC converter 100, and the other end of the high voltage battery V1 is connected to the other end on the H side of the DC-DC converter 100.
  • the DC-DC converter 100, the HV system device 300, and the auxiliary device 400 are connected to the vehicle power supply control unit 200.
  • the vehicle power supply control unit 200 controls the operation of these devices, the power transmission direction of the power exchanged between these devices and the high voltage battery V1 and the low voltage battery V2, the amount of power, and the like.
  • FIG. 2 is a diagram showing a basic circuit configuration of the DC-DC converter 100 according to the first embodiment of the present invention.
  • the DC-DC converter 100 of this embodiment includes an input switching circuit 10, a transformer 20, an output switching circuit 30, a voltage detector 41, a control circuit 50, and gate drivers 60 and 61. .
  • the input switching circuit 10 is connected via a positive input terminal 1 and a negative input terminal 2 to a high voltage battery V1 that acts as an input power source for the DC-DC converter 100.
  • the input switching circuit 10 includes switch elements 11a to 14a connected in a bridge. By switching the switch elements 11a to 14a, the DC power input from the high voltage battery V1 is changed to high frequency AC power. Converted and output to the primary side of the transformer 20.
  • the transformer 20 insulates the primary side from the secondary side, performs voltage conversion of AC power between the primary side and the secondary side, and steps down (or boosts) the AC power generated by the input switching circuit 10. The AC power thus output is output to the output switching circuit 30.
  • the output switching circuit 30 is connected to the low voltage battery V ⁇ b> 2 through the positive output terminal 3 and the negative output terminal 4.
  • the output switching circuit 30 includes switch elements 31a and 32a and snubber circuits 33 and 34 that are provided in parallel to the switch elements 31a and 32a and protect the switch elements 31a and 32a.
  • the output switching circuit 30 rectifies the AC power voltage-converted by the transformer 20 using the switch elements 31a and 32a, converts it into DC power, and outputs the DC power to the low-voltage battery V2.
  • the voltage detector 41 detects the output voltage of the output switching circuit 30 by detecting the voltage between the positive electrode output terminal 3 and the negative electrode output terminal 4. The output voltage detected by the voltage detector 41 is input to the control circuit 50.
  • the control circuit 50 is provided, for example, in the vehicle power supply control unit 200 of FIG. 1, and controls the switching operations of the switch elements 11a to 14a in the input switching circuit 10 based on the output voltage detected by the voltage detector 41, respectively. Output signals 51 to 54 are generated and output. Further, based on the output voltage detected by the voltage detector 41, output signals 55 to 56 for controlling the switching operations of the switch elements 31a and 32a in the output switching circuit 30 are generated and output.
  • the gate driver 60 converts the output signals 51 to 54 output from the control circuit 50 into drive signals 71 to 74 for driving the switch elements 11a to 14a, respectively, and outputs them to the input switching circuit 10.
  • the gate driver 60 insulates between the input switching circuit 10 and the control circuit 50.
  • the gate driver 61 converts the output signals 55 to 56 output from the control circuit 50 into drive signals 75 and 76 for driving the switch elements 31a and 32a, respectively, and outputs them to the output switching circuit 30.
  • the gate driver 61 insulates between the output switching circuit 30 and the control circuit 50.
  • the input switching circuit 10 converts DC power input from the high-voltage battery V ⁇ b> 1 through the positive input terminal 1 and the negative input terminal 2 into high-frequency AC power according to the control of the control circuit 50, and the primary winding of the transformer 20. It has a role to supply to the line N1.
  • a smoothing capacitor C1 is connected between the positive input terminal 1 and the negative input terminal 2 in parallel with the high voltage battery V1.
  • the input switching circuit 10 has a configuration in which four switch elements 11a to 14a are connected in a full bridge. That is, between the positive input terminal 1 and the negative input terminal 2, a series circuit of two switch elements 11a and 12a (hereinafter referred to as “first leg”), two switch elements 13a and 14a. A series circuit (hereinafter referred to as “second leg”) is connected to each other. A connection point A between the switch element 11a and the switch element 12a in the first leg is connected to one end side of the primary winding N1 of the transformer 20, and a connection between the switch element 13a and the switch element 14a in the second leg. Point B is connected to the other end of primary winding N1 of transformer 20.
  • the switch elements 11a to 14a can be configured by using any element capable of switching operation, and for example, an FET (field effect transistor) or the like is preferable.
  • the switch elements 11a to 14a are connected in parallel with flywheel diodes 11b to 14b and capacitors 11c to 14c, respectively. These diodes 11b to 14b and capacitors 11c to 14c may be configured as separate elements from the switch elements 11a to 14a, or may be parasitic components of the switch elements 11a to 14a. These may be used in combination.
  • a phase shift control method that is a drive method capable of reducing switching loss is used as a control method of the input switching circuit 10.
  • the switch element 11a on the upper side of the first leg and the switch element 14a on the lower side of the second leg Is controlled in accordance with the output voltage of the DC-DC converter 100.
  • the on / off phase difference between the switch element 12a below the first leg and the switch element 13a above the second leg is also controlled according to the output voltage of the DC-DC converter 100.
  • the period during which the switch element 11a and the switch element 14a are simultaneously turned on and the period during which the switch element 12a and the switch element 13a are simultaneously turned on are adjusted according to the output voltage.
  • the power transmitted from the input switching circuit 10 (primary side of the transformer 20) to the output switching circuit 30 (secondary side of the transformer 20) is a period during which the switch element 11a and the switch element 14a are simultaneously turned on
  • the switching element 12a and the switching element 13a are determined by a period during which the switching element 12a is turned on at the same time. Therefore, by controlling the phase difference as described above, the output voltage of the DC-DC converter 100 can be stabilized at a desired value.
  • the period in which the switch element 11a and the switch element 14a are simultaneously turned on and the period in which the switch element 12a and the switch element 13a are simultaneously turned on have the same length. Further, the ratio of the lengths of these periods in one cycle may be referred to as a duty ratio.
  • the transformer 20 has a role of performing voltage conversion on the AC power generated by the input switching circuit 10 and outputting the AC power after voltage conversion to the output switching circuit 30.
  • the transformer 20 includes a primary winding N1 connected to the input switching circuit 10 and a secondary winding N2 connected to the output switching circuit 30.
  • the transformer 20 has a center tap configuration in order to realize a full-wave rectifier circuit in combination with the output switching circuit 30, and the secondary winding N2 is divided into two secondary windings N2a and N2b in the middle. Has been.
  • the turn ratio (N1 / N2a or N1 / N2b) between the primary winding N1 and the secondary windings N2a and N2b is a voltage range of the input voltage Vin applied between the positive input terminal 1 and the negative input terminal 2, and It is set according to the voltage range of the output voltage Vout to be supplied between the positive electrode output terminal 3 and the negative electrode output terminal 4.
  • the transformer 20 has a predetermined leakage inductance in series with the primary winding N1, and this leakage inductance acts as a reactor component L1 for resonance.
  • the value of the leakage inductance in the transformer 20 is small, the value of the reactor component L1 may be increased by connecting an inductor by another reactor element in series with the primary winding N1. That is, the reactor component L1 provided between the input switching circuit 10 and the transformer 20 has at least one of the leakage inductance of the transformer 20 and the reactor element connected between the input switching circuit 10 and the transformer 20. Constructed using.
  • connection point A which is the midpoint of the first leg in the input switching circuit 10, via a reactor component L1.
  • the other end of the primary winding N ⁇ b> 1 is connected to a connection point B that is a midpoint of the second leg in the input switching circuit 10.
  • a neutral point T which is a connection point between the secondary winding N2a and the secondary winding N2b, is connected to the output switching circuit 30 together with both ends of the secondary winding N2.
  • the output switching circuit 30 converts the AC power appearing in the secondary windings N2a and N2b into DC power by smoothing and rectifying the AC power that flows in the primary winding N1 of the transformer 20 to the positive output terminal 3 and the negative electrode It has a role of outputting to the low voltage battery V2 via the output terminal 4.
  • a voltage detector 41 is connected between the positive electrode output terminal 3 and the negative electrode output terminal 4 in parallel with the low voltage battery V2. The voltage detector 41 detects the voltage of the DC power output from the output switching circuit 30 and outputs the detected value to the control circuit 50 as the output voltage Vout of the DC-DC converter 100.
  • the output switching circuit 30 has a configuration in which two switch elements 31a and 32a are connected between the transformer 20 and the rectifying connection point S.
  • the switch element 31a is connected between one end of the secondary winding N2b of the transformer 20 and the rectification connection point S.
  • the switch element 32a is connected between one end of the secondary winding N2a of the transformer 20 and the rectification connection point S. It is connected to the.
  • Snubber circuits 33 and 34 are connected in parallel to the switch elements 31a and 32a, respectively.
  • the switch elements 31a and 32a can be configured by using any element capable of switching operation like the switch elements 11a to 14a in the input switching circuit 10, for example, an FET (field effect transistor) is preferable. It is.
  • the flywheel diodes 31b and 32b and capacitors 31c and 32c are connected in parallel to the switch elements 31a and 32a, respectively. These diodes 31b and 32b and capacitors 31c and 32c may be configured as separate elements from the switch elements 31a and 32a, or may be parasitic components of the switch elements 31a and 32a. These may be used in combination.
  • a smoothing coil L2 and a smoothing capacitor C2 are connected to the output side of the output switching circuit 30.
  • the smoothing coil L2 is connected between the neutral point T and the positive electrode output terminal 3, and the smoothing capacitor C2 is connected between the positive electrode output terminal 3 and the negative electrode output terminal 4.
  • the switch elements 31a and 32a constitute a rectifier circuit that rectifies and converts the AC power output from the secondary windings N2b and N2a of the transformer 20 into DC power, respectively.
  • the smoothing coil L2 and the smoothing capacitor C2 constitute a smoothing circuit that smoothes the rectified output generated at the neutral point T.
  • the control circuit 50 is a circuit that controls the operation of the switch elements 11a to 14a of the input switching circuit 10 so that the output voltage Vout of the DC-DC converter 100 becomes a predetermined voltage target value.
  • the control circuit 50 generates output signals 51 to 54 for controlling the switch elements 11a to 14a of the input switching circuit 10 based on the output voltage Vout.
  • Output signals 51 to 54 generated by the control circuit 50 are output from the control circuit 50 to the gate driver 60 and converted into drive signals 71 to 74 by the gate driver 60, respectively.
  • the drive signals 71 to 74 are input to the respective gate terminals of the switch elements 11a to 14a in the input switching circuit 10 to drive the switch elements 11a to 14a, respectively. Thereby, the operation of the input switching circuit 10 is controlled by the control circuit 50.
  • control circuit 50 generates output signals 55 and 56 for controlling the switch elements 31a and 32a of the output switching circuit 30 based on the output voltage Vout.
  • Output signals 55 and 56 generated by the control circuit 50 are output from the control circuit 50 to the gate driver 61 and converted into drive signals 75 and 76 by the gate driver 61, respectively.
  • the drive signals 75 and 76 are input to the respective gate terminals of the switch elements 31a and 32a in the output switching circuit 30, and drive the switch elements 31a and 32a, respectively. Thereby, the operation of the output switching circuit 30 is controlled by the control circuit 50.
  • FIG. 3 is a timing chart showing how the voltage and current of each part change with time during the operation of the DC-DC converter 100 according to the first embodiment of the present invention.
  • FIGS. 4 to 9 show the switching state of each switch element at the time of operation
  • 4 to 9 correspond to periods # 1 to # 6 of the timing chart shown in FIG. 3, respectively. That is, FIGS. 4 to 9 show the on / off states of the switch elements 11a to 14a, 31a and 32a in the DC-DC converter 100 in the periods # 1 to # 6 of FIG.
  • the input switching circuit 10 the transformer 20 and the output.
  • the direction of the current flowing through the switching circuit 30 is shown.
  • the control circuit 50 controls the switching elements 11a to 14a of the input switching circuit 10 and the switching elements 31a and 32a of the output switching circuit 30 to switch the period # The transition from 1 to # 6 can be controlled.
  • voltage waveforms Vg_11a to Vg_14a represent temporal changes in the gate voltage of the switch elements 11a to 14a in the input switching circuit 10, respectively, and voltage waveform Vg_31a represents a temporal change in the gate voltage of the switch element 31a in the output switching circuit 30.
  • the current waveform I_L1 represents the time change of the current flowing through the reactor component L1 and the primary winding N1
  • the current waveforms I_N2a and I_N2b represent the time change of the current flowing through the secondary windings N2a and N2b of the transformer 20, respectively.
  • the direction of the current from the connection point A to the connection point B in FIG. 2 is positive.
  • FIG. 3 shows how each voltage and each current changes with time when the current waveform I_L1 of the reactor component L1 is negative.
  • the operation state of the DC-DC converter 100 in the periods # 1 to # 6 will be described with reference to FIGS. 4 to 9, respectively.
  • the direction of the current flowing through the secondary winding N2b is positive as shown by the arrow in FIG. It is preferable that the current polarity of the secondary winding N2b is reversed when the current flowing through the winding N2a exceeds a certain value. This point will be described in detail later in the description of the period # 2.
  • the switch elements 31a and 32a of the output switching circuit 30 are maintained in the ON state. Therefore, as indicated by an arrow in FIG. 5, a current flows in order from the transformer 20 to the smoothing coil L2, a load (not shown) connected in parallel with the smoothing capacitor C2, and the switching element 32a of the output switching circuit 30. Energy is stored in L2.
  • the direction of the current flowing through the secondary winding N2b via the switch element 31a changes according to the magnitude of the current flowing through the load. Specifically, when the negative overcurrent is large, the direction of the current flowing through the secondary winding N2b is the positive direction, that is, the direction opposite to the direction indicated by the arrow in FIG.
  • the current polarity is reversed, and the direction of the current flowing through the secondary winding N2b is the negative direction, that is, the direction indicated by the arrow in FIG.
  • the direction of the current flowing through the secondary winding N2b is reversed in the middle of the period # 1, and this state is continued even in the period # 2.
  • a resonance voltage is generated so that a current flows through the snubber circuit 33 as will be described later, and the circulating current in the input switching circuit 10 can be increased.
  • the current waveform I_N2a of the secondary winding N2a decreases, and the current waveform I_N2b of the secondary winding N2b increases in the negative direction.
  • Period # 3 Circulation period
  • the switch elements 11a and 13a are in the on state, and the switch elements 12a and 14a are in the off state.
  • the switch element 32a is maintained in the on state, and the switch element 31a is changed from the on state to the off state.
  • the switch element 31a transitions to the off state, the current flowing through the switch element 31a is cut off, and the current flows through the snubber circuit 33 connected in parallel with the switch element 31a.
  • a resonance voltage is generated by the secondary winding N2b of the transformer 20 and the snubber circuit 33.
  • the switch elements 11a and 13a are in the on state and the switch elements 12a and 14a are in the off state.
  • a circulating current that circulates through the input switching circuit 10, the reactor component L1, and the transformer 20 flows without passing through the high-voltage battery V1.
  • the resonance voltage generated by the secondary winding N2b of the transformer 20 and the snubber circuit 33 is applied from the output switching circuit 30 to the input switching circuit 10 via the transformer 20. This voltage increases the circulating current in the input switching circuit 10.
  • Period # 4 Dead time period
  • the switch element 13a is maintained in the on state, and the switch elements 12a and 14a are maintained in the off state, while the switch element 11a is in the on state. Transition from state to off state. Thereby, in a 1st leg, both a pair of switch element 11a and switch element 12a will be in an OFF state. Therefore, this period is called a dead time period.
  • the reactor component L1 keeps flowing current, so that the capacitor 11c connected in parallel to the switch element 11a is charged and the switch element 12a is charged as shown by the arrow in FIG.
  • the capacitor 12c connected in parallel is discharged.
  • the switch element 32a of the output switching circuit 30 is maintained in the on state, and the switch element 31a is maintained in the off state.
  • the polarity of the current flowing through the secondary winding N2b of the transformer 20 and the snubber circuit 33 is reversed at a predetermined timing according to the above-described resonance voltage. Note that the polarity of the current may be reversed not in the period # 4 but in a period # 5 or a period # 6 described later.
  • the operation of the DC-DC converter 100 after the period # 6 is an operation obtained by inverting the operation during the above-described periods # 1 to # 6. That is, the operation of each switching element in the input switching circuit 10 and the output switching circuit 30 and the direction of the current flowing through the input switching circuit 10 and the output switching circuit 30 in accordance with this operation are the periods # 1 to # 6 described above. The opposite is true for each. Specifically, in the input switching circuit 10, when the switch elements 11a and 14a are in the off state and the switch element 13a is in the on state, the switch element 12a is changed from the on state to the off state, and the period # 2, A circulation period similar to # 3 can be provided.
  • the switch elements 14a are connected in parallel as in the period # 4. It is possible to increase the amount of decrease in the voltage across the capacitor 14c. As a result, zero volt switching is also possible for the switch element 14a.
  • a DC-DC converter 100 that is a power converter includes an input switching circuit 10 that converts DC power input from a high-voltage battery V1 that is an input power source into AC power, and a transformer 20 that performs voltage conversion of AC power. , An output switching circuit 30 that converts the AC power voltage-converted by the transformer 20 into DC power and outputs it, a control circuit 50 that controls the input switching circuit 10 and the output switching circuit 30, and the input switching circuit 10 and the transformer 20. And a reactor component L1 provided therebetween.
  • the input switching circuit 10 includes a pair of switch elements 11a and 12a, and 13a and 14a that are connected in series between the positive and negative electrodes of the high-voltage battery V1 and controlled to be switched by the control circuit 50, respectively.
  • the output switching circuit 30 includes switch elements 31a and 32a that are controlled by the control circuit 50, and snubber circuits 33 and 34 provided in parallel with the switch elements 31a and 32a.
  • the control circuit 50 increases the circulating current by flowing the current to the snubber circuit 33 in the circulation period # 3 in which the circulating current that circulates through the input switching circuit 10, the reactor component L1, and the transformer 20 without passing through the high-voltage battery V1.
  • the output switching circuit 30 is controlled.
  • the control circuit 50 controls the input switching circuit 10 so as to shift to the dead time period # 4 in which both the pair of switch elements 11a and 12a are off after the circulation period # 3.
  • the DC-DC converter 100 can realize zero-volt switching of the input switching circuit 10 without reducing the output loss without detecting the output current. Therefore, it is possible to increase the efficiency of the DC-DC converter 100 that is a power conversion device while suppressing an increase in size and cost.
  • the reactor component L1 is configured using at least one of the leakage inductance of the transformer 20 and the reactor element connected between the input switching circuit 10 and the transformer 20. Since it did in this way, the reactor component L1 which has an optimal inductance according to the circuit characteristic of the input switching circuit 10 or the transformer 20 can be provided.
  • FIG. 10 is a diagram showing a basic circuit configuration of a DC-DC converter 100a according to the second embodiment of the present invention.
  • the DC-DC converter 100a of the present embodiment has a delay circuit between the control circuit 50 and the gate driver 60, as compared with the DC-DC converter 100 of FIG. 2 described in the first embodiment. The difference is that 90 is further provided.
  • FIG. 11 is a diagram illustrating an example of the delay circuit 90.
  • a delay circuit 90 shown in FIG. 11 is an example of an RC delay circuit configured using a resistor and a capacitor. Note that the delay circuit 90 is not limited to that shown in FIG. 11, and can have any circuit configuration. It goes without saying that the same effect can be obtained with any delay circuit 90 as long as the output signals 51 to 54 can be delayed by a desired timing.
  • the control circuit 50 outputs the output signals 51 to 54 to the input switching circuit 10 and the output signals 55 to 56 to the output switching circuit 30 in synchronization with each other.
  • the output signals 51 to 54 are delayed by the delay circuit 90, so that the switch element 11a of the input switching circuit 10 is turned off with respect to the switch element 31a of the output switching circuit 30 as described in the first embodiment.
  • the timing can be delayed.
  • a resonance voltage can be generated by the secondary winding N2b of the transformer 20 and the snubber circuit 33, and the circulating current in the input switching circuit 10 can be increased.
  • the off timing of the switch element 13a of the input switching circuit 10 can be delayed with respect to the switch element 32a of the output switching circuit 30, the resonance voltage is generated by the secondary winding N2a of the transformer 20 and the snubber circuit 34. And the circulating current in the input switching circuit 10 can be increased.
  • the DC-DC converter 100 a that is a power converter includes a delay circuit 90 provided between the control circuit 50 and the input switching circuit 10.
  • the control circuit 50 outputs output signals 51 to 54 for controlling the input switching circuit 10 and output signals 55 to 56 for controlling the output switching circuit 30 in synchronization with each other.
  • the delay circuit 90 delays the output signals 51 to 54 and outputs them to the input switching circuit 10 via the gate driver 60. Since it did in this way, it becomes possible to increase the circulating current in the input switching circuit 10 easily, without requiring special control in the control circuit 50.
  • the input switching circuit 10 that is a voltage-type full bridge circuit constituted by four switch elements 11a to 14a and the transformer 20 that is a current-type center tap circuit are combined.
  • the present invention has been described using the example of the control circuit 50 that controls the configured DC-DC converters 100 and 100a by the phase shift control method, the present invention is not limited to this.
  • An input switching circuit that converts input first DC power into AC power, a transformer that performs voltage conversion of AC power, and an output that converts AC power voltage-converted by the transformer into second DC power and outputs it If it is a power converter device which has a switching circuit, this invention can be applied and there can exist an effect similar to having demonstrated in each embodiment.
  • each embodiment described above may be applied individually or in any combination.
  • DC-DC converter 200 ... Vehicle power supply control unit, 300 ... HV system equipment, 400 ... Auxiliary equipment, 1000 ... vehicle, N1 ... primary winding, N2a, N2b ... secondary winding, S ... rectifying connection point, T ... neutral point, V1 ... high voltage battery , V2 ... low-voltage battery

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  • Dc-Dc Converters (AREA)

Abstract

La présente invention permet d'obtenir un rendement élevé d'un dispositif de conversion de puissance tout en supprimant l'augmentation de taille et de coût. Dans un convertisseur CC-CC (100), un circuit de commande (50) commande un circuit de commutation de sortie (30) de sorte que le courant circule à travers un circuit d'amortissement (33) dans une période de circulation pendant laquelle circule un courant circulant qui circule à travers un circuit de commutation d'entrée (10), un composant de réacteur (L1), et un transformateur (20) sans passer par une batterie haute tension (V1), et ainsi le courant de circulation augmente. Le circuit de commande (50) amener également le circuit de commutation d'entrée (10) à passer, après la période de circulation, à une période de temps mort durant laquelle une paire d'éléments de commutation (11a, 12a) sont tous deux éteints.
PCT/JP2019/010462 2018-04-27 2019-03-14 Dispositif de conversion de puissance WO2019208008A1 (fr)

Applications Claiming Priority (2)

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JP2018-086836 2018-04-27
JP2018086836A JP2019193514A (ja) 2018-04-27 2018-04-27 電力変換装置

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Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2007006653A (ja) * 2005-06-24 2007-01-11 Hitachi Ltd 絶縁共振形双方向ｄｃ／ｄｃコンバータ及びその制御方法
US20110317452A1 (en) * 2010-06-25 2011-12-29 Gueorgui Iordanov Anguelov Bi-directional power converter with regulated output and soft switching
JP2015154506A (ja) * 2014-02-10 2015-08-24 オリジン電気株式会社 Ｄｃ−ｄｃコンバータ
JP2017175793A (ja) * 2016-03-24 2017-09-28 株式会社デンソー Ｄｃ−ｄｃコンバータ

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2007006653A (ja) * 2005-06-24 2007-01-11 Hitachi Ltd 絶縁共振形双方向ｄｃ／ｄｃコンバータ及びその制御方法
US20110317452A1 (en) * 2010-06-25 2011-12-29 Gueorgui Iordanov Anguelov Bi-directional power converter with regulated output and soft switching
JP2015154506A (ja) * 2014-02-10 2015-08-24 オリジン電気株式会社 Ｄｃ−ｄｃコンバータ
JP2017175793A (ja) * 2016-03-24 2017-09-28 株式会社デンソー Ｄｃ−ｄｃコンバータ

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