WO2019077689A1 - 空気調和機 - Google Patents

空気調和機 Download PDF

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Publication number
WO2019077689A1
WO2019077689A1 PCT/JP2017/037609 JP2017037609W WO2019077689A1 WO 2019077689 A1 WO2019077689 A1 WO 2019077689A1 JP 2017037609 W JP2017037609 W JP 2017037609W WO 2019077689 A1 WO2019077689 A1 WO 2019077689A1
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WIPO (PCT)
Prior art keywords
pulse
control unit
current
power conversion
motor
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Application number
PCT/JP2017/037609
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English (en)
French (fr)
Japanese (ja)
Inventor
洋寿 小倉
田村　建司
貴宏 磯田
正博 田村
Original Assignee
日立ジョンソンコントロールズ空調株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
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Application filed by 日立ジョンソンコントロールズ空調株式会社 filed Critical 日立ジョンソンコントロールズ空調株式会社
Priority to CN201780003344.XA priority Critical patent/CN110326210B/zh
Priority to JP2018511291A priority patent/JP6364573B1/ja
Priority to PCT/JP2017/037609 priority patent/WO2019077689A1/ja
Priority to TW106146220A priority patent/TWI643444B/zh
Publication of WO2019077689A1 publication Critical patent/WO2019077689A1/ja

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    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F24—HEATING; RANGES; VENTILATING
    • F24F—AIR-CONDITIONING; AIR-HUMIDIFICATION; VENTILATION; USE OF AIR CURRENTS FOR SCREENING
    • F24F11/00—Control or safety arrangements
    • F24F11/88—Electrical aspects, e.g. circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/22—Current control, e.g. using a current control loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/24—Vector control not involving the use of rotor position or rotor speed sensors
    • H02P21/26—Rotor flux based control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors
    • H02P7/06—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current
    • H02P7/18—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power
    • H02P7/24—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices
    • H02P7/28—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices
    • H02P7/285—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only
    • H02P7/29—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only using pulse modulation

Definitions

  • the present invention relates to an air conditioner.
  • Patent Document 1 reduces the switching loss during PWM control by stopping the PWM output for a certain period based on the motor current phase during motor drive.
  • the invention described in Patent Document 1 is limited to a specific condition (lower than rotational speed / lower than average motor current), and is not a technology that can achieve high efficiency in a wide range.
  • this invention makes it a subject to provide the air conditioner which enables reduction of the switching loss accompanying a motor drive, and reduction of a motor copper loss, avoiding deterioration of a motor vibration and a motor stop.
  • an air conditioner of the present invention is provided with an electric motor and a power converter which performs electric power conversion for driving the electric motor by PWM control using a vector control system.
  • the power converter includes a pulse control unit that outputs a pulse signal for performing the PWM control, and a switch element having a three-phase configuration, and uses the pulse signal output from the pulse control unit.
  • Power control circuit for converting direct current power to alternating current power, current detection unit for detecting current flowing in the power conversion circuit, and vector control based on current detected by the current detection unit, to the pulse control unit
  • the pulse is generated in a section determined on the basis of the current phase of the power conversion circuit in order to stop the vector control unit generating the command voltage and the positive and negative switch elements of the predetermined phase of the power conversion circuit.
  • a pulse stop control unit for generating a pulse stop control signal for stopping the signal and outputting the pulse stop control signal to the pulse control unit.
  • the vector control unit starts the operation of the pulse stop control unit if the motor current of the motor is within a predetermined range with respect to the motor current at no load of the current rotational speed.
  • FIG. 7 is a waveform diagram showing a relationship between an AC voltage, an AC current, and a pulse signal flowing through the motor during intermittent energization operation and a phase pulse stop control signal. It is a wave form diagram showing the relation of U phase voltage, U phase current, and a pulse signal at the time of driving an actual machine provided with a power conversion device.
  • the power conversion device is a power conversion circuit (inverter) that converts DC power into AC power using a pulse signal of PWM control, and detects a current flowing in the power conversion circuit to vector the power conversion circuit. And a vector control unit for controlling.
  • the power converter further includes an open phase section for stopping the switch elements of the upper and lower arms in phase by stopping the pulse signal of the section determined based on the zero crossing point of the current phase flowing through the power conversion circuit.
  • the power conversion device can reduce the switching loss by reducing the number of switchings at the time of PWM control.
  • the power conversion device can acquire accurate position information of the magnet position of the motor by the zero crossing point of the current phase. As a result, stable vector control can be performed to improve the efficiency of the power conversion circuit (inverter) and the motor.
  • FIG. 1 shows a circuit configuration of a power conversion device 1 of a PWM control method according to the present embodiment.
  • the power conversion device 1 of the present embodiment in the case where the AC motor 3 which is a permanent magnet synchronous motor is driven by vector control by the power conversion circuit 4 consisting of a three phase inverter driven by PWM control.
  • the power conversion circuit 4 consisting of a three phase inverter driven by PWM control.
  • a control method when a phase pulse stop section (that is, an open phase section) is provided in the pulse signal of the power conversion circuit 4 will be described.
  • the power conversion device 1 is configured to include a power conversion circuit 4, a phase current detection unit 6, and a control device 5.
  • the power conversion circuit 4 is configured to include a three-phase inverter that converts DC power into AC power.
  • the phase current detection unit 6 detects the motor current flowing through the AC motor (motor) 3 connected to the power conversion circuit 4.
  • the control device 5 performs vector control using a pulse signal that performs PWM control based on the phase current information (current) ⁇ detected by the phase current detection unit 6.
  • a DC voltage Vd is applied to the power conversion circuit 4 by the power supply 2.
  • the power conversion circuit 4 is configured to include a power conversion main circuit 41 and a gate driver 42.
  • the gate driver 42 generates a gate signal supplied to an IGBT (Insulated Gate Bipolar Transistor) of the power conversion main circuit 41 based on the pulse signal ⁇ from the pulse control unit 7.
  • the power conversion main circuit 41 is composed of switching elements Q1 to Q6 of a three-phase configuration in which an IGBT and a diode are connected in parallel in the reverse direction.
  • the power conversion main circuit 41 has U-phase, V-phase, and W-phase switching legs, and converts DC power into AC power using the pulse signal ⁇ output from the pulse control unit 7.
  • the U-phase switching leg is configured by connecting switching elements Q1 and Q2 in series between the positive electrode and the negative electrode.
  • the collector of switching element Q1 is connected to the positive electrode
  • the emitter of switching element Q2 is connected to the collector of switching element Q2.
  • the emitter of the switching element Q2 is connected to the negative electrode.
  • a connection node between the emitter of switching element Q1 and the collector of switching element Q2 is connected to the U-phase coil of AC motor 3.
  • a voltage at a connection node between the emitter of the switching element Q1 and the collector of the switching element Q2 is referred to as a voltage Vu.
  • the current flowing through the U-phase coil of the AC motor 3 is referred to as a U-phase alternating current Iu.
  • the pulse signal GPU + output from the gate driver 42 is applied to the gate of the switching element Q1.
  • the pulse signal GPU- output from the gate driver 42 is applied to the gate of the switching element Q2.
  • the switching leg of the V phase is configured by connecting switching elements Q3 and Q4 in series between the positive electrode and the negative electrode.
  • the collector of switching element Q3 is connected to the positive electrode, and the emitter of switching element Q3 is connected to the collector of switching element Q4.
  • the emitter of switching element Q4 is connected to the negative electrode.
  • a connection node between the emitter of switching element Q3 and the collector of switching element Q4 is connected to the V-phase coil of AC motor 3.
  • Pulse signals output from the gate driver 42 are applied to the gates of the switching elements Q3 and Q4, respectively.
  • the switching leg of the W phase is configured by connecting switching elements Q5 and Q6 in series between the positive electrode and the negative electrode.
  • the collector of switching element Q5 is connected to the positive electrode, and the emitter of switching element Q5 is connected to the collector of switching element Q6.
  • the emitter of switching element Q6 is connected to the negative electrode.
  • a connection node between the emitter of switching element Q5 and the collector of switching element Q6 is connected to the W-phase coil of AC motor 3.
  • Pulse signals output from the gate driver 42 are applied to the gates of the switching elements Q5 and Q6, respectively.
  • control device 5 is configured to include a pulse control unit 7, a vector control unit 8, and a pulse stop control unit 9.
  • the pulse control unit 7 supplies a pulse signal ⁇ controlled based on the applied voltage command (command voltage) V * to the gate driver 42 to perform PWM control.
  • the vector control unit 8 performs vector control using the phase current information ⁇ detected by the phase current detection unit 6 to calculate an applied voltage command V * .
  • the pulse stop control unit 9 is a phase pulse stop control signal for stopping the pulse signal ⁇ of the phase pulse stop section (open phase section) ⁇ near the current zero cross based on the phase information (current phase) of the current calculated by vector control.
  • (Pulse stop control signal) ⁇ is output to the pulse control unit 7.
  • the phase pulse stop control signal (pulse stop control signal) ⁇ stops the switching elements on the positive side and the negative side of the predetermined phase of the power conversion circuit 4.
  • Non-Patent Document 1 Sudmoto et al., “Simple Vector Control of Position Sensorless Permanent Magnet Synchronous Motor for Home Appliances”) Theory of Electrical Engineering D, Vol. 124, No. 11 (2004) pp. 1131-3140
  • Non-Patent Document 2 Tobari et al., "Study of New Vector Control Method for Permanent Magnet Synchronous Motor for High Speed," Electrology D, Vol. 129, Vol. 1, No. 1 (2009) pp.
  • the inverter output current is detected, three-phase to two-phase conversion (dq conversion; direct-quadrature conversion) is fed back to the control system, and the two-phase to three-phase conversion is performed again to drive the inverter It can be realized by using general vector control, and the control method is not specified. Therefore, since the operation of the vector control unit 8 is a known technique, the detailed description will be omitted.
  • FIG. 2 is a front view of the indoor unit 100, the outdoor unit 200, and the remote control Re of the air conditioner A in the present embodiment.
  • the air conditioner A is called a so-called room air conditioner.
  • the air conditioner A includes an indoor unit 100, an outdoor unit 200, a remote controller Re, and the power conversion device 1 (not shown in FIG. 2) shown in FIG.
  • the indoor unit 100 and the outdoor unit 200 are connected by a refrigerant pipe 300, and the air in the room where the indoor unit 100 is installed is air-conditioned by a known refrigerant cycle.
  • the indoor unit 100 and the outdoor unit 200 mutually transmit and receive information via a communication cable (not shown).
  • the outdoor unit 200 is connected by a wire (not shown), and an AC voltage is supplied via the indoor unit 100.
  • the power conversion device 1 (see FIG. 1) is included in the outdoor unit 200, and converts alternating current power supplied from the indoor unit 100 side into direct current power.
  • the remote control Re is operated by the user, and transmits an infrared signal to the remote control transmission / reception unit Q of the indoor unit 100.
  • the contents of the infrared signal are commands such as an operation request, a change of the set temperature, a timer, a change of the operation mode, and a stop request.
  • the air conditioner A performs the air conditioning operation such as the cooling mode, the heating mode, and the dehumidifying mode based on the instruction of the infrared signals.
  • the indoor unit 100 transmits data such as room temperature information, humidity information, and electricity cost information from the remote control transmission / reception unit Q to the remote control Re.
  • the operation of the power conversion device 1 mounted on the air conditioner A will be described.
  • the power conversion device 1 converts the DC voltage Vd supplied from the power supply 2 into an AC again to drive an AC motor 3 (not shown in FIG. 2).
  • the AC motor 3 (not shown) is a DC fan motor, but may be applied to a compressor motor.
  • FIG. 3 is a waveform diagram showing the relationship between AC voltage, AC current, and pulse signal flowing in the AC motor 3 in the comparative example, the horizontal axis representing voltage phase, and the vertical axis representing each level of voltage, current and pulse signal. ing.
  • the control device 5 compares the PWM carrier signal with the applied voltage command V * to generate a PWM pulse signal (pulse signal ⁇ ) in the pulse control unit 7. Further, the command value of the applied voltage command V * is obtained by the calculation of the vector control unit 8 based on the phase current information ⁇ detected by the phase current detection unit 6.
  • acquisition of the phase current information ⁇ by the phase current detection unit 6 is, for example, directly detecting an AC output current by CT (Current Transformer) as disclosed in FIG. 1 of JP-A-2004-48886.
  • CT Current Transformer
  • current information of a DC bus may be acquired by a shunt resistor, and a phase current may be reproduced based on the current information.
  • the first graph of FIG. 3 shows the PWM carrier signal and the applied voltage command V * , and shows the U-phase applied voltage command Vu * as a representative.
  • ⁇ v indicates a voltage phase with reference to the U phase.
  • the pulse control unit 7 In the PWM control method, as shown in the first graph of FIG. 3, the pulse control unit 7 generates the third graph of FIG. 3 based on the U-phase applied voltage command Vu * and the triangular wave carrier signal (PWM carrier signal).
  • the pulse signals GPU + and GPU ⁇ shown are generated, and the pulse signals GPU + and GPU ⁇ are output to the gate driver 42 for driving the power conversion main circuit 41.
  • the pulse signal GPU + is voltage-converted by the gate driver 42 and applied to the gate of the switching element Q1 on the upper side of the U phase.
  • the pulse signal GPU- is voltage-converted by the gate driver 42 and applied to the gate of the switching element Q2 on the lower side of the U phase. That is, the pulse signal GPU + and the pulse signal GPU- are opposite in polarity (1, 0).
  • a U-phase alternating current Iu as shown in the second graph of FIG. 3 flows in the alternating current motor 3.
  • ⁇ indicates the phase difference between the voltage and the current.
  • the vector control unit 8 performs vector control based on phase current information ⁇ including the U-phase alternating current Iu to control the voltage amplitude and the phase difference ⁇ between the voltage and the current.
  • FIG. 4 is a waveform diagram showing a relationship between an AC voltage, an AC current and a pulse signal flowing in the AC motor 3 and a phase pulse stop control signal in the present embodiment, in which the horizontal axis represents voltage phase and the vertical axis represents voltage; The respective levels of the current, the pulse signal and the open phase control signal (phase pulse stop control signal) are shown. That is, FIG. 4 is a waveform chart at the time of intermittent energization operation shown in comparison with the waveform chart at the time of normal operation of FIG.
  • the pulse stop control unit 9 generates the phase ⁇ and the phase ⁇ + ⁇ with reference to the zero-crossing point ⁇ of the current phase controlled by the vector control as shown in the following equation (1) Further, a phase pulse stop control signal (open phase control signal) ⁇ for stopping switching of both the pulse signals GPU + and GPU ⁇ is output to the pulse control unit 7 during the phase pulse stop interval (open phase interval) ⁇ .
  • the phase pulse stop control signal ⁇ outputs “0” when stopping switching of both the pulse signals GPU + and GPU ⁇ , and outputs “1” when performing switching of the PWM control method without stopping the switching.
  • the voltage phase ⁇ v with reference to the U phase is ⁇ / When 2 ⁇ v ⁇ + ⁇ / 2 and ⁇ + ⁇ / 2 ⁇ v ⁇ + ⁇ + ⁇ / 2, switching by the pulse signals GPU + and GPU ⁇ is stopped. And switching by pulse signal GPU + and GPU- is performed at other times.
  • both of the pulse signals GPU + and GPU ⁇ are turned off in the phase pulse stop interval ⁇ of the phase pulse stop control signal ⁇ . Therefore, as shown in the third graph of FIG. 4, the pulse control unit 7 outputs a signal train of pulse signals paused in the phase pulse stop interval ⁇ .
  • the phase pulse stop interval (open phase interval) ⁇ is set twice over one cycle of the voltage and current.
  • the target PWM control modulation method is not limited to the sine wave PWM control method, and the same phase pulse can be used in the two-phase modulation PWM control method or the third harmonic addition PWM control method. It is possible to provide the stop section ⁇ .
  • the pulse signals GPU + and GPU- provided with a period for stopping the switching operation by the pulse stop control unit 9 reference the applied voltage phase and the induced voltage phase of the AC motor 3 in the switching stop period and the switching operation period.
  • the shape is not provided. That is, the switching stop period and the switching operation period of the pulse signals GPU + and GPU ⁇ are set with reference to the zero cross point of the current phase.
  • the pulse signal train has an ON / OFF duty before and after the zero cross point of voltage. Is symmetrical.
  • the phase pulse stop section ⁇ is provided based on the current phase (that is, because it is not a pulse signal based on the voltage phase), as shown in the third graph of FIG.
  • the ON / OFF duty of the pulse signal train is not symmetrical. That is, in the present embodiment, the ON / OFF duty of the pulse signal train is asymmetrical before and after the current zero cross point.
  • the phase pulse stop section ⁇ is provided in the section including the zero cross point of the current, so as shown in the third graph of FIG.
  • the front and rear pulse signal trains A and B have an asymmetrical shape. From this, when the phase pulse stop section ⁇ is provided in the section including the zero cross point of the current, the present embodiment is implemented by observing whether the pulse signals before and after the phase pulse stop section ⁇ are asymmetrical. It can be easily determined whether or not the intermittent energization operation of the above is applied.
  • FIG. 5 is a waveform diagram showing the relationship between the U-phase voltage, the U-phase current, and the pulse signal when driving an actual device provided with the power conversion device 1 of the present embodiment, the horizontal axis representing voltage phase and the vertical axis The respective levels of voltage, current, and pulse signal are shown. That is, FIG. 5 is a method in which the phase pulse stop section is provided in the vicinity including the zero cross point of the current due to the intermittent energization operation of this embodiment, and the phase pulse stop section is set in the two-phase modulation type PWM control method Shows the voltage, current and pulse signal when driving
  • the first graph of FIG. 5 shows U-phase terminal voltage Vun of the power conversion main circuit 41
  • the second graph of FIG. 5 shows U-phase AC current Iu flowing through the AC motor 3
  • the switching signals of the pulse signals GPU + and GPU ⁇ are both off in the section (indicated by ⁇ ) sandwiched by the one-dot chain line, and the phase pulse stop section ⁇ is set. Can be confirmed. In addition, since the phase pulse stop section ⁇ is set, it can be confirmed at the same time that the U-phase alternating current Iu becomes zero in the section sandwiched by the one-dot chain line.
  • FIG. 6 is a characteristic diagram showing the relationship between the power conversion circuit loss, the motor loss and the total loss obtained by adding them to the phase pulse stop interval (open phase interval) ⁇ by the power conversion device 1 of the present embodiment.
  • the axis represents a phase pulse stop section (open phase section) ⁇
  • the vertical axis represents a loss. That is, FIG. 6 shows the characteristics of the total loss obtained by combining the phase pulse stop interval ⁇ set by the pulse stop control unit 9 and the loss of the power conversion circuit 4, the loss of the AC motor 3, and these two losses.
  • the loss (power conversion circuit loss) of the power conversion circuit 4 of the present embodiment is reduced because the number of times of switching decreases as the phase pulse stop interval ⁇ increases. Do. Further, the loss (motor loss) of the AC motor 3 is increased because the harmonic component of the current is increased by providing the phase pulse stop section ⁇ . Furthermore, since the increase of the harmonic component of the current becomes remarkable due to the increase of the phase pulse stop interval ⁇ , the increase of the loss (motor loss) of the AC motor 3 resulting from this also becomes remarkable. Therefore, as shown in FIG. 6, there is a phase pulse stop interval ⁇ opt in which the total loss obtained by adding these two losses (power conversion circuit loss and motor loss) is minimized. By setting the phase pulse stop interval ⁇ to this phase pulse stop interval ⁇ opt , it is possible to reduce the overall loss of the power conversion device 1.
  • the pulse stop control unit 9 As described above, by using the pulse stop control unit 9, it is possible to reduce the number of switching times of the pulse signal for performing the PWM control. In other words, when the pulse stop control unit 9 performed by the control of the microcomputer is configured by software, the configuration of the power conversion circuit 4 of the comparative example is not changed, and the addition of new hardware is not performed. It becomes possible to achieve high efficiency. Further, since the switching operation is stopped near the zero cross of the current of the AC motor 3, it is possible to suppress an increase in torque pulsation with respect to the 150-degree conduction method.
  • the vector control method of the present embodiment is position sensorless simple vector control, and is simplified based on conventional vector control.
  • This position sensorless simple vector control can exhibit the same performance as ideal vector control except for a transient state in which the speed and load torque fluctuate.
  • position sensorless simple vector control can not be expected to perform as well as ideal vector control in transient conditions in which speed and load torque change. In such a transient state, if the PWM output is stopped by the intermittent current supply operation, the vibration may be deteriorated or stopped.
  • the intermittent energization operation is performed only when it is determined that the motor is stably driven, thereby preventing the deterioration of the motor vibration and the stop of the motor.
  • FIG. 7 is a graph showing an execution area and a hysteresis area of the intermittent energization operation when applied to a DC fan.
  • the horizontal axis of the graph indicates the number of rotations per minute, that is, the rotation speed.
  • the vertical axis of the graph indicates the current flowing through the AC motor 3.
  • the Im reference value is a current value which is a high frequency rotation speed at no load.
  • the motor current Im can be calculated by the following equation (2).
  • the solid line graph shows the relationship between the actual rotation speed N and the motor current Im at no load.
  • the middle broken line graph shows the relationship between the actual rotation speed N and the motor current Im when the predetermined positive load is applied to the AC motor 3, and is a value higher than the solid line graph by the current I r2 .
  • the fine broken line graph shows the relationship between the actual rotation speed N and the motor current Im when a larger positive load is applied to the AC motor 3, which is higher than the medium broken line graph by the current Ih2 . For example, when a headwind blows on the DC fan, a positive load is applied to the AC motor 3 and swings in the direction of a medium broken line graph or a fine broken line graph.
  • the alternate long and short dash line graph indicates the relationship between the actual rotation speed N and the motor current Im when the predetermined negative load is applied to the AC motor 3, and is a value lower than the solid line graph by the current I r1 .
  • the rough broken line graph shows the relationship between the actual rotation speed N and the motor current Im when a further negative load is applied to the AC motor 3, which is lower than the medium broken line graph by the current Ih1 .
  • a forward wind blows on a DC fan a negative load is applied to the AC motor 3 and swings in the direction of a dashed dotted line graph or a rough broken line graph.
  • Execution region Z 1 is a region of dense hatching indicates a region to begin executing the intermittent power supply operation.
  • the execution region Z 1 is a region between the dashed graph and dashed line graphs moderate. That is, a load within a predetermined range is applied to the motor.
  • the control device 5 starts the intermittent energization operation.
  • FIG. 7 is a case where it applies to a DC fan, it is thought that the load concerning AC motor 3 is substantially the same in positive / negative. Therefore, the current I r1 and the current I r2 are set equal.
  • Execution region Z 1 further is directed to Im lower limit value or more regions plus current I h1 to the limiter.
  • the phase current detection unit 6 of the present embodiment detects a current by a shunt resistor (not shown). Therefore, there is a detectable Im lower limit. Therefore, there is provided a lower limit to execution region Z 1.
  • Hysteresis region Z 2 is a region of the thin hatching, when running intermittent energization operation, it indicates a region to continue the execution.
  • Hysteresis region Z 2 is a region between the fine broken line graph and long dashed line graph.
  • the control device 5 when the offset or hysteresis to the execution area Z 1, which stops the intermittent power supply operation. By providing the hysteresis, it is possible to prevent chattering at the boundary of the execution region Z 1.
  • FIG. 7 is a case where it applies to a DC fan, it is thought that the load concerning AC motor 3 is substantially the same in positive / negative. Therefore, the current I h1 and the current I h2 are set equal.
  • Hysteresis region Z 2 are as Im lower limit limiter or more regions.
  • execution region Z 1 and the hysteresis region Z 2 are a high-frequency rotational speed following areas.
  • FIG. 8 is a graph showing an execution region and a hysteresis region of the intermittent energization operation when applied to a compressor.
  • the solid line shows the relationship between the actual rotation speed N and the motor current Im at no load.
  • the middle broken line shows the relationship between the actual rotation speed N and the motor current Im when the predetermined positive load is applied to the AC motor 3, and is a value higher than the solid line by the current I r4 .
  • the fine broken line shows the relationship between the actual rotation speed N and the motor current Im when a larger positive load is applied to the AC motor 3, which is higher than the medium broken line by the current I h4 .
  • the alternate long and short dash line indicates the relationship between the actual rotation speed N and the motor current Im when a predetermined negative load is applied to the AC motor 3, and is a value lower than the solid line by the current I r3 .
  • the rough broken line shows the relationship between the actual rotation speed N and the motor current Im when a further large negative load is applied to the AC motor 3, which is a value lower than the middle broken line by the current Ih3 .
  • Execution region Z 3 is a region of dense hatching indicates a region to begin executing the intermittent power supply operation.
  • the execution region Z 3 is an area between the medium dashed and dashed line. That is, a load within a predetermined range is applied to the motor. At this time, the control device 5 starts the intermittent energization operation.
  • FIG. 8 is a case applied to a compressor, it is considered that the load applied to the AC motor 3 is mostly positive. Therefore, the current I r2 is set larger than the current I r1 .
  • Execution region Z 3 further has a value or more regions plus current I h3 in Im lower limit limiter.
  • the phase current detection unit 6 of the present embodiment detects a current by a shunt resistor (not shown). Therefore, there is a detectable Im lower limit. Therefore, there is provided a lower limit to execution region Z 3.
  • Hysteresis region Z 4 is a region of the thin hatching, when running intermittent energization operation, it indicates a region to continue the execution. Hysteresis region Z 4 is a region between the fine broken line and long dashed line.
  • FIG. 8 is a case where it applies to a compressor, it is thought that the case where it applies to the AC motor 3 is mostly positive. Therefore, the current I h4 is set larger than the current I h3 .
  • Hysteresis region Z 2 are as Im lower limit limiter or more regions. Furthermore the execution region Z 1 and the hysteresis region Z 2, are a high-frequency rotational speed following areas.
  • FIG. 9 is a diagram showing an execution region and a hysteresis region of the intermittent energization operation defined by the modulation factor.
  • the modulation factor exceeds M 1
  • the intermittent energization operation starts.
  • the modulation rate becomes smaller than (M 1 -M h ) after M 1 is exceeded, the intermittent power supply operation is stopped.
  • the intermittent energization operation is stopped when the modulation factor exceeds M 2 during the intermittent energization operation.
  • the modulation rate becomes smaller than (M 2 -M h ) after M 2 is exceeded, the intermittent power supply operation is started.
  • the intermittent energization operation is performed when the modulation rate is in the middle range, and the intermittent energization operation is stopped when the middle zone is deviated beyond a predetermined hysteresis. Thereby, it can be more accurately determined that the motor is stably driven.
  • FIG. 10 is a diagram showing an execution region and a hysteresis region of the intermittent energization operation defined by the rotational speed.
  • the intermittent energization operation is stopped.
  • the intermittent energization operation is started.
  • the intermittent energization operation is performed when the rotational speed is in the middle range, and the intermittent energization operation is stopped when the middle range is deviated beyond a predetermined hysteresis. Thereby, it can be more accurately determined that the motor is stably driven.
  • FIG. 11 is a diagram showing an execution region and a hysteresis region of the intermittent energization operation defined by the outside air temperature.
  • the intermittent energization operation when the outside air temperature exceeds T 2, the intermittent power supply operation is stopped. In after the outside air temperature exceeds T 2, when it becomes less than (T 2 -T h), the intermittent energization operation is started.
  • the intermittent energization operation is performed when the outside air temperature is in the middle range, and the intermittent energization operation is stopped when the middle zone is deviated beyond the predetermined hysteresis. Thereby, it can be more accurately determined that the motor is stably driven.
  • FIG. 12 is a graph showing a phase adjustment method in the case where the intermittent energization is stopped and in the case where it is permitted.
  • the intermittent power supply operation is permitted before time t0.
  • the control device 5 performs the intermittent power supply operation of the power conversion circuit 4 at the intermittent phase ⁇ .
  • control device 5 determines that the intermittent energization operation is stopped. After that, the control device 5 gradually decreases the intermittent phase until time t1, and stops the intermittent power supply operation at time t1. At time t2, the control device 5 determines the start of the intermittent power supply operation. After this, the control device 5 gradually increases the intermittent phase until time t3 and performs intermittent current supply operation at intermittent phase ⁇ at time t3. As described above, since the intermittent phase is gradually changed, it is possible to alleviate the switching shock accompanying the start and stop of the intermittent energization operation.
  • the present invention is not limited to the embodiments described above, but includes various modifications.
  • the above-described embodiments are described in detail to explain the present invention in an easy-to-understand manner, and are not necessarily limited to those having all the described configurations. It is possible to replace part of the configuration of one embodiment with the configuration of another embodiment, and it is also possible to add the configuration of another embodiment to the configuration of one embodiment. Moreover, it is also possible to add, delete, and replace other configurations for part of the configurations of the respective embodiments.
  • Each of the configurations, functions, processing units, processing means, etc. described above may be realized partially or entirely by hardware such as an integrated circuit.
  • Each configuration, function, etc. described above may be realized by software by the processor interpreting and executing a program that realizes each function.
  • Information such as programs, tables, and files that implement each function can be placed in a memory, hard disk, recording device such as a solid state drive (SSD), or recording medium such as a flash memory card or a digital versatile disk (DVD) it can.
  • SSD solid state drive
  • DVD digital versatile disk
  • control lines and information lines indicate what is considered to be necessary for the description, and not all control lines and information lines in a product are shown. In practice, almost all configurations may be considered to be connected to each other.
  • control lines and information lines indicate what is considered to be necessary for the description, and not all control lines and information lines in a product are shown. In practice, almost all configurations may be considered to be connected to each other.
  • the invention is not limited to a DC fan or a motor of a compressor, and may be applied to any motor.
  • the execution region may not have to be lower than or equal to the high frequency rotation number.
  • Determining stable driving is not limited to the area indicated by the motor current Im and the number of revolutions per minute, but may be the area indicated by the torque and the number of revolutions per minute.
  • the torque value is calculated by the sum of the torque theoretical formula calculated value and the offset value, as shown in equation (3).
  • the torque can be used instead of the motor current Im to determine whether or not stable driving is performed.
  • Determining stable driving is not limited to the area indicated by the motor current Im and the number of revolutions per minute, but may be the area indicated by the modulation rate and the number of revolutions per minute. When the applied voltage is constant, the modulation factor can be uniquely calculated from the motor current Im.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Chemical & Material Sciences (AREA)
  • Combustion & Propulsion (AREA)
  • Mechanical Engineering (AREA)
  • General Engineering & Computer Science (AREA)
  • Control Of Ac Motors In General (AREA)
  • Air Conditioning Control Device (AREA)
PCT/JP2017/037609 2017-10-17 2017-10-17 空気調和機 WO2019077689A1 (ja)

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JP2013115955A (ja) * 2011-11-30 2013-06-10 Hitachi Appliances Inc 電力変換装置、電動機駆動装置及び空気調和機
JP2014166044A (ja) * 2013-02-26 2014-09-08 Hitachi Appliances Inc 冷蔵庫

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DE10128839B4 (de) * 2001-06-15 2006-11-23 Otis Elevator Co., Farmington Verfahren und Vorrichtung zur Steuerung des Antriebs einer Fördereinrichtung
JP2009055748A (ja) * 2007-08-29 2009-03-12 Sanyo Electric Co Ltd 電流検出ユニット及びモータ制御装置
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JP2006014388A (ja) * 2004-06-22 2006-01-12 Matsushita Electric Ind Co Ltd インバータ制御装置
WO2013042437A1 (ja) * 2011-09-21 2013-03-28 日立アプライアンス株式会社 電力変換装置、電動機駆動装置および空調機
JP2013115955A (ja) * 2011-11-30 2013-06-10 Hitachi Appliances Inc 電力変換装置、電動機駆動装置及び空気調和機
JP2014166044A (ja) * 2013-02-26 2014-09-08 Hitachi Appliances Inc 冷蔵庫

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