WO2019015298A1 - 一种采用堆叠行波天线单元的低剖面宽带圆极化阵列天线 - Google Patents

一种采用堆叠行波天线单元的低剖面宽带圆极化阵列天线 Download PDF

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Publication number
WO2019015298A1
WO2019015298A1 PCT/CN2018/074772 CN2018074772W WO2019015298A1 WO 2019015298 A1 WO2019015298 A1 WO 2019015298A1 CN 2018074772 W CN2018074772 W CN 2018074772W WO 2019015298 A1 WO2019015298 A1 WO 2019015298A1
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Prior art keywords
antenna
layer
printed
antenna unit
rectangular
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PCT/CN2018/074772
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English (en)
French (fr)
Inventor
王海明
无奇
尹杰茜
余晨
洪伟
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东南大学
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Application filed by 东南大学 filed Critical 东南大学
Priority to US16/626,541 priority Critical patent/US11069965B2/en
Publication of WO2019015298A1 publication Critical patent/WO2019015298A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H01Q21/0037—Particular feeding systems linear waveguide fed arrays
    • H01Q21/0043—Slotted waveguides
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/16—Resonant antennas with feed intermediate between the extremities of the antenna, e.g. centre-fed dipole
    • H01Q9/26—Resonant antennas with feed intermediate between the extremities of the antenna, e.g. centre-fed dipole with folded element or elements, the folded parts being spaced apart a small fraction of operating wavelength
    • H01Q9/27—Spiral antennas

Definitions

  • the invention relates to a broadband circularly polarized antenna array manufactured by using PCB (Printed Circuit Board) technology, which belongs to the field of antenna technology.
  • PCB printed Circuit Board
  • Antennas are an important part of wireless communication systems. The rapid development of wireless communication has created an urgent need for antenna arrays that are small in size, low in cost, high in gain, and wider in bandwidth.
  • the circularly polarized antenna can receive arbitrary polarized electromagnetic waves from any antenna, can effectively improve the receiving and radiation efficiency, and is therefore widely used in practical interference and electronic reconnaissance.
  • the circularly polarized antenna can be realized by various antenna forms such as a horn antenna, a microstrip antenna or a back cavity antenna.
  • the present invention provides a low profile broadband circularly polarized array antenna using a stacked traveling wave antenna unit, which uses a traveling wave antenna unit of a stacked printed structure as an antenna unit, in a special Parameter optimization under boundary conditions, using Substrate Integrated Waveguide (SIW) technology to feed, which can meet the needs of wireless communication systems, can be applied to the microwave millimeter wave frequency band, easy to design and process, low
  • SIW Substrate Integrated Waveguide
  • the traveling wave antenna unit of the stacked printed structure is fed by designing the SIW slot coupling, and the parameters are optimized under special boundary conditions to excite the required broadband circularly polarized radiation in the far field; by adding matching metallized vias,
  • the T-junction and the H-junction in the SIW feed network are optimized to realize the broadbandization of the feed network of the antenna.
  • the antenna has the advantages of directional radiation, low profile, wideband circular polarization, high efficiency and the like.
  • the antenna body is composed of a dielectric plate of an antenna layer and 8 ⁇ 8 antenna elements printed thereon, which are formed by metal strips on the lower surface of the dielectric plate and metallized vias connecting them.
  • each antenna unit has the same shape, and the radiating portion is composed of three metal segments printed on both sides of the dielectric plate end to end and a metalized through hole connecting the two layers: the width is fixed, and the track is an Archimedes spiral
  • the metal strips are separated in proportion and printed on both sides of the dielectric plate, and the rectangular metal strip printed on the lower side of the dielectric plate is connected with the Archimedes spiral metal strip on the same side, and the two layers are connected.
  • the metallized vias connect the two layers of metallized strips to form the radiating portion of the antenna unit.
  • the constructed antenna can realize broadband right-hand circularly polarized radiation.
  • the upper feed network consists of two floors printed on the dielectric layer, 4 ⁇ 4 rectangular metal cavities composed of metalized vias, and rectangular strips cut on the upper and lower surfaces of the floor.
  • the gap is formed.
  • each rectangular metal cavity is composed of a metallized via arranged along a rectangular edge and a metallized via arranged along the central axis of the two long sides; a rectangular slit formed at the center of the rectangular metal cavity through the lower floor thereof
  • the stripe and the lower feed network feed the upper feed network to excite the rectangular metal cavity; the 2 ⁇ 2 rectangular slit strips cut at the edge of the rectangular metal cavity through the lower floor, and the electromagnetic coupling of the rectangular metal cavity to the antenna layer Feeding.
  • the lower layer feed network consists of two floors printed on the dielectric layer, a 1-minute 16-channel SIW splitter composed of a plurality of metalized vias, and an upwardly cut surface on the floor.
  • the 1 minute 16-channel SIW splitter consists of 3 T-junctions, 4 H-junctions and multiple metallized vias for impedance matching.
  • the power distribution order is T-junction, T-junction and H-type. Knot.
  • the design process of the antenna unit is:
  • Metal strips with a fixed width and a track of Archimedes spiral are separated by a specific ratio and printed on both sides of the dielectric plate.
  • the trajectory of the Archimedes spiral follows the following formula in the polar coordinate system:
  • the portion of the metal strip printed on the surface of the dielectric plate is an Archimedes spiral having a starting and ending value of ⁇ st and ⁇ mid respectively; the portion of the metal strip printed on the lower surface of the dielectric plate is composed of two segments, respectively having starting and ending values
  • the Archimedes spirals of ⁇ mid and ⁇ end and the rectangular metal strips used for slot coupling.
  • Metal strips on either side of the dielectric plate are joined by metallized vias to form the radiating portion of the antenna unit of the stacked printed structure.
  • the antenna unit is fed through the gap of the feeding network layer, and the traveling wave characteristic is excited on the antenna unit, and the circularly polarized radiation characteristic in a wide frequency band is realized.
  • the optimization process of the antenna unit is:
  • the periodic boundary conditions are applied to the dielectric layer including the antenna unit and the air layer above the antenna to simulate the axial ratio and impedance characteristics of the array. Under this condition, the simulation parameters are used to optimize the antenna parameters.
  • the wide-band circularly polarized antenna array of a traveling wave antenna unit using a stacked printed structure comprises three metal sections printed on both sides of the dielectric board end to end and a metallized through hole connecting the two layers.
  • a radiating portion of a circularly polarized antenna element a 2 ⁇ 2 antenna sub-array composed of a metallized through-hole cavity and four antenna elements, a 16-way fully parallel feed network composed of metallized via holes, a feed layer and a metal A gap between the cavity and the antenna for coupling the feed, a grounded Coplanar Waveguide (GCPW) for testing, and a transfer structure between the Substrate Integrated Waveguide (SIW).
  • GCPW Coplanar Waveguide
  • the antenna layer and the two feeding layers of the antenna are respectively printed on different dielectric plates, and the layers are fed through the gap coupling without physical connection, so that the bonding layer can be processed through a single layer PCB process. Bonding the multi-layer board brings the advantages of planar structure, easy integration, and simple processing.
  • the traveling wave antenna unit of the stacked printed structure of the antenna array can have directional circular polarization radiation characteristics over a wide bandwidth, thus bringing about broadband polarization characteristics of the array.
  • FIG. 1 is a schematic structural view of a layer of an antenna array after separation according to the present invention
  • FIG. 2 is a schematic diagram of a three-dimensional structure of an antenna unit according to the present invention.
  • Figure 3 is a plan view and a side view and a specific size of the antenna unit of the present invention.
  • FIG. 4 is a partial schematic view of an antenna array according to the present invention, including a SIW rectangular cavity fed thereto and a rectangular slit cut on the upper surface of the rectangular cavity;
  • FIG. 5 is a partial schematic view of an antenna array according to the present invention, including a rectangular slit cut on the upper surface of the rectangular cavity and a rectangular slit on the surface of the lower surface of the rectangular cavity that excites the rectangular cavity;
  • FIG. 6 is a partial schematic view of an antenna array of the present invention, including a schematic diagram of a lower 1/16 feeder network feeding at an outlet;
  • FIG. 7 is a schematic structural view of a T-junction in a 1 minute 16 feed network of an antenna array according to the present invention.
  • FIG. 8 is a schematic structural view of an H-type junction in a 1 minute 16 feed network of an antenna array according to the present invention.
  • FIG. 9 is a schematic diagram of a lower layer 1 minute 16-channel feed network of an antenna array according to the present invention.
  • FIG. 10 is a schematic diagram of simulation and actual measurement of standing wave variation with frequency of an antenna array according to the present invention.
  • FIG. 11 is a schematic diagram of simulation and actual measurement of the axial ratio and gain of the antenna array according to the present invention as a function of frequency;
  • Figure 12 is a diagram showing the measured axial ratio of the XZ plane of the antenna array of the present invention at 32 GHz;
  • Figure 13 is a diagram showing the measured axial ratio of the YZ plane of the antenna array of the present invention at 32 GHz;
  • Figure 14 is a diagram showing the measured axial ratio of the XZ plane of the antenna array of the present invention at 35 GHz;
  • Figure 15 is a diagram showing the measured axial ratio of the YZ plane of the antenna array of the present invention at 35 GHz;
  • Figure 16 is a diagram showing the measured axial ratio of the XZ plane of the antenna array of the present invention at 38 GHz;
  • Figure 17 is a diagram showing the measured axial ratio of the YZ plane of the antenna array of the present invention at 38 GHz;
  • Figure 18 is a physical test picture of the present invention.
  • a broadband circularly polarized antenna array of a traveling wave antenna unit using a stacked printed structure of the present invention is processed by a single printed circuit board (PCB) process.
  • PCB printed circuit board
  • FIG. 1 is a structural diagram of the antenna array layer separated.
  • the invention comprises a dielectric layer 10 of an antenna layer and 8 ⁇ 8 antenna elements 1 printed thereon by metal strips on the lower surface of the dielectric board and metallized vias connecting them; the antenna layer is separated from a dielectric plate 9 of the feed network layer; a fully-fed feed network 7 and 8 consisting of a two-layer Substrate Integrated Waveguide (SIW) feed network; a grounded coplanar waveguide for testing (Grounded Coplanar) GCPW-SIW transfer structure 6 between Waveguide, GCPW) and SIW.
  • SIW Substrate Integrated Waveguide
  • the antenna body is composed of a dielectric plate 10 of an antenna layer and 8 ⁇ 8 antenna elements 1 printed thereon, which are composed of metal strips on the lower surface of the dielectric plate and metallized vias connecting them.
  • each antenna unit 1 is equal in shape.
  • 2 is a schematic view showing the three-dimensional structure of the antenna unit 1.
  • the radiating portion of the circularly polarized antenna unit consisting of two sections of metal strips 14 and 19 printed on both sides of the dielectric plate 11 and the metallized through holes 15 connecting the two layers are connected end to end: the width is fixed and the track is
  • the metal strips of the Archimedes spiral are separated by a specific ratio and printed on both sides of the dielectric plate, and the rectangular metal strip printed on the lower side of the dielectric plate and the Archimedes spiral metal strip on the same side.
  • the two layers of metallized strips 14, 19 are joined by joining two layers of metallized vias 15 to form the radiating portion of the antenna unit 1.
  • the trajectory of the Archimedes spiral follows the following formula in the polar coordinate system:
  • the metal strip portions printed on the upper surface of the dielectric plate 11 are Archimedes spirals having starting and ending values of ⁇ st and ⁇ mid , respectively; the metal strip portions printed on the lower surface of the dielectric plate 11 are composed of two segments, respectively The values are the Archimedes spirals of ⁇ mid and ⁇ end , and the rectangular metal strips used for slot coupling.
  • the initial value of the proportional parameter can be chosen to be 4.
  • the metal strips on both sides of the dielectric plate 11 are connected by metallized through holes 15 to constitute the radiating portions of the antenna unit 1 of the stacked printed structure.
  • the antenna unit 1 is fed through the gap of the feeding network layer, and the traveling wave characteristic is excited on the antenna unit 1, and the circularly polarized radiation characteristic in a wide frequency band is realized.
  • the constructed antenna can realize broadband right-hand circularly polarized radiation.
  • dielectric layer 12 is a dielectric plate that separates the antenna layer from the feed network layer.
  • the dielectric layer 13 is a dielectric layer in which the SIW for feeding is located; 16 is a slit for coupling feeding on the surface metal layer of the SIW, the slit is a rectangle, and the long side thereof is perpendicular to the feeding direction of the SIW; 17 is a metallized through hole constituting the SIW.
  • 3(a) is a plan view and a specific size of the antenna unit 1
  • FIG. 3(b) is a side view and a specific size of the antenna unit 1.
  • l 1 is the side length of the antenna dielectric plate
  • l 2 is the width of the SIW feed line
  • l 3 is the length of the feed slot 16
  • w 1 is the width of the feed slot 16
  • w 2 is the distance from the end of the lower metal strip
  • the length of the center w 3 is the width of the metal strip
  • w 4 is the distance from the center of the feed gap 16 to the short-circuit end of the SIW feed line
  • r 1 is the diameter of the metallized via constituting the SIW feed line
  • p is the pitch of the metal via
  • h 1 is the dielectric plate height of the SIW feeder layer
  • h 2 is the dielectric plate height between the SIW feeder layer and the antenna layer
  • h 3 is the dielectric plate height of the antenna layer.
  • the upper feed network 8 consists of two floors printed on the dielectric layer, 4 x 4 rectangular metal cavities consisting of metallized vias, and cut on the upper and lower surfaces of the floor.
  • the rectangular strip slit 2 is formed.
  • each rectangular metal cavity 3 is composed of a metallized via arranged along a rectangular edge and a metallized via arranged along the central axis of the two long sides; a center of the rectangular metal cavity 3 cut through the lower floor thereof a rectangular slit strip 4, the lower feed network feeds the upper feed network, excites the rectangular metal cavity 3; the 2 ⁇ 2 rectangular slit strip 2, which is cut at the edge of the rectangular metal cavity 3, cut through the lower floor, rectangular metal
  • the cavity 3 is electromagnetically coupled to the antenna layer.
  • the lower layer feed network is formed by two floors printed on the dielectric layer, a 1-minute 16-channel SIW splitter 5 composed of a plurality of metalized vias, and a surface cut on the floor.
  • a rectangular strip slot 4 fed to the upper feed network and a GCPW-SIW transfer structure for testing 6 are formed.
  • the 1-minute 16-channel SIW splitter consists of three T-junctions, four H-junctions, and a plurality of metallized vias for impedance matching. Each of the T-junction and the H-junction utilizes metallized vias to improve its matching performance.
  • FIG. 4 is the uppermost antenna unit, the SIW rectangular cavity for feeding it, and the rectangular slit cut by the upper surface of the rectangular cavity;
  • FIG. 5 is a rectangular slit cut by the upper surface of the rectangular cavity and a rectangle of the lower surface of the rectangular cavity exciting the rectangular cavity.
  • Figure 6 is a schematic diagram of the lower layer of the 1 minute 16 feed network feeding at the exit.
  • s 1 is the pitch of the antenna elements
  • c 1 is the length of the rectangular slot feeding the antenna
  • d 1 is the width of the rectangular slot feeding the antenna
  • c 2 is the length of the rectangular slot feeding the rectangular cavity
  • d 2 is the width of the rectangular slot feeding the rectangular cavity
  • m 1 is the distance between the matching via and the edge of the SIW feeder in the lower feed network
  • m 2 and m 3 are the feed gap and SIW in the lower feed network
  • the distance between the edges of the feeders, m 4 and m 5 are the distances between the feed gaps feeding the antennas in the upper feed network and the edges of the SIW rectangular cavities
  • m 6 is the feed for the rectangular cavities in the upper feed network.
  • FIG 7 and Figure 8 are schematic diagrams of T-junction and H-junction in a 1 minute 16 feed network, respectively.
  • the black arrow represents the direction of power distribution.
  • the T-junction and the H-junction are composed of metallized vias represented by black circles.
  • Figure 9 is a schematic diagram of the lower layer 1 minute 16-channel feed network, consisting of SMA-GCPW-SIW switch, 3 T-junctions and 4 H-junctions.
  • the periodic boundary conditions are applied to the dielectric layer including the antenna unit and the air layer above the antenna to simulate the axial ratio and impedance characteristics of the array. Under this condition, the electromagnetic parameters are used to optimize the antenna parameters to obtain the antenna size.
  • the parameters are shown in Table 1. Where ⁇ r is the dielectric constant of the dielectric plate, and the meanings of the remaining parameters are explained above.
  • FIG. 10 is a schematic diagram of simulation and actual measurement of standing wave variation with frequency according to the present invention.
  • Figure 11 is a schematic diagram showing the simulation and actual measurement of the axial ratio and gain as a function of frequency according to the present invention.
  • 12 is a measured axial ratio pattern of the XZ plane at 32 GHz according to the present invention;
  • FIG. 13 is a measured axial ratio pattern of the YZ plane at 32 GHz according to the present invention;
  • FIG. 14 is a measured axial ratio pattern of the XZ plane at 35 GHz according to the present invention;
  • 15 is a measured axial ratio pattern of the YZ plane at 35 GHz according to the present invention;
  • FIG. 16 is a measured axial ratio pattern of the XZ plane at 38 GHz according to the present invention; and
  • FIG. 17 is a measured axial ratio pattern of the YZ plane at 38 GHz according to the present invention.
  • Figure 18 is a physical test picture of the present invention. It can be seen from the measured results that the designed broadband circularly polarized antenna achieves a 35.4% (30.3 GHz to 43.4 GHz) -10 dB impedance bandwidth, a 33.8% (29.5 GHz to 41.5 GHz) 3 dB axial ratio bandwidth, and 32.2% (30 GHz). ⁇ 41.5 GHz) 3 dB gain bandwidth and a right-handed circular polarization peak gain of 23.53 dBic.
  • parameter Value (mm) parameter Value (mm) l 1 5.0 l 2 4.0 l 3 3.5 w 1 0.6 w 2 0.9 w 3 0.3 w 4 0.6 r 1 0.3 r 2 0.6 p 0.5 h 1 0.508 h 2 0.381 h 3 1.016 a sp 0.2 ⁇ st 2.6 ⁇ mid 3.79 ⁇ end 8.63 s 1 5.0 m 1 1.4 m 2 0.3 m 3 0.3 m 4 0.3 m 5 0.3 m 6 0.3 a 1 0.157 a 2 1.438 c 1 3.5 c 2 3.5

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Abstract

本发明公开了一种基于堆叠行波天线单元的低剖面宽带圆极化阵列天线，包括：由3段首尾相连的印刷在介质板两侧的金属层及连接2层的金属化通孔构成的圆极化天线单元、由金属化通孔腔体及4个天线单元构成的2×2天线子阵、由金属化通孔构成的16路全并行馈电网络、馈电层和金属腔及天线之间用于耦合馈电的缝隙、用于测试的接地共面波导（Grounded Coplanar Waveguide, GCPW）与基片集成波导（Substrate Integrated Waveguide, SIW）之间的转接结构。采用本发明的方法所设计的天线阵列可以采用印刷电路板工艺制作。该天线阵列能够在非常宽的频段内实现圆极化辐射。

Description

一种采用堆叠行波天线单元的低剖面宽带圆极化阵列天线 技术领域
本发明涉及一种应用前景广泛的采用PCB(Printed Circuit Board，印刷电路板)技术制造的宽带圆极化天线阵列，属于天线技术领域
背景技术
天线是无线通信系统的重要组成部分。无线通信的快速发展，对体积小、成本低、高增益以及更宽带宽的天线阵列产生迫切需求。
圆极化天线能够接收来自任意天线的任意极化电磁波，可以有效地提高接收和辐射效率，因此被广泛地应用于实际的干扰与电子侦察中。圆极化天线可以利用喇叭天线、微带天线或背腔天线等多种天线形式实现。随着现代无线通信的快速发展，对低剖面易于平面集成、单向辐射、高增益、工作在毫米波频段、宽带化的圆极化天线阵列产生了很大需求。而现有的通过PCB印刷等形式加工的圆极化平面阵列天线的可用带宽通常不超过17％，难以满足毫米波频段日益增长的带宽需求。
发明内容
发明目的：针对现有技术中存在的问题与不足，本发明提供一种采用堆叠行波天线单元的低剖面宽带圆极化阵列天线，采用堆叠印刷结构的行波天线单元作为天线单元，在特殊边界条件下进行参数优化，利用基片集成波导(Substrate Integrated Waveguide,SIW)技术进行馈电，实现了可以满足无线通信系统需要的、可应用于微波毫米波频段的、易于设计和加工的、低剖面易于平面集成的8×8宽带圆极化天线阵列。通过设计SIW缝隙耦合给堆叠印刷结构的行波天线单元进行馈电，并在特殊边界条件下进行参数优化，在远场激励起所需的宽带圆极化辐射；通过加入匹配金属化过孔，对SIW馈电网络中的T型结和H型结进行优化，实现了天线的馈电网络的宽带化。该天线具有定向辐射、低剖面、宽带圆极化、效率高等优点。
技术方案：一种采用堆叠行波天线单元的低剖面宽带圆极化阵列天线，包括天线层的介质板及8×8个印刷于其上的、由位于介质板上下表面的金属条带及连接它们的金属化过孔所构成的天线单元；隔开天线层与馈电网络层的介质板；由 两层SIW馈电网络构成的全并馈馈电网络；用于测试的接地共面波导(Grounded Coplanar Waveguide,GCPW)与SIW之间的GCPW-SIW转接结构。
所述天线层中，天线本体由天线层的介质板及8×8个印刷于其上的、由位于介质板上下表面的金属条带及连接它们的金属化过孔所构成的天线单元构成。其中，每个天线单元形状相等，其辐射部分由3段首尾相连的印刷在介质板两侧的金属层及连接两层的金属化通孔构成：将宽度固定、轨迹为阿基米德螺旋线的金属条带按比例分开，分别印刷于介质板两侧，并将印刷于介质板下侧的矩形金属条带与位于同侧的阿基米德螺旋线金属条带连接，通过连接两层的金属化通孔将两层金属化条带连接，构成天线单元的辐射部分。构成的天线可实现宽带右旋圆极化辐射。
所述的2层馈电网络中，上层馈电网络由印刷在介质层上的两层地板、4×4个由金属化过孔构成的矩形金属腔及在地板上下表面切割出的矩形条状缝隙构成。其中，每个矩形金属腔由沿矩形边缘排布的金属化过孔及沿两条长边中轴线排布的金属化过孔构成；通过其下层地板切割出的位于矩形金属腔中心的矩形缝隙条带，下层馈电网络向上层馈电网络馈电，激励矩形金属腔；通过其下层地板切割出的位于矩形金属腔边缘处的2×2矩形缝隙条带，矩形金属腔向天线层电磁耦合馈电。
所述的2层馈电网络中，下层馈电网络由印刷在介质层上的两层地板、由多个金属化过孔构成的1分16路SIW功分器、地板上表面切割出的向上层馈电网络馈电的矩形条状缝隙及用于测试的GCPW-SIW转接结构构成。其中1分16路SIW功分器由3个T型结、4个H型结及多个用于阻抗匹配的金属化过孔构成，功率分配顺序依次为T型结、T型结和H型结。
天线单元的设计过程为：
将宽度固定、轨迹为阿基米德螺旋线的金属条带按特定比例分开，分别印刷于介质板两侧。阿基米德螺旋线的轨迹在极坐标系下遵循以下公式：
r＝a spφ        (式1)
其中，r是极坐标中的半径，φ是极坐标中的角度，a sp为螺旋线的半径增长常数。印刷于介质板上表面的金属条带部分为起止值分别为φ st和φ mid的阿基米德螺旋 线；印刷于介质板下表面的金属条带部分由两段构成，分别为起止值分别为φ mid和φ end的阿基米德螺旋线，及用于缝隙耦合的矩形金属条带。介质板两侧的金属条带通过金属化过孔连接，构成所述的堆叠印刷结构的天线单元的辐射部分。通过馈电网络层的缝隙对天线单元进行馈电，在天线单元上激励起了行波特性，实现了较宽频段内圆极化辐射特性。
天线单元的优化过程为：
将周期边界条件适用于包括天线单元的介质层及天线上方的空气层的四周，用以模拟阵列的轴比及阻抗特性，在此条件下，利用仿真软件对天线参数进行优化。
有益效果：本发明提供的采用堆叠印刷结构的行波天线单元的宽带圆极化天线阵列，由3段首尾相连的印刷在介质板两侧的金属层及连接两层的金属化通孔构成的圆极化天线单元的辐射部分、由金属化通孔腔体及4个天线单元构成的2×2天线子阵、由金属化通孔构成的16路全并行馈电网络、馈电层和金属腔及天线之间用于耦合馈电的缝隙、用于测试的接地共面波导(Grounded Coplanar Waveguide,GCPW)与基片集成波导(Substrate Integrated Waveguide,SIW)之间的转接结构。
具有如下优点：
该天线的天线层及两层馈电层分别印刷于不同的介质板上，层与层间均通过缝隙耦合馈电，且没有物理连接，因此可以通过单层PCB工艺加工后，通过粘合层对多层板进行粘合，带来了平面结构、易于集成、加工简单等优点。
该天线阵应用的堆叠印刷结构的行波天线单元，在很宽的带宽下能具有定向圆极化的辐射特性，因此带来了阵列的宽带圆极化特性。
附图说明
图1为本发明天线阵列层层分离后的结构示意图；
图2为本发明天线单元的三维结构示意图；
图3为本发明天线单元的俯视图和侧视图及具体尺寸；
图4为本发明天线阵列的局部示意图，包括为其馈电的SIW矩形腔及矩形腔上层表面切割的矩形缝隙；
图5为本发明天线阵列的局部示意图，包括矩形腔上层表面切割的矩形缝隙 及激励矩形腔的矩形腔下层表面的的矩形缝隙；
图6为本发明天线阵列的局部示意图，包括其下层的1分16馈电网络在出口处馈电的示意图；
图7为本发明天线阵列的1分16馈电网络中，T型结的结构示意图；
图8为本发明天线阵列的1分16馈电网络中，H型结的结构示意图；
图9为本发明天线阵列的下层1分16路馈电网络的示意图；
图10为本发明天线阵列的驻波随频率变化的仿真和实测示意图；
图11为本发明天线阵列的轴比和增益随频率变化的仿真和实测示意图；
图12为本发明天线阵列在32GHz处XZ平面的实测轴比方向图；
图13为本发明天线阵列在32GHz处YZ平面的实测轴比方向图；
图14为本发明天线阵列在35GHz处XZ平面的实测轴比方向图；
图15为本发明天线阵列在35GHz处YZ平面的实测轴比方向图；
图16为本发明天线阵列在38GHz处XZ平面的实测轴比方向图；
图17为本发明天线阵列在38GHz处YZ平面的实测轴比方向图；
图18为本发明的实物测试图片。
具体实施方式
下面结合具体实施例，进一步阐明本发明，应理解这些实施例仅用于说明本发明而不用于限制本发明的范围，在阅读了本发明之后，本领域技术人员对本发明的各种等价形式的修改均落于本申请所附权利要求所限定的范围。
本发明的一种采用堆叠印刷结构的行波天线单元的宽带圆极化天线阵列，采用单层印刷电路板(Printed Circuit Board，PCB)工艺加工。
图1为天线阵列层层分离后的结构图。本发明包括天线层的介质板10及8×8个印刷于其上的、由位于介质板上下表面的金属条带及连接它们的金属化过孔所构成的天线单元1；隔开天线层与馈电网络层的介质板9；由两层基片集成波导(Substrate Integrated Waveguide,SIW)馈电网络构成的全并馈的馈电网络7、8；用于测试的接地共面波导(Grounded Coplanar Waveguide,GCPW)与SIW之间的GCPW-SIW转接结构6。
天线层中，天线本体由天线层的介质板10及8×8个印刷于其上的、由位于介质板上下表面的金属条带及连接它们的金属化过孔所构成的天线单元1构成。 其中，每个天线单元1形状相等。图2为天线单元1的三维结构示意图。由3段首尾相连的印刷在介质板11两侧的两层金属化条带14、19及连接两层的金属化通孔15构成的圆极化天线单元的辐射部分：将宽度固定、轨迹为阿基米德螺旋线的金属条带按特定比例分开，分别印刷于介质板两侧，并将印刷于介质板下侧的矩形金属条带与位于同侧的阿基米德螺旋线金属条带连接，通过连接两层的金属化通孔15将两层金属化条带14、19连接，构成天线单元1的辐射部分。阿基米德螺旋线的轨迹在极坐标系下遵循以下公式：
r＝a spφ       (式1)
其中，r是极坐标中的半径，φ是极坐标中的角度，a sp为螺旋线的半径增长常数。印刷于介质板11上表面的金属条带部分为起止值分别为φ st和φ mid的阿基米德螺旋线；印刷于介质板11下表面的金属条带部分由两段构成，分别为起止值分别为φ mid和φ end的阿基米德螺旋线，及用于缝隙耦合的矩形金属条带。上下阿基米德螺旋线金属条带的比例可通过定义比例参数r ul＝n 1/n 2确定，其中，n 1＝φ mid-φ st，n 2＝φ end-φ mid。比例参数初值可选取为4。介质板11两侧的金属条带通过金属化通孔15连接，构成所述的堆叠印刷结构的天线单元1的辐射部分。通过馈电网络层的缝隙对天线单元1进行馈电，在天线单元1上激励起了行波特性，实现了较宽频段内圆极化辐射特性。构成的天线可实现宽带右旋圆极化辐射。图2中，介质层12为隔开天线层与馈电网络层的介质板。介质层13为用于馈电的SIW所在的介质层；16为在SIW上表面金属层切割出的用于耦合馈电的缝隙，缝隙为长方形，其长边与SIW的馈电方向相垂直；17为构成SIW的金属化通孔。图3(a)为天线单元1的俯视图及具体尺寸，图3(b)为天线单元1的侧视图及具体尺寸。其中，l 1为天线介质板的边长，l 2为SIW馈线的宽度，l 3为馈电缝隙16的长度，w 1为馈电缝隙16的宽度，w 2为下层金属条带末端距离天线中心的长度，w 3为金属条带的宽度，w 4为馈电缝隙16中心距离SIW馈线短路端的距离，r 1为构成SIW馈线的金属化过孔的直径，p为金属过孔的间距，h 1为SIW馈线层的介质板高度，h 2为SIW馈线层和天线层之间的介质板高度，h 3为天线层的介质板高度。
图1所示意的2层馈电网络中，上层馈电网络8由印刷在介质层上的两层地板、4×4个由金属化过孔构成的矩形金属腔3及在地板上下表面切割出的矩形条状缝隙2构成。其中，每个矩形金属腔3由沿矩形边缘排布的金属化过孔及沿两条长边中轴线排布的金属化过孔构成；通过其下层地板切割出的位于矩形金属腔3中心的矩形缝隙条带4，下层馈电网络向上层馈电网络馈电，激励矩形金属腔3；通过其下层地板切割出的位于矩形金属腔3边缘处的2×2矩形缝隙条带2，矩形金属腔3向天线层电磁耦合馈电。
所述的2层馈电网络中，下层馈电网络由印刷在介质层上的两层地板、由多个金属化过孔构成的1分16路SIW功分器5、地板上表面切割出的向上层馈电网络馈电的矩形条状缝隙4及用于测试的GCPW-SIW转接结构构成6。其中1分16路SIW功分器由3个T型结、4个H型结及多个用于阻抗匹配的金属化过孔构成。其中每个T型结和H型结都利用金属化过孔改善其匹配性能。
图4-6为天线阵列的局部示意图。图4为最上层的天线单元、为其馈电的SIW矩形腔及矩形腔上层表面切割的矩形缝隙；图5为矩形腔上层表面切割的矩形缝隙及激励矩形腔的矩形腔下层表面的的矩形缝隙；图6为其下层的1分16馈电网络在出口处馈电的示意图。其中，s 1为天线单元的间距，c 1为向天线馈电的矩形缝隙的长度，d 1为向天线馈电的矩形缝隙的宽度，c 2为向矩形腔馈电的矩形缝隙的长度，d 2为向矩形腔馈电的矩形缝隙的宽度，m 1为下层馈电网络中匹配过孔和SIW馈线边缘之间的距离，m 2和m 3为下层馈电网络中馈电缝隙和SIW馈线边缘之间的距离，m 4和m 5为上层馈电网络中为天线馈电的馈电缝隙和SIW矩形腔边缘之间的距离，m 6为上层馈电网络中为矩形腔馈电的馈电缝隙和SIW矩形腔过孔之间的距离。
图7和图8分别为1分16馈电网络中，T型结和H型结的示意图。黑色箭头代表功率分配的方向。T型结和H型结由黑色圆形代表的金属化过孔组成。图9为下层1分16路馈电网络的示意图，由SMA-GCPW-SIW转接、3个T型结和4个H型结组成。
将周期边界条件适用于包括天线单元的介质层及天线上方的空气层的四周，用以模拟阵列的轴比及阻抗特性，在此条件下，采用电磁仿真软件对天线参数进行优化，得到天线尺寸参数如表1所示。其中，ε r为介质板的介电常数，其余各 参数代表的意义已在上文说明。
图10为本发明的驻波随频率变化的仿真和实测示意图。图11为本发明的轴比和增益随频率变化的仿真和实测示意图。图12为本发明32GHz处XZ平面的实测轴比方向图；图13为本发明在32GHz处YZ平面的实测轴比方向图；图14为本发明在35GHz处XZ平面的实测轴比方向图；图15为本发明在35GHz处YZ平面的实测轴比方向图；图16为本发明在38GHz处XZ平面的实测轴比方向图；图17为本发明在38GHz处YZ平面的实测轴比方向图。图18为本发明的实物测试图片。由实测结果图可见，所设计的宽带圆极化天线实现了35.4％(30.3GHz～43.4GHz)的-10dB阻抗带宽，33.8％(29.5GHz～41.5GHz)的3dB轴比带宽，32.2％(30GHz～41.5GHz)的3dB增益带宽，以及23.53dBic的右旋圆极化峰值增益。
参数 数值(mm) 参数 数值(mm)
l 1 5.0 l 2 4.0
l 3 3.5 w 1 0.6
w 2 0.9 w 3 0.3
w 4 0.6 r 1 0.3
r 2 0.6 p 0.5
h 1 0.508 h 2 0.381
h 3 1.016 a sp 0.2
φ st 2.6 φ mid 3.79
φ end 8.63 s 1 5.0
m 1 1.4 m 2 0.3
m 3 0.3 m 4 0.3
m 5 0.3 m 6 0.3
a 1 0.157 a 2 1.438
c 1 3.5 c 2 3.5
d 1 0.6 d 2 0.6
b 1 1.846 b 2 0.296
b 3 0.503 ε r 2.2

Claims (7)

  1. 一种采用堆叠行波天线单元的低剖面宽带圆极化阵列天线，其特征在于：包括天线层的介质板及8×8个印刷于其上的、由位于介质板上下表面的金属条带及连接它们的金属化过孔所构成的天线单元；隔开天线层与馈电网络层的介质板；由两层SIW馈电网络构成的全并馈馈电网络；用于测试的接地共面波导与SIW之间的GCPW-SIW转接结构。
  2. 如权利要求1所述的采用堆叠行波天线单元的低剖面宽带圆极化阵列天线，其特征在于：所述天线层中，天线本体由天线层的介质板及8×8个印刷于其上的、由位于介质板上下表面的金属条带及连接它们的金属化过孔所构成的天线单元构成。
  3. 如权利要求2所述的采用堆叠行波天线单元的低剖面宽带圆极化阵列天线，其特征在于：每个天线单元形状相等，由3段首尾相连的印刷在介质板两侧的金属层及连接两层的金属化通孔构成的圆极化天线单元的辐射部分：将宽度固定、轨迹为阿基米德螺旋线的金属条带按比例分开，分别印刷于介质板两侧，并将印刷于介质板下侧的矩形金属条带与位于同侧的阿基米德螺旋线金属条带连接，通过连接两层的金属化通孔将两层金属化条带连接，构成天线单元的辐射部分；构成的天线可实现宽带右旋圆极化辐射。
  4. 如权利要求1所述的采用堆叠行波天线单元的低剖面宽带圆极化阵列天线，其特征在于：所述的2层馈电网络中，上层馈电网络由印刷在介质层上的两层地板、4×4个由金属化过孔构成的矩形金属腔及在地板上下表面切割出的矩形条状缝隙构成；其中，每个矩形金属腔由沿矩形边缘排布的金属化过孔及沿两条长边中轴线排布的金属化过孔构成；通过其下层地板切割出的位于矩形金属腔中心的矩形缝隙条带，下层馈电网络向上层馈电网络馈电，激励矩形金属腔；通过其下层地板切割出的位于矩形金属腔边缘处的2×2矩形缝隙条带，矩形金属腔向天线层电磁耦合馈电。
  5. 如权利要求1所述的采用堆叠行波天线单元的低剖面宽带圆极化阵列天线，其特征在于：所述的2层馈电网络中，下层馈电网络由印刷在介质层上的两层地板、由多个金属化过孔构成的1分16路SIW功分器、地板上表面切割出的向上层馈电网络馈电的矩形条状缝隙及用于测试的GCPW-SIW转接结构构成；其中1分16路SIW功分器由3个T型结、4个H型结及多个用于阻抗匹配的金 属化过孔构成。
  6. 如权利要求1所述的采用堆叠行波天线单元的低剖面宽带圆极化阵列天线，其特征在于：天线单元的设计过程为：
    将宽度固定、轨迹为阿基米德螺旋线的金属条带按比例分开，分别印刷于介质板两侧；阿基米德螺旋线的轨迹在极坐标系下遵循以下公式：
    r＝a spφ           (式1)
    其中，r是极坐标中的半径，φ是极坐标中的角度，a sp为螺旋线的半径增长常数。印刷于介质板上表面的金属条带部分为起止值分别为φ st和φ mid的阿基米德螺旋线；印刷于介质板下表面的金属条带部分由两段构成，分别为起止值分别为φ mid和φ end的阿基米德螺旋线，及用于缝隙耦合的矩形金属条带。介质板两侧的金属条带通过金属化过孔连接，构成所述的堆叠印刷结构的天线单元的辐射部分；通过馈电网络层的缝隙对天线单元进行馈电，在天线单元上激励起了行波特性，实现了较宽频段内圆极化辐射特性。
  7. 如权利要求1所述的采用堆叠行波天线单元的低剖面宽带圆极化阵列天线，其特征在于：天线单元的优化过程为：
    将周期边界条件适用于包括天线单元的介质层及天线上方的空气层的四周，用以模拟阵列的轴比及阻抗特性，在此条件下，对天线参数进行优化。
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