WO2018216158A1 - Dispositif de conversion de puissance - Google Patents

Dispositif de conversion de puissance Download PDF

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Publication number
WO2018216158A1
WO2018216158A1 PCT/JP2017/019476 JP2017019476W WO2018216158A1 WO 2018216158 A1 WO2018216158 A1 WO 2018216158A1 JP 2017019476 W JP2017019476 W JP 2017019476W WO 2018216158 A1 WO2018216158 A1 WO 2018216158A1
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Prior art keywords
timing
voltage
switching element
power supply
voltage component
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PCT/JP2017/019476
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English (en)
Japanese (ja)
Inventor
章太 渡辺
義章 石黒
友一 坂下
前田　貴史
陽 山上
達也 平山
Original Assignee
三菱電機株式会社
三菱電機照明株式会社
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Application filed by 三菱電機株式会社, 三菱電機照明株式会社 filed Critical 三菱電機株式会社
Priority to PCT/JP2017/019476 priority Critical patent/WO2018216158A1/fr
Priority to JP2019519896A priority patent/JP6659196B2/ja
Publication of WO2018216158A1 publication Critical patent/WO2018216158A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac

Definitions

  • the present invention relates to a power conversion device that performs DC / DC power conversion.
  • Zero cross switching control (hereinafter referred to as ZCS control) is known as a highly efficient control method for a power conversion device that includes a switching element and a reactor and converts an input DC voltage into a DC voltage of an arbitrary magnitude.
  • the ZCS control is a control for detecting the timing when the current flowing through the switching element or the current flowing through the reactor becomes zero as a zero current signal and switching the switching element at the timing when the zero current signal is detected.
  • the ZCS control has a problem that the switching frequency is increased at a light load, and the switching loss is increased.
  • Patent Document 1 discloses a method of inserting a delay time between detection of a zero current signal and switching of a switching element.
  • Patent Document 2 discloses a method of counting the number of detected zero current signals and switching the switching element at a timing when the number of zero current signals reaches a certain number.
  • Patent Document 1 and Patent Document 2 the case where an AC voltage component is superimposed on an input DC voltage that is an input voltage of a power converter is not studied. Therefore, when an AC voltage component is superimposed on the input DC voltage, there is a problem that a large ripple occurs in the output voltage.
  • the present invention has been made to solve the above-described problems, and provides a power conversion device capable of reducing ripple of an output voltage even when an AC voltage component is superimposed on an input DC voltage. Objective.
  • a power conversion device includes a power supply main circuit unit that has a switching element and a reactor, converts an input voltage in which an AC voltage component is superimposed on a DC voltage component, and outputs the power to a load.
  • the switching element When the detected value of the input voltage increases due to the AC voltage component superimposed on the DC voltage component, the switching element is turned on more than when the detected value of the input voltage decreases due to the AC voltage component superimposed on the DC voltage component.
  • the power supply control part which determines the ON timing of the said switching element so that timing may be delayed is provided.
  • output voltage ripple can be reduced even when an AC voltage component is superimposed on an input DC voltage.
  • FIG. 1 is a circuit block diagram showing a power conversion apparatus 1 according to Embodiment 1 of the present invention.
  • the power conversion device 1 according to the first embodiment includes a power supply main circuit unit 2 and a power supply control unit 3.
  • the power supply main circuit unit 2 includes a converter 6 having a switching element 11, a diode 13, and a reactor 12, and a capacitor Co that smoothes the output voltage of the converter 6.
  • an input power supply 4 is connected to the input side of the converter 6, and a load 5 is connected to the output side of the capacitor Co.
  • the input power supply 4 is a device that outputs a voltage Vin (hereinafter referred to as an input voltage Vin or a pulsating voltage Vin) including an AC voltage component and a DC voltage component.
  • the input power supply 4 only needs to output a pulsating voltage Vin, and as shown in FIG. 2, the AC voltage Vac output from the AC power supply 41 is full-wave rectified by a diode bridge circuit 42, and then PFC (Power Factor Correction).
  • the circuit 43 may perform power conversion.
  • C1 and C2 indicate capacitors.
  • the input power supply 4 may be configured to output a voltage obtained by full-wave rectifying the AC voltage Vac by the diode bridge circuit 42 without using the PFC circuit 43.
  • the input power supply 4 an AC / DC converter (not shown) that directly converts the AC voltage Vac into a DC voltage without using the diode bridge circuit 42 may be used.
  • the input power supply 4 for generating the pulsating voltage Vin is shown as a circuit diagram in which an AC power supply 4A and a DC power supply 4B are connected in series.
  • the converter 6 is a power converter that inputs an input voltage (pulsation voltage) Vin and converts DC / DC power to a target output voltage Vo.
  • the converter 6 includes a step-down chopper circuit including a switching element 11, a reactor 12, and a diode 13. Composed.
  • the converter 6 may be any circuit that has a switching element and a reactor and performs DC / DC power conversion.
  • the converter 6 may be a step-up chopper circuit, a step-up / step-down chopper circuit, an H-bridge type step-up / step-down circuit, a SEPIC (Single Ended Primary Inductor). Converter), flyback converter, or Cuk converter.
  • SEPIC Single Ended Primary Inductor
  • the switching element 11 includes a FET (Field Effect Transistor) element and an IGBT (Insulated Gate Bipolar Transistor) element driven by a switching element drive signal Ga (hereinafter referred to as a gate signal Ga) generated by a power supply control unit 3 to be described later.
  • a gate signal Ga a switching element drive signal generated by a power supply control unit 3 to be described later.
  • the diode 13 may be changed to a switching element Q1 (not shown) such as an FET element or an IGBT element, and a synchronous rectification method may be employed in which the switching element 11 and the switching element Q1 are turned on / off by reverse logic.
  • the power main circuit unit 2 includes an input voltage detection unit 7, an output voltage detection unit 8, and a zero current detection unit 9.
  • the input voltage detector 7 detects the magnitude of the input voltage (pulsation voltage) Vin as an input voltage detection value Vinsen.
  • Vinsen For example, as shown in FIG. 1, two or more voltage dividing resistors connected in series Is provided.
  • the output voltage detection unit 8 detects the magnitude of the DC output voltage vo as an output voltage detection value Vosen.
  • the zero current detection unit 9 is for detecting the zero point of the current flowing through the reactor 12. For example, as shown in FIG. 1, an auxiliary winding having a reverse polarity with respect to the reactor 12 is provided.
  • the voltage VLsen obtained from the auxiliary winding of the zero current detection unit 9 is output to a zero current signal generation unit 31 of the power supply control unit 3 to be described later, and the zero current signal generation unit 31 detects the zero point of the current of the reactor 12 to zero.
  • the current signal ZCD is output.
  • the zero current detection unit 9 may not be a method using an auxiliary winding as long as it can detect the zero point of the current flowing through the reactor 12, for example, a current detection resistor is installed on the low side of the reactor 12, A method of detecting the zero point of the current of the reactor 12 from the voltage generated at both ends of the current detection resistor may be used.
  • the power supply control unit 3 includes a zero current signal generation unit 31, an on time generation unit 32, an on timing generation unit 33, and a switching drive unit 34.
  • the zero current signal generation unit 31 outputs the zero current signal ZCD representing the timing when the current flowing through the reactor 12 becomes zero based on the voltage VLsen obtained from the zero current detection unit 9.
  • the on-time generation unit 32 derives a time for maintaining the gate signal Ga at High (hereinafter referred to as “H”), that is, an on-time of the switching element 11. .
  • the on-timing generator 33 performs count variable ZCS control based on the zero current signal ZCD, the input voltage detection value Vinsen, and the output voltage detection value Vosen, and the timing when the gate signal Ga is set to “H”, that is, the switching element 11 is turned on. Determine timing.
  • the count variable ZCS control is control for determining the timing at which the gate signal Ga is set to “H” based on the AC voltage component superimposed on the input voltage (pulsation voltage) Vin.
  • the count variable ZCS control will be described in detail later.
  • the switching drive unit 34 receives the on-time from the on-time generation unit 32 and the on-timing from the on-timing generation unit 33, and generates a gate signal Ga that operates the switching element 11.
  • FIG. 3 shows the relationship between the gate signal Ga output from the switching drive unit 34, the reactor current iL flowing through the reactor 12, and the zero current signal ZCD output from the zero current signal generating unit 31 as time on the horizontal axis.
  • the gate signal Ga becomes Low (hereinafter referred to as “L”) and the switching element 11 is turned off, current flows in the order of the reactor 12, the load 5, the diode 13, and the reactor 12, and the reactor current iL decreases to zero. During the period when the reactor current iL decreases to zero, the zero current signal ZCD becomes “L”.
  • the period during which the reactor current iL increases and the period during which the reactor current iL decreases to zero become shorter as the power supplied to the load 5 decreases.
  • variable count ZCS control the rising of the zero current signal ZCD to “H” is counted during the period in which the resonance current flows through the reactor 12, and the gate signal Ga is set to “H” when the count reaches a predetermined number. .
  • the number of counts until the gate signal Ga is set to “H” is varied based on the AC voltage component superimposed on the pulsating voltage Vin. Specifically, when the voltage value of the pulsating voltage Vin increases due to the superimposed AC voltage component, the number of counts until the gate signal Ga is set to “H” is increased. Further, when the voltage value of the pulsation voltage Vin becomes smaller due to the superimposed AC voltage component, the number of counts until the gate signal Ga becomes “H” is decreased.
  • FIG. 4 and 5 are operation explanatory diagrams of the count variable ZCS control.
  • the zero current signal ZCD is counted, and the gate signal Ga is set to “H” at the timing when the count number becomes two.
  • the zero current signal ZCD is counted, and the gate signal Ga is set to “H” at the timing when the count number becomes three. 5 in which the count number of the zero current signal ZCD is increased and the gate signal Ga is set to “H”, the count number of the zero current signal ZCD is decreased and the gate signal Ga is set to “H” in FIG. It can be seen that the period during which the gate signal Ga is set to “L” is increased and the duty ratio of the gate signal Ga is reduced as compared with the one shown.
  • the duty ratio of the gate signal Ga is reduced by increasing the count number of the zero current signal ZCD, thereby suppressing an increase in output voltage.
  • the count number of the zero current signal ZCD is reduced to increase the duty ratio of the gate signal Ga and suppress the decrease in the output voltage.
  • variable count ZCS control varies the count number of the zero current signal ZCD according to the power supplied to the load 5. Specifically, at the time of light load, the count number of the zero current signal ZCD is increased compared with the case of high load. As a result, the power supplied to the load 5 is reduced, and it is possible to prevent the switching frequency from increasing even when the period during which the reactor current iL increases and the period during which the reactor current iL decreases are shortened.
  • the count number of the zero current signal ZCD may be set in any way as long as the switching frequency is set not to increase. For example, the switching frequency is set to be almost the same regardless of the power of the load 5. Alternatively, for example, when the power supplied to the load 5 is small, the switching frequency may be set to be lower than when the power supplied to the load is large.
  • the power supply control unit 3 may be a general digital control circuit (including a circuit using software having the same function as the digital control circuit) that does not use an IC (Interconnected Circuit), and some of the components thereof It may be a digital control circuit. Furthermore, an analog control circuit that does not use a digital control circuit may be used. In this embodiment, a configuration of a digital control circuit using a microcomputer is described.
  • the on-time generator 32 calculates the difference between the output voltage detection value Vosen and the target voltage value Voref, and determines the on-time of the switching element 11 so that the difference becomes zero.
  • the on-time is calculated using the output voltage detection value Vosen and the target voltage, such as PI control (proportional integral control), PID control (proportional derivative integral control), or other modern control, or H ⁇ (H-infinity) control. Any control may be used as long as the control is performed so that the difference between the values Voref is zero.
  • the output voltage Vo can be adjusted to an arbitrary target voltage value Voref by calculating the on-time of the on-time generator 32.
  • the on-timing generator 33 performs count variable ZCS control using the zero current signal ZCD, the input voltage detection value Vinsen, and the output voltage detection value Vosen, and generates the on-timing of the gate signal Ga.
  • the symbol S means a processing step.
  • the on-timing generation unit 33 starts control processing, the input voltage detection value Vinsen obtained by detecting the input voltage (pulsation voltage) Vin by the input voltage detection unit 7 of the power supply main circuit unit 2, and the output voltage detection unit
  • the output voltage detection value Vosen obtained by detecting the output voltage Vo is acquired by 8 (step S1).
  • step S2 the supply power of the load 5 is calculated from the output voltage detection value Vosen and the resistance value of the load 5 known in advance, and the reference count cnt is determined based on the supply power of the load 5 (step S2).
  • the reference count cnt is an integer equal to or greater than 1, and is set so that the numerical value increases as the power supplied to the load 5 decreases.
  • the execution position of step S2 may not be the position shown in FIG. 6, and step S2 may be executed after step S3 or step S4 described later. It is also possible to add a current detection circuit for the current flowing through the load 5 and calculate the power supplied to the load 5 using the detection value of the current flowing through the load 5 and the output voltage detection value Vosen.
  • step S3 the DC voltage component of the input voltage detection value Vinsen is calculated by calculating the average value of the input voltage detection value Vinsen, and the calculated result is set as the comparison threshold value Vcomp (step S3).
  • step S3 need not be performed every control cycle of the on-timing generation unit 33, and step S3 may be omitted after the comparison threshold value Vcomp is set once.
  • the comparison threshold value Vcomp need not be calculated from the input voltage detection value Vinsen. If the magnitude of the DC voltage component of the input power supply 4 is known in advance, the value may be set as the comparison threshold value Vcomp. .
  • the target output voltage of the AC / DC converter may be set in advance as the comparison threshold value Vcomp.
  • step S4 the comparison threshold Vcomp calculated in step S3 is compared with the input voltage detection value Vinsen.
  • FIG. 7 is a diagram for explaining a comparison between the comparison threshold value Vcomp and the input voltage detection value Vinsen.
  • a period T1 in which the input voltage detection value Vinsen is equal to or greater than the comparison threshold Vcomp is indicated by hatching, and is distinguished from a period T2 in which the input voltage detection value Vinsen is smaller than the comparison threshold Vcomp.
  • step S4 As a result of the comparison between the comparison threshold value Vcomp and the input voltage detection value Vinsen in step S4, during the period T2 when the input voltage detection value Vinsen is smaller than the comparison threshold value Vcomp, a value obtained by subtracting the decrease correction value x1 from the reference count cnt is set as the turn-on count ZCDcnt. Set (step S5). During a period T1 where the input voltage detection value Vinsen is equal to or greater than the comparison threshold Vcomp, a value obtained by adding the increase correction value x2 to the reference count cnt is set as the turn-on count ZCDcnt (step S6).
  • the decrease correction value x1 and the increase correction value x2 are both integers of 0 or more, but the decrease correction value x1 and the increase correction value x2 do not become 0 at the same time.
  • the decrease correction value x1 has a value less than the reference count cnt. Therefore, the turn-on count ZCDcnt never becomes zero or negative.
  • the zero current signal generation unit 31 of the power supply control unit 3 outputs a zero current signal ZCD indicating the timing when the reactor current iL becomes zero, and the on timing generation unit 33 detects the zero current signal ZCD (step S7). ). Then, the detection of the zero current signal ZCD is counted, and when the count number reaches the turn-on count ZCDcnt, the timing when the gate signal Ga is set to “H”, that is, the ON timing of the switching element 11 is determined (step S8).
  • the above description is the description of the operation of the on-timing generation unit 33 (the flowchart of FIG. 6). As described above, the count variable ZCS control can be realized by operating.
  • the effect of the count variable ZCS control of the present embodiment was confirmed using circuit simulation of Myway Plus.
  • a DC voltage of 300 V and an AC voltage of 20 V (100 Hz) were connected in series to obtain an input voltage.
  • the comparison threshold Vcomp is set to 300V
  • the reference count cnt is set to 3
  • the decrease correction value x1 is set to 1
  • the increase correction value x2 is set to 1
  • the target voltage value Voref is set to 200V.
  • FIG. 8 and 9 are diagrams showing simulation results when the count variable ZCS control is applied and when it is not applied.
  • the upper diagram shows the waveform of the input voltage detection value Vinsen and the comparison threshold value Vcomp
  • the middle diagram shows the waveform of the output voltage Vo
  • the lower diagram shows the turn-on count ZCDcnt.
  • FIG. 8 compares the input voltage detection value Vinsen and the comparison threshold Vcomp.
  • the turn-on count ZCDcnt is 4
  • the input voltage detection value Vinsen is the comparison threshold Vcomp. It can be confirmed that the turn-on count ZCDcnt is 2 when it is smaller (Vinsen ⁇ Vcomp).
  • FIG. 9 shows simulation results when the turn-on count ZCDcnt is always set to 2 regardless of the magnitude of the input voltage detection value.
  • the simulation result in FIG. 8 confirms that the pulsation of the output voltage Vo is smaller than the simulation result in FIG.
  • the ripple rate of the output voltage Vo calculated by dividing the difference between the maximum value and the minimum value of the output voltage Vo by the average value of the output voltage Vo is 0.068 in the simulation result of FIG. 8, and 0 in the simulation result of FIG. 131. Therefore, the output voltage ripple reduction effect of the variable count ZCS control was confirmed.
  • the turn-on count ZCDcnt is determined by comparing the input voltage detection value Vinsen and the comparison threshold value Vcomp calculated from the input voltage detection value Vinsen.
  • the turn-on count ZCDcnt may be determined in any way as long as it is determined based on the AC voltage component superimposed on the DC voltage component of the input voltage (pulsation voltage).
  • Vcomp1 and Vcomp2 may be provided as comparison threshold values, and the comparison threshold values Vcomp1 and Vcomp2 may be compared with the input voltage detection value Vinsen.
  • the turn-on count ZCDcnt is variable by three during one cycle of the pulsating voltage Vin.
  • a period T30 in which the input voltage detection value Vinsen is smaller than the comparison threshold Vcomp1 a period T20 in which the input voltage detection value Vinsen is smaller than the comparison threshold Vcomp2 and greater than or equal to the comparison threshold Vcomp1
  • the turn-on count ZCDcnt is determined so as to increase in order.
  • the step-down chopper circuit shown in FIG. 1 is used as the converter 6.
  • the converter 6 includes a switching element and a reactor, and any circuit that performs DC / DC conversion can be used.
  • a simple circuit may be used.
  • a booster chopper circuit may be used as the converter 6 as shown in FIG.
  • variable count ZCS control can be performed similarly to the configuration using the step-down chopper circuit for the converter 6 described so far. That is, the ripple of the output voltage Vo can be reduced by varying the turn-on count ZCDcnt according to the AC voltage component superimposed on the input voltage (pulsation voltage) Vin.
  • the effect of the variable count ZCS control of the present embodiment was confirmed using a circuit simulation of Myway Plus Co., in the case of using the boost chopper circuit of FIG.
  • a DC voltage of 100 V and an AC voltage of 20 V (100 Hz) were connected in series to obtain an input voltage.
  • the comparison threshold Vcomp is set to 100V
  • the reference count cnt is set to 3
  • the decrease correction value x1 is set to 1
  • the increase correction value x2 is set to 1
  • the target voltage value Voref is set to 200V.
  • 12 and 13 show simulation results when the variable count ZCS control is applied and when it is not applied when the step-up chopper circuit of FIG. 11 is used as the converter 6.
  • 12 and 13 the upper diagram shows the waveform of the input voltage detection value Vinsen and the comparison threshold Vcomp, the middle diagram shows the waveform of the output voltage Vo, and the lower diagram shows the turn-on count ZCDcnt.
  • FIG. 12 shows a simulation waveform when the variable count ZCS control is applied.
  • Vcomp comparison threshold
  • the turn-on count ZCDcnt 4
  • the input voltage detection value Vinsen is the comparison threshold Vcomp. It can be confirmed that the turn-on count ZCDcnt is 2 when it is smaller (Vinsen ⁇ Vcomp).
  • FIG. 13 is a simulation waveform when the turn-on count ZCDcnt is always set to 2 regardless of the input voltage detection value Vinsen. It can be confirmed that the pulsation of the output voltage Vo is smaller when the count variable ZCS control of FIG. 12 is applied than when the count variable ZCS control is not applied of FIG.
  • the ripple rate of the output voltage Vo calculated by dividing the difference between the maximum value and the minimum value of the output voltage Vo by the average value of the output voltage Vo is 0.043 in the case of FIG. 12, and 0.069 in the case of FIG. Met. Therefore, even when the booster chopper circuit is used as the converter 6, the output voltage ripple reduction effect by the variable count ZCS control can be confirmed.
  • the zero point of the current flowing through the reactor 12 is detected as the zero current signal ZCD using the zero current detecting unit 9 and the zero current signal generating unit 31, and the count variable ZCS control is performed.
  • the timing when the voltage applied to the switching element 11 becomes zero may be detected as the zero voltage signal ZVD, and the zero voltage signal ZVD may be used instead of the zero current signal ZCD.
  • the zero voltage detector 90 and the switching element 11 for detecting the voltage applied to the switching element 11 are applied as shown in FIG.
  • the zero voltage signal generator 310 that outputs the timing when the voltage becomes zero as the zero voltage signal ZVD is used.
  • Other configurations and operations are the same as those described above.
  • the control method for determining the ON timing of the switching element using the count number of the zero current signal ZCD has been described.
  • the ON timing of the switching element is set according to the AC voltage component superimposed on the input voltage.
  • the zero current signal ZCD may not be counted.
  • the ON timing of the switching element may be set to a timing at which a predetermined time has elapsed, and may be realized by a control method in which the predetermined time is made variable by an AC voltage component superimposed on the input voltage.
  • control for varying the predetermined time by the AC voltage component superimposed on the input voltage will be described based on the circuit diagram of the power conversion device in FIG. 15 and the circuit operation diagram in FIG.
  • the configurations of the power supply main circuit unit 2 and the power supply control unit 3 of the power conversion device 1 are basically the same as those of FIG. The operation is different.
  • the power supply control unit 3 includes a zero current signal generation unit 31 that outputs a zero current signal ZCD indicating a timing at which the current flowing through the reactor 12 becomes zero based on the voltage VLsen obtained from the zero current detection unit 9;
  • An on-time generator 32 for deriving an on-time of the switching element 11 based on the output voltage detection value Vosen and the target voltage value Voref, and a timing at which a predetermined time has elapsed based on the zero current signal ZCD is determined as the on-timing of the switching element 11.
  • An on-timing generation unit 33A that receives the on-time from the on-time generation unit 32 and the on-timing from the on-timing generation unit 33A, and generates a gate signal Ga that operates the switching element 11. Yes.
  • the on-timing generator 33A starts time measurement from the first rising timing t1 of the zero current signal ZCD after the switching element 11 is turned off, and switching is performed at the timing when the measured time reaches the predetermined time Td.
  • the on-timing for turning on the element 11 is determined.
  • the predetermined time Td for determining the ON timing of the switching element 11 is determined by an AC voltage component superimposed on the input voltage. That is, when the detected value Vinsen of the input voltage becomes larger due to the AC voltage component superimposed on the DC voltage component, the predetermined time Td than when the detected value of the input voltage Vinsen becomes smaller due to the AC voltage component superimposed on the DC voltage component. Delay control to increase
  • the timing for starting the time measurement is not based on the zero current signal ZCD, but may be based on the zero voltage signal ZVD described in FIG. 14, for example. Alternatively, the timing when the switching element 11 is turned on or the timing when the switching element 11 is turned off may be used.
  • FIG. 17 shows an example of a power converter that starts time measurement from the timing when the switching element 11 is turned on or off.
  • the switching detection unit 35 detects the on / off timing of the switching element 11 based on the gate signal Ga from the switching drive unit 34.
  • the on-timing generation unit 33B starts time measurement from the timing when the switching element 11 is turned on or off, and determines the on-timing for turning on the switching element 11 when the measured time reaches a predetermined time.
  • Other operations are the same as those described in FIGS. 15 and 16.
  • the power supply main circuit unit that has the switching element and the reactor, converts the input voltage in which the AC voltage component is superimposed on the DC voltage component, and outputs the power to the load,
  • the on-timing of the switching element is delayed compared to when the detected value of the input voltage decreases due to the AC voltage component superimposed on the DC voltage component.
  • the power supply control unit that determines the ON timing of the switching element is provided, the ripple generated in the output voltage can be reduced.
  • the power supply control unit compares the detected value of the input voltage with the comparison threshold value, and delays the on-timing of the switching element when the detected value of the input voltage is equal to or greater than the comparison threshold value compared to when it is smaller than the comparison threshold value. Since the ON timing of the switching element is determined, ripple generated in the output voltage can be reduced by simple control.
  • the comparison threshold value is a DC voltage component of the input voltage, ripple generated in the output voltage can be reduced by simple control.
  • the power supply control unit outputs a zero current signal that outputs a zero current signal indicating the timing when the current flowing through the reactor becomes zero, and a zero voltage that outputs a zero voltage signal indicating the timing when the voltage applied to the switching element becomes zero
  • An on-timing generator that counts the number of times either one of the signal generators and one of the zero-current signal and the zero-voltage signal and determines the timing when the count reaches a predetermined number as the on-timing of the switching element
  • a switching drive unit that turns on the switching element at the on-timing determined by the on-timing generation unit, and when the detected value of the input voltage becomes larger due to the AC voltage component superimposed on the DC voltage component, the detected value of the input voltage Compared to when the voltage becomes smaller due to the AC voltage component superimposed on the DC voltage component, Since variable count zero-crossing switching control is performed to increase the predetermined number of times, the ripple generated in the output voltage can be reduced, and the timing at which the current flowing through the reactor becomes zero or the voltage applied to
  • the power supply control unit outputs a zero current signal that indicates a timing when the current flowing through the reactor becomes zero, and a zero voltage that outputs a zero voltage signal that indicates the timing when the voltage applied to the switching element becomes zero From any one of the signal generation unit and the switching detection unit that detects the timing at which the switching element is turned on or off, and the zero current signal, the zero voltage signal, and the timing at which the switching element is turned on or off
  • An on-timing generator that determines when a predetermined time has elapsed as an on-timing of the switching element, and a switching drive unit that turns on the switching element at the on-timing determined by the on-timing generator, and the detected value of the input voltage is a DC voltage component Larger due to AC voltage component superimposed on When the detected value of the input voltage becomes smaller due to the AC voltage component superimposed on the DC voltage component, delay control is performed to increase the predetermined time, so the ripple generated in the output voltage by simple control Can be reduced.
  • the power supply control unit determines the on-timing of the switching element so as to delay the on-timing of the switching element compared to when the power supplied to the load is high.
  • count variable zero cross switching control is performed to increase the predetermined number of times compared to when the power supplied to the load is high.
  • delay control is performed to increase the predetermined time compared to when the power supplied to the load is high.
  • the power supply control unit when the power supplied to the load is large, (1) when the detected value of the input voltage becomes larger due to the AC voltage component superimposed on the DC voltage component, the detected value of the input voltage Compared to when it becomes smaller due to the AC voltage component superimposed on the component, the on-timing of the switching element is determined so as to delay the on-timing of the switching element, and the switching element is controlled to switch,
  • the power supplied to the load is small, (2) a control method for switching control of the switching element at a constant switching cycle, (3) regardless of the AC voltage component in which the detected value of the input voltage is superimposed on the DC voltage component,
  • a control method that counts the number of zero current signals indicating the timing at which the current flowing through the reactor becomes zero, determines the timing at which the count reaches a predetermined number as the ON timing of the switching element, and controls the switching of the switching element , At least one control may be performed. According to this, when the power supplied to the load is large, the ripple generated in the output voltage can be reduced.
  • the power supply control unit determines the on-time of the switching element based on the output voltage detection value and the target voltage value of the power supply main circuit unit, a desired output voltage can be obtained.
  • FIG. FIG. 18 is a circuit block diagram showing a power conversion device according to Embodiment 2 of the present invention.
  • the load is an LED (Light Emitting Diode) module 50 as compared with the first embodiment.
  • the load 5 in FIG. 1 is changed to the LED module 50, and an output voltage detection unit. 8 is changed to the output current detection unit 80, the output voltage detection value Vosen is changed to the output current detection value Isen, and the target voltage value Voref input to the on-time generation unit 32 is changed to the target current value Ioref.
  • the difference was made.
  • the output current detection unit 80 includes a current detection resistor (not shown), and detects a potential difference generated between both ends of the current detection resistor as a voltage conversion value Isen corresponding to the current flowing through the LED module 50.
  • the LED module 50 has a configuration in which all LED chips are connected in series in FIG. 18, the LED module 50 is not limited to a series connection, and may be a parallel connection or a series-parallel connection, or may be a single LED.
  • LED is connected as load here, you may change not to LED but to organic electroluminescence (organic EL), a laser diode, etc.
  • the control is changed from the control for adjusting the output voltage to the target voltage to the control for adjusting the output current to the target current.
  • the on-time generation unit 32 derives the on-time of the switching element 11 based on the output current detection value Iosen and the target current value Ioreef. That is, the on-time generating unit 32 calculates the difference between the output current detection value Isen and the target current value Ioref, and determines the on-time of the switching element 11 so that the difference becomes zero. If comprised in this way, control of the output current which flows into the LED module 50 can be performed by control similar to Embodiment 1.
  • the power supply control unit 3 determines that the input voltage detection value Vinsen becomes a DC voltage component when the input voltage detection value Vinsen becomes larger due to the AC voltage component superimposed on the DC voltage component. Since the switching control is performed by determining the on-timing of the switching element 11 so as to delay the on-timing of the switching element 11 as compared with the time when it becomes smaller due to the superimposed AC voltage component, the ripple of the output current can be reduced. .
  • the load is an LED
  • the ripple generated in the output current can be reduced by the variable count ZCS control or the delay control described in the first embodiment, the occurrence of light flickering can be prevented.
  • the dimming function can be achieved if the target current value Ioref that is normally input from outside is made variable by the dimming function. realizable.
  • the output current can be adjusted to the target current, Effects similar to those described in Embodiment 1 can be obtained. In particular, the ripple generated in the output current can be reduced.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)

Abstract

L'invention concerne un dispositif de conversion de puissance comprenant une unité (2) de circuit principal d'alimentation électrique et une unité (3) de commande d'alimentation électrique. L'unité (2) de circuit principal d'alimentation électrique comporte un élément (11) de commutation et un réacteur (12), et effectue une conversion de puissance sur une tension d'entrée ayant une composante de tension alternative superposée à une composante de tension continue pour transmettre la tension d'entrée convertie à une charge. L'unité (3) de commande d'alimentation électrique détermine la synchronisation de mise en marche de l'élément (11) de commutation, de façon à retarder la synchronisation de mise en marche de l'élément (11) de commutation lorsque la valeur détectée (Vinsen) de la tension d'entrée devient importante en raison de la composante de tension alternative superposée sur la composante de tension continue par rapport au moment où la valeur détectée (Vinsen) de la tension d'entrée devient petite en raison de la composante de tension alternative superposée à la composante de tension continue.
PCT/JP2017/019476 2017-05-25 2017-05-25 Dispositif de conversion de puissance WO2018216158A1 (fr)

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PCT/JP2017/019476 WO2018216158A1 (fr) 2017-05-25 2017-05-25 Dispositif de conversion de puissance
JP2019519896A JP6659196B2 (ja) 2017-05-25 2017-05-25 電力変換装置

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Citations (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2003098215A (ja) * 2001-09-26 2003-04-03 Canon Inc 電力変換システムにおける地絡検出のための装置及び方法
JP2014131455A (ja) * 2012-12-30 2014-07-10 Fuji Electric Co Ltd スイッチング電源装置
JP5828106B2 (ja) * 2011-04-13 2015-12-02 パナソニックＩｐマネジメント株式会社 固体光源点灯装置およびそれを用いた照明器具
JP2016059182A (ja) * 2014-09-10 2016-04-21 シャープ株式会社 スイッチング電源装置
JP2016111764A (ja) * 2014-12-03 2016-06-20 三菱重工業株式会社 不平衡補正装置、不平衡補正方法及びプログラム
JP2016119830A (ja) * 2014-12-22 2016-06-30 三菱電機株式会社 光源点灯装置及び照明器具
JP2016187241A (ja) * 2015-03-27 2016-10-27 サンケン電気株式会社 力率改善回路
JP2017070192A (ja) * 2015-09-28 2017-04-06 サンケン電気株式会社 スイッチング電源装置及びｌｅｄ点灯回路

Patent Citations (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2003098215A (ja) * 2001-09-26 2003-04-03 Canon Inc 電力変換システムにおける地絡検出のための装置及び方法
JP5828106B2 (ja) * 2011-04-13 2015-12-02 パナソニックＩｐマネジメント株式会社 固体光源点灯装置およびそれを用いた照明器具
JP2014131455A (ja) * 2012-12-30 2014-07-10 Fuji Electric Co Ltd スイッチング電源装置
JP2016059182A (ja) * 2014-09-10 2016-04-21 シャープ株式会社 スイッチング電源装置
JP2016111764A (ja) * 2014-12-03 2016-06-20 三菱重工業株式会社 不平衡補正装置、不平衡補正方法及びプログラム
JP2016119830A (ja) * 2014-12-22 2016-06-30 三菱電機株式会社 光源点灯装置及び照明器具
JP2016187241A (ja) * 2015-03-27 2016-10-27 サンケン電気株式会社 力率改善回路
JP2017070192A (ja) * 2015-09-28 2017-04-06 サンケン電気株式会社 スイッチング電源装置及びｌｅｄ点灯回路

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