WO2018141283A1 - 一种无桥pfc电路 - Google Patents

一种无桥pfc电路 Download PDF

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Publication number
WO2018141283A1
WO2018141283A1 PCT/CN2018/075243 CN2018075243W WO2018141283A1 WO 2018141283 A1 WO2018141283 A1 WO 2018141283A1 CN 2018075243 W CN2018075243 W CN 2018075243W WO 2018141283 A1 WO2018141283 A1 WO 2018141283A1
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Prior art keywords
switch
bridge arm
autotransformer
output
circuit
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PCT/CN2018/075243
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English (en)
French (fr)
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胡永辉
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中兴通讯股份有限公司
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Publication of WO2018141283A1 publication Critical patent/WO2018141283A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H02M1/15—Arrangements for reducing ripples from dc input or output using active elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present disclosure relates to the field of power electronics, and in particular to a bridgeless power factor correction (PFC) circuit.
  • PFC power factor correction
  • the topology of the currently popular AC-DC converter is bridgeless PFC.
  • the industry derives various improved bridgeless PFC topologies from the traditional bridgeless PFC topology.
  • the inductor ripple current of the boost inductor is large and the inductor volume is large; The current value of the switching tube is large, and the circuit conversion efficiency is low. Therefore, the bridgeless PFC circuit in the related art has low conversion efficiency and power density.
  • Embodiments of the present disclosure provide a bridgeless PFC circuit.
  • the present disclosure provides a bridgeless PFC circuit including: an AC power source, a boost inductor, an autotransformer, at least two sets of switch bridge arms, and a bus capacitor; each set of the switch bridge arm includes a bridge arm midpoint and At least two bridge arm ends; the autotransformer includes at least two output terminals; one end of the boost inductor is connected to the alternating current power source, and the other end is connected to an input end of the autotransformer; the autotransformer Each output terminal is connected to a midpoint of a bridge arm of one of the switch bridge arms, and the arm end points of each set of the switch bridge arms are respectively connected to different end points of the bus bar capacitor.
  • the switch bridge arm includes at least one of a two-level bridge arm, a T-type three-level bridge arm, and an NPC-type three-level bridge arm.
  • each output end of the autotransformer forms a coil number equal to the input end.
  • the switch in the switch bridge arm includes at least one of a diode, a metal oxide semiconductor (MOS) transistor, a transistor, and a junction field effect transistor.
  • MOS metal oxide semiconductor
  • the number of sets of the switch bridge arms is N
  • the phase difference between the drive signals for driving the switch arms of each group is 360/N degrees, wherein N is an integer greater than 1.
  • the bus capacitor includes at least one output capacitor group; each of the output capacitor groups is connected in parallel with each other; wherein each of the output capacitor groups includes two output capacitors connected in series.
  • one end of the AC power source is connected to one end of the boosting inductor, and the other end is connected to a series connection point of two output capacitors in each output capacitor group; Connected to two end points of each of the output capacitor groups.
  • embodiments of the present disclosure also provide a bridgeless PFC circuit comprising three sets of any of the above-described bridgeless PFC circuits provided by the present disclosure.
  • the phases of the three sets of AC power sources are different by 120 degrees.
  • the bridgeless PFC circuit provided by the embodiment of the present disclosure solves the problem of low conversion efficiency and low power density of the bridgeless PFC circuit in the related art.
  • the switch bridge arm When the switch bridge arm is opened or closed to convert the alternating current into direct current, the communication is performed.
  • the boost inductor experiences at least two charges and at least two discharges during each change cycle of the signal.
  • the increase of the charge and discharge frequency effectively reduces the current ripple of the boost inductor and the bus capacitor, and also flows through the switch bridge arm.
  • the current value of the middle switch tube is smaller, thereby improving the power conversion efficiency; and, since the ripple frequency on the boost inductor is at least twice the switching frequency, the inductance of the boost inductor can also be reduced by a corresponding multiple. Therefore, the boost inductor has a smaller volume and a higher power density, which effectively improves power conversion efficiency and power density.
  • FIG. 1 is a schematic structural diagram of a bridgeless PFC circuit according to an embodiment of the present disclosure
  • FIG. 2 is another schematic structural diagram of a bridgeless PFC circuit according to an embodiment of the present disclosure
  • FIG. 3 is a schematic structural diagram of still another bridgeless PFC circuit according to an embodiment of the present disclosure.
  • FIG. 4 is a schematic structural view of a bidirectional switch in the bridgeless PFC circuit shown in FIG. 3;
  • FIG. 5 is a schematic structural diagram of still another bridgeless PFC circuit according to an embodiment of the present disclosure.
  • FIG. 6 is a schematic structural diagram of a three-phase bridgeless PFC circuit according to an embodiment of the present disclosure
  • FIG. 7 is another schematic structural diagram of a three-phase bridgeless PFC circuit according to an embodiment of the present disclosure.
  • FIG. 8 is still another schematic structural diagram of a three-phase bridgeless PFC circuit according to an embodiment of the present disclosure.
  • Embodiments of the present disclosure provide a bridgeless PFC circuit, including:
  • An AC power source a boost inductor, an autotransformer, at least two sets of switch bridge arms, and a bus capacitor; each set of switch bridge arms includes a bridge arm midpoint and at least two bridge arm end points; the autotransformer includes at least two outputs One end of the boosting inductor is connected to the alternating current power source, and the other end is connected to an input end of the autotransformer; each output end of the autotransformer is in a bridge arm of one of the switch bridge arms Connected to the points, the end points of the bridge arms of the switch arms of each group are respectively connected to different end points of the bus capacitor.
  • the bridgeless PFC circuit when the driving switch arm is opened or closed to convert the alternating current into direct current, the boosting inductor experiences at least two charging and at least two times in each variation period of the alternating current signal. Discharge, the increase of the charge and discharge frequency effectively reduces the current ripple of the boost inductor and the bus capacitor, and also makes the current effective value of the switch flowing through the switch bridge arm smaller, thereby improving the power conversion efficiency;
  • the ripple frequency on the boost inductor is at least twice the switching frequency, so the sense of the boost inductor can also be reduced by a corresponding multiple, resulting in a smaller boost inductor and higher power density, which effectively improves power conversion. Efficiency and power density.
  • the switch bridge arm in this embodiment may include multiple bridge arms in the switch bridge, which may be a two-level bridge arm, or a T-type three-level bridge arm or an NPC-type three-level bridge.
  • the arms can also be a combination of these bridge arms.
  • the switches in each set of the switching bridge arms may include one or more of a diode, a MOS transistor, a transistor, and a junction field effect transistor. The embodiments of the present disclosure do not limit this.
  • the bus capacitor may alternatively include an output capacitor group or a plurality of output capacitor groups;
  • the output capacitor groups are connected in parallel with each other; wherein each output capacitor group includes two output capacitors connected in series with each other.
  • One end of the AC power source may be connected to one end of the boost inductor, and the other end is connected to a series connection point of two output capacitors in each output capacitor group; the end points of the bridge arms of each group of the switch bridge arms and the output capacitor group respectively The two endpoints are connected.
  • the number of turns formed by each output and input of the autotransformer may be equal or unequal.
  • the boosting inductance is symmetric with respect to the charging and discharging processes of the positive and negative half axes of the alternating current.
  • the boosting inductance is positive and negative half of the alternating current.
  • the charging and discharging processes are asymmetrical. This embodiment can be applied to application fields such as a communication power supply including an AC/DC conversion circuit, an industrial power supply, a UPS, and a motor drive.
  • the bridgeless PFC circuit of the embodiment of the present disclosure may include: two sets of switch bridge arms and autotransformers composed of switches S1 , S2 , S3 , and S4 .
  • boost inductor L1 bus capacitor composed of one output capacitor group C1, C2, AC grid; midpoint of switch bridge arm composed of switches S1, S2 and first output end of autotransformer T1 (ie, auto-coupling) a coil of the transformer T is connected; the midpoint of the switch bridge formed by the switches S3, S4 is connected to the second output of the autotransformer T1 (ie the other coil of the autotransformer T); One end of the arm is connected to one end of the output capacitor C1; the other end of the two sets of the switch bridge arm is connected to one end of the output capacitor C2; the input end of the autotransformer T1 (center tap) is connected to one end of the boost inductor L1, The other end of the piezoelectric inductor L1 is connected to one end of the AC grid; the other end of the AC grid is connected to the connection point of the output capacitors C1 and C2.
  • the number of turns of the two coils of the autotransformer T1 may be equal or unequal. In the case where the number of turns of the two coils of the autotransformer T1 is equal, the charging and discharging processes of the current in two directions are symmetrical.
  • the boosting inductor L1, the autotransformer T1, the switches S2, and S4 form a three-state switching unit circuit, including the switches S2 and S4 being simultaneously turned on, simultaneously turned off, and turned on. The same is true for one disconnection of three states.
  • the boost inductor L1, the autotransformer T1, the switches S1 and S3 also constitute a three-state switching unit circuit. Alternatively, these three states can be achieved by conventional pulse width modulation control.
  • switches S1 and S2 are controlled by the same set of pulse width modulation signals, but the control signals are in opposite directions
  • switches S3 and S4 are controlled by the same set of pulse width modulation signals, but the control signals are in opposite directions, between switches S1 and S2, switch S3 and The phase between S4 differs by 180°.
  • the magnitudes of the alternating current and the alternating current are constantly changing.
  • the duty ratio of the closed state of each switch under the pulse width modulation control is also Will be in constant change.
  • the switches S2 and S4 may be simultaneously turned on, simultaneously turned off, and turned on and off one state.
  • the pulse width modulated (PWM) carrier signals of switches S2, S4 are sawtooth waves that are 180 degrees out of phase, and the duty cycle signals of the PWM are given by a bridgeless PFC control circuit.
  • PWM pulse width modulated
  • the two coils of autotransformer T1 are connected to the bus voltage by switches S2 and S3.
  • the voltage on the center tap of autotransformer T1 that is, the output of boost inductor L1.
  • the voltage at the negative terminal of the bus is half the bus voltage.
  • the boost inductor L1 may be in a state of charge or may be in a discharged state depending on the instantaneous value of the AC input grid voltage.
  • both charging and discharging can increase the boost inductor L1 by one charge and discharge process, which is beneficial to reduce the current ripple of the boost inductor and the bus capacitor.
  • the boost inductor L1 may be in a state of charge or may be in a discharged state depending on the instantaneous value of the AC input grid voltage.
  • the three-state switching unit circuit In the negative half cycle of the AC input power grid, the three-state switching unit circuit also has the above three working states, and the principle thereof is the same as the working state in the positive half cycle, and details are not described herein again.
  • the boosting inductor undergoes two charging and discharging in one switching cycle, thereby reducing the current pattern of the boosting inductor and the busbar capacitor.
  • the current flowing through the switch tube has a smaller effective value, which improves the conversion efficiency; and the ripple frequency on the boost inductor is twice the switching frequency, so the inductance of the boost inductor can be reduced by half, and the boost inductor The smaller the volume, the higher the power density, thus solving the problem of lower conversion efficiency and lower power density of the related art.
  • the bus capacitance includes an output capacitor group (including output capacitors C1, C2), but embodiments of the present disclosure are not limited thereto. In other embodiments of the present disclosure, a plurality of output capacitor banks may be included, each of which is connected in parallel with each other.
  • the above embodiment employs two sets of switch bridge arms, but the disclosure is not limited thereto.
  • three or more switch bridge arms may be adopted, assuming that the number of sets of the switch bridge arms is N, driving the phase between the drive signals of the switch arms of each group The difference is 360/N degrees, where N is an integer greater than one.
  • N is an integer greater than one.
  • the phase difference between the drive signals for driving the switch arm switches of each group is 90 degrees.
  • the boost inductor experiences three or more charges and discharges in one AC cycle, and the ripple frequency on the boost inductor is three times the switching frequency. Or more times, so the inductance of the boost inductor can be further reduced, the boost inductor is smaller, and a higher power density is obtained.
  • Figure 2 is another bridgeless PFC circuit of an embodiment of the present disclosure.
  • the bridgeless PFC circuit provided in this embodiment may include:
  • Three sets of switch bridge arms composed of switches S1, S2, S3, S4, S5, S6, autotransformer T1, boost inductor L1, output capacitor group (busbar capacitor) composed of output capacitors C1 and C2, and an AC grid;
  • the midpoint of the switch bridge arm formed by the switches S1, S2 is connected to one coil of the autotransformer T1; the midpoint of the switch bridge arm formed by the switches S3, S4 is connected to the other coil of the autotransformer T1; by the switch S5
  • the midpoint of the switch bridge arm formed by S6 is connected to another coil of the autotransformer T1; one end of the three sets of the switch bridge arm is connected to one end of the output capacitor C1; and the other end of the three sets of the switch bridge arm is One end of the output capacitor C2 is connected; the center tap of the autotransformer T1 is connected to the output end of the boost inductor L1, and the input end of the boost inductor L1 is connected to one end of the AC grid; One end is connected to the connection
  • the ripple frequency on the boost inductor is three times the switching frequency, so the inductance of the boost inductor can be further reduced, and the boost inductor is smaller. , to obtain higher power density.
  • the bridge arms in the switch bridge are two-level bridge arms, but the disclosure is not limited thereto. Other forms of bridge arms may also be employed in other embodiments of the present disclosure.
  • the embodiment of the present disclosure further provides a bridgeless PFC circuit, including: two sets of T-type three-level switch bridge arms composed of switches S1, S2, S3, S4, S5, and S6. , an autotransformer T1, a boost inductor L1, an output capacitor bank (busbar capacitor) composed of two output capacitors C1 and C2, an AC grid; a midpoint of the switch bridge arm composed of switches S1, S2, and S5 and an autotransformer One coil of T1 is connected; the midpoint of the switch bridge arm composed of switches S3, S4, and S6 is connected to the other coil of the autotransformer T1; one end of the two sets of the T-type three-level switch bridge arm and the output capacitor C1 One end of the T-type three-level switch bridge arm is connected to one end of the output capacitor C2; the third end of the two sets of the T-type three-level switch bridge arm is connected to two output capacitors C1 a connection point of C2; the center tap of the autotransformer
  • the bidirectional switch is represented by K.
  • the bidirectional switch K may include a diode, a MOS transistor, a crystal triode, one or more of three kinds of switching devices, and may be combined in combination, and of course other transistors may be used.
  • Formed as a form of JFET. 4a to 4f show an implementation in which a diode, a MOS transistor, and a transistor are combined to form a bidirectional switch.
  • an embodiment of the present disclosure also provides another bridgeless PFC circuit.
  • the bridgeless PFC circuit of the embodiment of the present disclosure includes:
  • the above embodiments are all for a single-phase AC power bridgeless PFC circuit. Based on the circuit provided in the above embodiment, a bridgeless PFC circuit for multi-phase AC power can also be formed.
  • an embodiment of the present disclosure further provides a bridgeless PFC circuit, including three sets of any of the bridgeless PFC circuits provided in the foregoing embodiments.
  • the three groups of AC power sources have a phase difference of 120 degrees.
  • FIG. 6 another bridgeless PFC circuit of an embodiment of the present disclosure.
  • the bridgeless PFC circuit of the embodiment of the present disclosure includes: three sets of three-phase neutral line bridgeless PFC circuits composed of three bridgeless PFC circuits as shown in FIG. The specific structure and working principle have been described in detail in the foregoing, and will not be described here.
  • FIG. 7 is a bridgeless PFC circuit according to an embodiment of the present disclosure.
  • the bridgeless PFC circuit of the embodiment of the present disclosure includes three sets of three-phase band-free PFC circuits composed of a bridgeless PFC circuit as shown in FIG.
  • the specific structure and working principle have been described in detail in the foregoing, and will not be described here.
  • FIG. 8 is another bridgeless PFC circuit according to an embodiment of the present disclosure.
  • the bridgeless PFC circuit of the embodiment of the present disclosure includes: three sets of three-phase band-lined bridgeless PFC circuits composed of three bridgeless PFC circuits as shown in FIG. 5. The specific structure and working principle have been described in detail in the foregoing, and will not be described here.
  • the solution provided by the embodiment of the present disclosure provides that when the driving switch arm is opened or closed to convert the alternating current into direct current, the boosting inductor experiences at least two charging and at least two discharging during each change period of the alternating current signal.
  • the increase of the discharge frequency effectively reduces the current ripple of the boost inductor and the bus capacitor, and also reduces the current effective value of the current flowing through the switch tube in the switch bridge arm, thereby improving the power conversion efficiency; and, due to the boost inductor
  • the ripple frequency is at least twice the switching frequency, so the inductance of the boost inductor can also be reduced by a corresponding multiple, so that the boost inductor has a smaller volume and higher power density, which effectively improves the power conversion efficiency and power. density.

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Abstract

一种无桥PFC电路，包括：交流电源（AC）、升压电感（L1）、自耦变压器（T1）、至少两组开关桥臂、母线电容（C1、C2）；每组开关桥臂包括一个桥臂中点和至少两个桥臂端点；自耦变压器包括至少两个输出端；升压电感一端与交流电源相连，另一端与自耦变压器的输入端相连；自耦变压器的每个输出端都与其中一组开关桥臂的桥臂中点相连，各组开关桥臂的桥臂端点分别与母线电容的不同端点相连。该PFC电路能够提高电路的转换效率和功率密度。

Description

一种无桥PFC电路
相关申请的交叉引用
本申请基于申请号为201710064266.6、申请日为2017年02月04日的中国专利申请提出，并要求该中国专利申请的优先权，该中国专利申请的全部内容在此引入本申请作为参考。
技术领域
本公开涉及电力电子技术领域，特别是涉及一种无桥功率因数校正(PFC，Power Factor Correction)电路。
背景技术
在电力电子交流整流技术领域，特别是PFC，目前比较流行的AC-DC变换器的拓扑为无桥PFC。业界从传统的无桥PFC拓扑衍生出各种改进型的无桥PFC拓扑，然而相关技术中的交错并联无桥PFC电路中升压电感的电感纹波电流大，电感体积大；同时，流过开关管的电流有效值大，电路转换效率低。因此，相关技术中的无桥PFC电路转换效率和功率密度较低。
发明内容
本公开实施例提供一种无桥PFC电路。
一方面，本公开提供一种无桥PFC电路，包括：交流电源、升压电感、自耦变压器、至少两组开关桥臂、母线电容；每组所述开关桥臂包括一个桥臂中点和至少两个桥臂端点；所述自耦变压器包括至少两个输出端；所述升压电感一端与所述交流电源相连，另一端与所述自耦变压器的输入端相连；所述自耦变压器的每个输出端都与其中一组开关桥臂的桥臂中点相 连，各组所述开关桥臂的桥臂端点分别与所述母线电容的不同端点相连。
上述方案中，所述开关桥臂包括两电平桥臂、T型三电平桥臂、NPC型三电平桥臂中的至少一种。
上述方案中，所述自耦变压器的每个输出端与输入端形成线圈匝数相等。
上述方案中，所述开关桥臂中的开关包括二极管、金属氧化物半导体(MOS，Metal Oxide Semiconductor)管、晶体三极管，结型场效应晶体管中的至少一种。
上述方案中，所述开关桥臂的组数为N，驱动各组所述开关桥臂开关动作的驱动信号之间的相位差为360/N度，其中，N为大于1的整数。
上述方案中，所述母线电容包括至少一个输出电容组；各所述输出电容组之间相互并联；其中，每个所述输出电容组包括相互串联的两个输出电容。
上述方案中，所述交流电源一端与所述升压电感的一端相连，另一端与各输出电容组中两个输出电容的串联连接点分别相连；各组所述开关桥臂的桥臂端点分别与各所述输出电容组的两个端点相连。
另一方面，本公开的实施例还提供一种无桥PFC电路，包括三组本公开提供的上述任一种无桥PFC电路。
上述方案中，三组交流电源的相位相差120度。
本公开实施例提供的无桥PFC电路，用以解决相关技术中无桥PFC电路转换效率和功率密度较低的问题，当驱动开关桥臂的断开或闭合将交流电转换成直流电时，在交流信号的每个变化周期内升压电感会经历至少两次充电和至少两次放电，充放电频率的增加有效减小了升压电感和母线电容的电流纹波，同时也使流经开关桥臂中开关管的电流有效值更小，从而提高了电源转换效率；而且，由于升压电感上的纹波频率为开关频率的至 少两倍，所以升压电感的感量也可以减小相应的倍数，从而使升压电感体积更小，功率密度更高，有效提高了电源转换效率和功率密度。
附图说明
图1是本公开实施例提供的无桥PFC电路的一种结构示意图；
图2是本公开实施例提供的无桥PFC电路的另一种结构示意图；
图3是本公开实施例提供的无桥PFC电路的又一种结构示意图；
图4是图3所示的无桥PFC电路中的双向开关的一种结构示意图；
图5是本公开实施例提供的无桥PFC电路的再一种结构示意图；
图6是本公开实施例提供的三相无桥PFC电路的一种结构示意图；
图7是本公开实施例提供的三相无桥PFC电路的另一种结构示意图；
图8是本公开实施例提供的三相无桥PFC电路的又一种结构示意图。
具体实施方式
以下结合附图对本公开进行详细说明。应当理解，此处所描述的具体实施例仅仅用以解释本公开，并不限定本公开。
本公开实施例提供一种无桥PFC电路，包括：
交流电源、升压电感、自耦变压器、至少两组开关桥臂、母线电容；每组开关桥臂包括一个桥臂中点和至少两个桥臂端点；所述自耦变压器包括至少两个输出端；所述升压电感一端与所述交流电源相连，另一端与所述自耦变压器的输入端相连；所述自耦变压器的每个输出端都与其中一组开关桥臂的桥臂中点相连，各组所述开关桥臂的桥臂端点分别与所述母线电容的不同端点相连。
本公开实施例提供的无桥PFC电路，当驱动开关桥臂的断开或闭合将交流电转换成直流电时，在交流信号的每个变化周期内升压电感会经历至少两次充电和至少两次放电，充放电频率的增加有效减小了升压电感和母 线电容的电流纹波，同时也使流经开关桥臂中开关管的电流有效值更小，从而提高了电源转换效率；而且，由于升压电感上的纹波频率为开关频率的至少两倍，所以升压电感的感量也可以减小相应的倍数，从而使升压电感体积更小，功率密度更高，有效提高了电源转换效率和功率密度。
可选地，本实施例中的开关桥臂可包括开关电桥中的多种桥臂，既可以是两电平桥臂，也可以是T型三电平桥臂或NPC型三电平桥臂，还可以是这些桥臂的组合。每组所述开关桥臂中的开关可以包括二极管、MOS管、晶体三极管，结型场效应晶体管中的一种或几种。本公开的实施例对此不作限定。
在一实施例中，由于交流电具有正负之分，为了对两个方向的电流进行更有效的整流和滤波，可选地，母线电容可以包括一个输出电容组或者多个输出电容组；各所述输出电容组之间相互并联；其中，每个输出电容组包括相互串联的两个输出电容。交流电源一端可以与升压电感的一端相连，另一端与各输出电容组中两个输出电容的串联连接点分别相连；各组所述开关桥臂的桥臂端点分别与各所述输出电容组的两个端点相连。
可选地，自耦变压器的每个输出端与输入端形成的线圈匝数可以相等也可以不等。当各线圈匝数相等时，升压电感对于交流电的正半轴和负半轴的充、放电过程对称，当各线圈匝数不相等时，升压电感对于交流电的正半轴和负半轴的充、放电过程不对称。本实施例可应用于包含AC/DC转换电路的通信电源、工业电源、UPS、电机驱动等应用领域。
举例说明，如图1所示，在本公开的一个实施例中，本公开实施例的无桥PFC电路可包括：由开关S1、S2、S3、S4构成的两组开关桥臂、自耦变压器T1、升压电感L1、由一个输出电容组C1、C2构成的母线电容、交流电网；由开关S1、S2构成的开关桥臂的中点与自耦变压器T1的第一输出端(即自耦变压器T的一个线圈)相连；由开关S3、S4构成的开关桥 臂的中点与自耦变压器T1的第二输出端(即自耦变压器T的另一个线圈)相连；两组所述开关桥臂的一端与输出电容C1的一端相连；两组所述开关桥臂的另一端与输出电容C2的一端相连；自耦变压器T1的输入端(中心抽头)和升压电感L1的一端相连，升压电感L1的另一端连接至交流电网的一端；交流电网的另一端连接至输出电容C1和C2的连接点。可选地，自耦变压器T1的两个线圈匝数可以相等也可以不等。在自耦变压器T1的两个线圈匝数相等的情况下，电流沿两个方向的充、放电过程相对称。
本公开实施例的无桥PFC电路中，由升压电感L1、自耦变压器T1、开关S2、S4构成了三态开关单元电路，包括开关S2、S4同时导通、同时断开、一个导通一个断开三种状态，同样道理，由升压电感L1、自耦变压器T1、开关S1和S3也构成了三态开关单元电路。可选地，可以通过常用的脉冲宽度调制控制实现这三种状态。其中，开关S1和S2由同一组脉冲宽度调制信号控制，但控制信号方向相反，开关S3和S4由同一组脉冲宽度调制信号控制，但控制信号方向相反，开关S1和S2之间，开关S3和S4之间相位分别相差180°。
具体地，在交流电的一个周期内，交流电流和交流电压的大小处于随时变化之中，为了维持直流输出电压和电流的恒定，处于脉冲宽度调制控制下的各个开关的闭合状态的占空比也会处于不断的变化中。而在各个开关的占空比不断变化的过程中，可能出现开关S2、S4同时导通、同时断开、一个导通一个断开三种状态。
以下详细说明三种状态的工作原理。
在交流输入电网的正半周期中，状态一：
开关S2、S4的脉冲宽度调制(PWM)载波信号为相位相差180度的锯齿波，并且该PWM的占空比信号由无桥PFC控制电路给出。当开关S2、S4的工作占空比大于50％的时候，开关S2、S4存在同时导通的状态。此 时，自耦变压器T1的两个线圈被开关S2、S4短路，交流输入电网给升压电感L1充电。
状态二：
当开关S2导通，开关S4断开时，自耦变压器T1的两个线圈被开关S2、S3连接到母线电压，此时自耦变压器T1中心抽头上的电压，即升压电感L1的输出端对母线负端的电压为一半的母线电压。升压电感L1可能处于充电状态，也可能处于放电状态，这取决于交流输入电网电压的瞬时值。但无论是充电和是放电，都可以使升压电感L1增加了一次充放电过程，有利于减小升压电感和母线电容的电流纹波。
当开关S2断开，开关S4导通时，自耦变压器T1的两个线圈被开关S1、S4连接到母线电压，此时自耦变压器T1中心抽头上的电压，即升压电感L1的输出端对母线负端的电压为一半的母线电压。升压电感L1可能处于充电状态，也可能处于放电状态，这取决于交流输入电网电压的瞬时值。
状态三：
当开关S2、S4的工作占空比小于50％的时候，开关S2、S4存在同时断开的状态。此时，自耦变压器T1的两个线圈被开关S1、S3短路，升压电感L1处于放电状态。
在交流输入电网的负半周期中，三态开关单元电路也有上述三种工作状态，其原理与正半周期中的工作状态相同，此处不再赘述。
采用上述技术方案后，当采用两组开关桥臂构成无桥PFC电路时，在一个开关周期内，升压电感经历了两次充电和放电，因此减小了升压电感和母线电容的电流纹波，流经开关管的电流有效值更小，提高了转换效率；并且，升压电感上的纹波频率为开关频率的两倍，所以升压电感的感量可以减小一半，升压电感体积更小，获得更高的功率密度，因此解决了相关 技术的转换效率和功率密度较低的问题。
需要说明的是，本实施例中，母线电容包括一个输出电容组(包括输出电容C1、C2)，但本公开的实施例不限于此。在本公开的其他实施例中，可以包括多个输出电容组，各输出电容组之间相互并联。
还需要说明的是，上述实施例采用了两组开关桥臂，但本公开不限于此。在本公开的其他实施例中，可以采取三组或者更多的开关桥臂，假设所述开关桥臂的组数为N，驱动各组所述开关桥臂开关动作的驱动信号之间的相位差为360/N度，其中，N为大于1的整数。例如，如果采用四组开关桥臂，驱动各组所述开关桥臂开关动作的驱动信号之间的相位差为90度。在采用三组或者更多的开关桥臂的情况下，在一个交流周期内，升压电感会经历三次或者更多次的充电和放电，升压电感上的纹波频率为开关频率的三倍或者更多倍，所以升压电感的感量可以进一步减小，升压电感体积更小，获得更高的功率密度。
例如，图2为本公开实施例的另一种无桥PFC电路。如图2所示，本实施例提供的无桥PFC电路可包括：
由开关S1、S2、S3、S4、S5、S6构成的三组开关桥臂、自耦变压器T1、升压电感L1、由输出电容C1和C2构成的输出电容组(母线电容)、交流电网；由开关S1、S2构成的开关桥臂的中点与自耦变压器T1的一个线圈相连；由开关S3、S4构成的开关桥臂的中点与自耦变压器T1的另一个线圈相连；由开关S5、S6构成的开关桥臂的中点与自耦变压器T1的又另一个线圈相连；三组所述开关桥臂的一端与输出电容C1的一端相连；三组所述开关桥臂的另一端与输出电容C2的一端相连；所述自耦变压器T1的中心抽头和所述升压电感L1的输出端相连，所述升压电感L1的输入端连接至交流电网的一端；所述交流电网的另一端连接至两个输出电容C1和C2的连接点。优选的，所述自耦变压器T1的三个原边绕组和三个副边绕 组的线圈匝数相等。
由于在一个开关周期内，升压电感会经历三次充电和放电，升压电感上的纹波频率为开关频率的三倍，所以升压电感的感量可以进一步减小，升压电感体积更小，获得更高的功率密度。
图1和图2所示的实施例中，开关电桥中的桥臂为两电平桥臂，但本公开不限于此。在本公开的其他实施例中还可以采用其他形式的桥臂。
具体而言，如图3所示，本公开实施例还提供一种无桥PFC电路，包括：由开关S1、S2、S3、S4、S5、S6构成的两组T型三电平开关桥臂、自耦变压器T1、升压电感L1、两个输出电容C1和C2构成的输出电容组(母线电容)、交流电网；由开关S1、S2、S5构成的开关桥臂的中点与自耦变压器T1的一个线圈相连；由开关S3、S4、S6构成的开关桥臂的中点与自耦变压器T1的另一个线圈相连；两组所述T型三电平开关桥臂的一端与输出电容C1的一端相连；两组所述T型三电平开关桥臂的另一端与输出电容C2的一端相连；两组所述T型三电平开关桥臂的第三端连接至两个输出电容C1和C2的连接点；所述自耦变压器T1的中心抽头和所述升压电感L1的输出端相连，所述升压电感L1的输入端连接至交流电网的一端；所述交流电网的另一端连接至两个输出电容C1和C2的连接点。其中，所述开关S5、S6为双向开关。
图4是本公开实施例的双向开关的实施方式示意图。参见图4，双向开关用K代表，可选地，双向开关K可包括二极管、MOS管、晶体三极管，三种开关器件的一种或多种，以组合形式构成，当然也可以采用其它晶体管(如JFET)的形式构成。图4a～图4f为二极管、MOS管、晶体三极管以组合构成双向开关的实现方式。
如图5所示，本公开实施例还提供另一种无桥PFC电路。本公开实施例的无桥PFC电路包括：
由开关S1、S2、S3、S4、S5、S6、S7、S8和二极管D1、D2、D3、D4、D5、D6、D7、D8、D9、D10、D11、D12构成的两组NPC型三电平开关桥臂、自耦变压器T1、升压电感L1、输出电容C1和C2、交流电网；由开关S1、S2、S3、S4、D1、D2、D3、D4、D5、D6构成的开关桥臂的中点与自耦变压器T1的一个线圈相连；由开关S5、S6、S7、S8、D7、D8、D9、D10、D11、D12构成的开关桥臂的中点与自耦变压器T1的另一个线圈相连；两组所述NPC型三电平开关桥臂的一端与输出电容C1的一端相连；两组所述NPC型三电平开关桥臂的另一端与输出电容C2的一端相连；两组所述NPC型三电平开关桥臂的箝位二极管(D5、D6和D11、D12)的中点连接至输出电容C1和C2的连接点；所述自耦变压器T1的中心抽头和所述升压电感L1的输出端相连，所述升压电感L1的输入端连接至交流电网的一端；所述交流电网的另一端连接至两组母线电容C1和C2的连接点。所述二极管D1、D2、D3、D4、D7、D8、D9、D10可以是开关管的体二极管或者外置二极管。
进一步地，上述实施例都是针对单相交流电的无桥PFC电路，基于上面实施例提供的电路，还可以形成针对多相交流电的无桥PFC电路。
可选的，本公开的实施例还提供一种无桥PFC电路，包括三组上述实施例中提供的任一种无桥PFC电路。其中，三组交流电源的相位相差120度。
举例说明，参见图6，本公开实施例的另一种无桥PFC电路。本公开实施例的无桥PFC电路包括：三组如图1所示的无桥PFC电路构成的三相带中线的无桥PFC电路。其具体结构和工作原理已经在前文进行了详细说明，此处不再赘述。
参见图7，图7为本公开实施例的一种无桥PFC电路。本公开实施例的无桥PFC电路包括：三组如图3所示的无桥PFC电路构成的三相带中线 的无桥PFC电路。其具体结构和工作原理已经在前文进行了详细说明，此处不再赘述。
参见图8，图8为本公开实施例的另一种无桥PFC电路。本公开实施例的无桥PFC电路包括：三组如图5所示的无桥PFC电路构成的三相带中线的无桥PFC电路。其具体结构和工作原理已经在前文进行了详细说明，此处不再赘述。
需要说明的是，在本文中，术语“包括”、“包含”或者其任何其他变体意在涵盖非排他性的包含，从而使得包括一系列要素的过程、方法、物品或者装置不仅包括那些要素，而且还包括没有明确列出的其他要素，或者是还包括为这种过程、方法、物品或者装置所固有的要素。在没有更多限制的情况下，由语句“包括一个……”限定的要素，并不排除在包括该要素的过程、方法、物品或者装置中还存在另外的相同要素。
通过以上的实施方式的描述，本领域的技术人员可以清楚地了解到上述实施例方法可借助软件加必需的通用硬件平台的方式来实现，当然也可以通过硬件，但很多情况下前者是更佳的实施方式。基于这样的理解，本公开的技术方案本质上或者说对现有技术做出贡献的部分可以以软件产品的形式体现出来，该计算机软件产品存储在一个存储介质(如ROM/RAM、磁碟、光盘)中，包括若干指令用以使得一台终端设备(可以是手机，计算机，服务器，空调器，或者网络设备等)执行本公开各个实施例所述的方法。
以上仅为本公开的优选实施例，并非因此限制本公开的专利范围，凡是利用本公开说明书及附图内容所作的等效结构或等效流程变换，或直接或间接运用在其他相关的技术领域，均同理包括在本公开的专利保护范围内。
工业实用性
本公开实施例提供的方案，当驱动开关桥臂的断开或闭合将交流电转换成直流电时，在交流信号的每个变化周期内升压电感会经历至少两次充电和至少两次放电，充放电频率的增加有效减小了升压电感和母线电容的电流纹波，同时也使流经开关桥臂中开关管的电流有效值更小，从而提高了电源转换效率；而且，由于升压电感上的纹波频率为开关频率的至少两倍，所以升压电感的感量也可以减小相应的倍数，从而使升压电感体积更小，功率密度更高，有效提高了电源转换效率和功率密度。

Claims (9)

  1. 一种无桥PFC电路，包括：
    交流电源、升压电感、自耦变压器、至少两组开关桥臂、母线电容；每组所述开关桥臂包括一个桥臂中点和至少两个桥臂端点；所述自耦变压器包括至少两个输出端；
    所述升压电感一端与所述交流电源相连，另一端与所述自耦变压器的输入端相连；
    所述自耦变压器的每个输出端都与其中一组开关桥臂的桥臂中点相连，各组所述开关桥臂的桥臂端点分别与所述母线电容的不同端点相连。
  2. 根据权利要求1所述的电路，其中，所述开关桥臂包括两电平桥臂、T型三电平桥臂、NPC型三电平桥臂中的至少一种。
  3. 根据权利要求1所述的电路，其中，所述自耦变压器的每个输出端与输入端形成线圈匝数相等。
  4. 根据权利要求1所述的电路，其中，所述开关桥臂中的开关包括二极管、MOS管、晶体三极管，结型场效应晶体管中的至少一种。
  5. 根据权利要求1所述的电路，其中，所述开关桥臂的组数为N，驱动各组所述开关桥臂开关动作的驱动信号之间的相位差为360/N度，其中，N为大于1的整数。
  6. 根据权利要求1至5中任一项所述的电路，其中，所述母线电容包括至少一个输出电容组；各所述输出电容组之间相互并联；其中，每个所述输出电容组包括相互串联的两个输出电容。
  7. 根据权利要求6所述的电路，其中，所述交流电源一端与所述升压电感的一端相连，另一端与各输出电容组中两个输出电容的串联连接点分别相连；
    各组所述开关桥臂的桥臂端点分别与各所述输出电容组的两个端点相 连。
  8. 一种无桥PFC电路，包括三组权利要求1-7任一项所述的无桥PFC电路。
  9. 根据权利要求8所述的电路，其中，三组交流电源的相位相差120度。
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Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112787497A (zh) * 2021-01-28 2021-05-11 三峡大学 一种带z型桥结构的单相三电平功率因数校正电路
CN112865569A (zh) * 2021-01-28 2021-05-28 三峡大学 一种混合t型桥的单相三电平整流器
CN112865565A (zh) * 2021-01-28 2021-05-28 三峡大学 一种对称t型桥的双开关三电平整流器
EP3876388A1 (en) * 2020-03-03 2021-09-08 Delta Electronics, Inc. Method for operating power factor correction circuit and method for operating uninterruptible power supply apparatus
WO2021213676A1 (en) * 2020-04-24 2021-10-28 Huawei Technologies Co., Ltd. Bridgeless single-phase pfc multi-level totem-pole power converter
WO2021247008A1 (en) * 2020-06-02 2021-12-09 Innovative Power Solutions, Llc Adaptive power factor correction (pfc) controller

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111654196B (zh) * 2020-04-16 2021-09-28 山西大学 一种电容分压的改进无桥双Boost功率因数校正整流器
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CN116131651A (zh) * 2022-09-09 2023-05-16 深圳深源技术能源有限公司 一种三相ac-dc双向变换电路

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20100171480A1 (en) * 2009-01-06 2010-07-08 Yang Ye Method and apparatus of a unified control solution for bridgeless power factor controllers and grid connected inverters
CN101860192A (zh) * 2010-03-30 2010-10-13 艾默生网络能源有限公司 一种三态三电平pfc电路及多态三电平pfc电路
CN101860189A (zh) * 2009-04-13 2010-10-13 台达电子工业股份有限公司 用于临界连续电流模式的无桥功率因数校正电路及其方法

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP2422441A4 (en) * 2010-05-24 2013-04-03 Huawei Tech Co Ltd METHOD AND DEVICE FOR POWER GENERATION
WO2012106862A1 (zh) * 2011-07-01 2012-08-16 华为技术有限公司 功率因数校正转换器以及功率因数校正转换设备
CN103580502A (zh) * 2013-11-15 2014-02-12 华为技术有限公司 电源转换电路及控制直流-交流电路的方法
WO2016105272A1 (en) * 2014-12-23 2016-06-30 Robert Bosch (Sea) Pte. Ltd. Balancing circuit and inverter comprising the same

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20100171480A1 (en) * 2009-01-06 2010-07-08 Yang Ye Method and apparatus of a unified control solution for bridgeless power factor controllers and grid connected inverters
CN101860189A (zh) * 2009-04-13 2010-10-13 台达电子工业股份有限公司 用于临界连续电流模式的无桥功率因数校正电路及其方法
CN101860192A (zh) * 2010-03-30 2010-10-13 艾默生网络能源有限公司 一种三态三电平pfc电路及多态三电平pfc电路

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP3876388A1 (en) * 2020-03-03 2021-09-08 Delta Electronics, Inc. Method for operating power factor correction circuit and method for operating uninterruptible power supply apparatus
WO2021213676A1 (en) * 2020-04-24 2021-10-28 Huawei Technologies Co., Ltd. Bridgeless single-phase pfc multi-level totem-pole power converter
US11996789B2 (en) 2020-04-24 2024-05-28 Huawei Digital Power Technologies Co., Ltd. Bridgeless single-phase PFC multi-level totem-pole power converter
WO2021247008A1 (en) * 2020-06-02 2021-12-09 Innovative Power Solutions, Llc Adaptive power factor correction (pfc) controller
CN112787497A (zh) * 2021-01-28 2021-05-11 三峡大学 一种带z型桥结构的单相三电平功率因数校正电路
CN112865569A (zh) * 2021-01-28 2021-05-28 三峡大学 一种混合t型桥的单相三电平整流器
CN112865565A (zh) * 2021-01-28 2021-05-28 三峡大学 一种对称t型桥的双开关三电平整流器

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