WO2018129835A1 - 一种基于维也纳pfc的智能型半桥正弦波电压转换电路 - Google Patents

一种基于维也纳pfc的智能型半桥正弦波电压转换电路 Download PDF

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WO2018129835A1
WO2018129835A1 PCT/CN2017/081785 CN2017081785W WO2018129835A1 WO 2018129835 A1 WO2018129835 A1 WO 2018129835A1 CN 2017081785 W CN2017081785 W CN 2017081785W WO 2018129835 A1 WO2018129835 A1 WO 2018129835A1
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diode
electrolytic capacitor
unit
switching transistor
anode
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PCT/CN2017/081785
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English (en)
French (fr)
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侯涛
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广东百事泰电子商务股份有限公司
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the invention relates to a voltage conversion circuit, in particular to an intelligent half bridge sinusoidal voltage conversion circuit based on the Vienna PFC.
  • the intelligent buck-boost conversion device from AC to AC is also called a travel plug.
  • the voltage conversion circuit is a key circuit thereof, and is a circuit capable of realizing AC-AC conversion, which can be AC-AC conversion realizes the function of buck-boost and stabilizes voltage and frequency.
  • most of the current AC-AC portable device market adopts a complicated topology circuit structure, and many unit modules are involved, which not only has high cost, but also has low PF value, low output voltage quality, and poor safety and reliability.
  • a certain high-frequency pulse signal exists on the output side of the circuit, thereby affecting the quality of the output voltage, and thus it is difficult to meet the conversion requirement.
  • the technical problem to be solved by the present invention is to provide a Vienna PFC-based intelligent type that can simplify the circuit structure, filter high frequency crosstalk, improve PF value, improve output voltage quality, and save cost, in view of the deficiencies of the prior art.
  • Half bridge sine wave voltage conversion circuit
  • the present invention adopts the following technical solutions.
  • An intelligent half-bridge sinusoidal voltage conversion circuit based on Vienna PFC comprising: an input unit for connecting to the grid AC; a Vienna PFC boost unit comprising a boost inductor, a first switch, and a a diode, a second diode, a third diode, a fourth diode, a fifth diode, a sixth diode, a first electrolytic capacitor, and a second electrolytic capacitor, the boost inductor
  • the front end is connected to the first output end of the input unit
  • the rear end of the boost inductor is connected to the anode of the first diode and the cathode of the second diode
  • the drain of the first switch tube and the third a cathode of the diode is connected to the cathode of the first diode
  • a source of the first switching tube and an anode of the fourth diode are both connected to an anode of the second diode
  • the first switching tube a gate for accessing a PWM
  • a drain of the second switching transistor and a positive electrode of the third electrolytic capacitor are connected to an anode of an output terminal of the Vienna PFC boosting unit, and a source of the second switching transistor is connected to the first
  • the drain of the three switch tubes, the source of the third switch tube and the cathode of the fourth electrolytic capacitor are both connected to the output terminal negative terminal of the Vienna PFC boost unit, the gate of the second switch tube and the third switch tube
  • the gates are respectively used to access the PWM control signals, so that the second switch tube and the third switch tube are alternately turned on, and the anode of the third electrolytic capacitor and the anode of the fourth electrolytic capacitor are connected to the common ground end.
  • a positive pole of the fourth electrolytic capacitor is used as a first output end of the half bridge inverter unit, a source of the second switching transistor is connected to a front end of the filter inductor, and a rear end of the filter inductor is used as a half bridge inverter unit The second output.
  • the input unit comprises a socket, a first fuse, a lightning protection resistor, a common mode suppression inductor and a safety capacitor, wherein the first fuse is connected to a neutral or a live line of the socket, and the common mode suppression inductor
  • the first fuse is connected to a neutral or a live line of the socket
  • the common mode suppression inductor The front end is connected in parallel to the socket
  • the lightning protection resistor is connected in parallel to the front end of the common mode suppression inductor
  • the safety capacitor is connected in parallel to the rear end of the common mode rejection inductor
  • the back end of the common mode suppression inductor is used as the output of the input unit end.
  • a control unit is further included, the gate of the first switch tube is connected to the control unit, and the control unit is configured to load a PWM pulse signal to the gate of the first switch tube.
  • control unit comprises a single chip microcomputer and peripheral circuits thereof.
  • the source of the third switch tube is connected in series with a limiting current resistor, and the source of the third switch tube is connected to the control unit, so that the control unit collects an electrical signal of the source of the third switch tube.
  • a second insurance is further included, and the second insurance is connected to the first output end of the half bridge inverter unit.
  • the voltage sampling unit further includes a first sampling resistor and a second sampling resistor connected in series, and a front end of the first sampling resistor is connected to a drain of the second switching transistor, The rear end of the second sampling resistor is connected to the control unit to enable the control unit to collect an electrical signal of the drain of the second switching transistor.
  • the method further includes an AC sampling unit connected between the input end of the input unit and the control unit, wherein the AC sampling unit is configured to collect the voltage of the AC side of the input unit and feed back to the control unit.
  • the AC sampling unit comprises an operational amplifier, and the two input ends of the operational amplifier are respectively connected to the input end of the input unit through a current limiting resistor, and the output end of the operational amplifier is connected to the control unit.
  • a pull-down resistor is connected between the gate and the source of the first switching transistor.
  • the Vienna PFC-based intelligent half-bridge sine wave voltage conversion circuit disclosed in the present invention
  • the Vienna PFC boosting unit enters the boost mode and adjusts the first switch tube.
  • the duty cycle of the PWM signal of the gate adjusts its on-time, so that the alternating current output by the voltage conversion circuit
  • the current and voltage phases on the input side are the same to improve the PF value of the conversion topology circuit.
  • the present invention not only improves the PF value of the voltage conversion circuit, but also improves the output voltage quality, making the voltage conversion process more secure and reliable.
  • the voltage conversion circuit of the invention has a simple structure and involves fewer unit modules, which not only reduces the failure rate of the product, but also saves the product volume and reduces the product cost.
  • the filter inductor can be used to filter out the high-frequency pulse in the output signal of the half-bridge inverter unit, so that the load can obtain high-quality power frequency sinusoidal alternating current, thereby improving the output voltage quality to meet the power supply requirements.
  • FIG. 1 is a schematic diagram of a sinusoidal voltage conversion circuit of the present invention.
  • FIG. 2 is a circuit schematic diagram of an AC sampling unit in a preferred embodiment of the present invention.
  • FIG. 3 is a circuit schematic diagram of a control unit in a preferred embodiment of the present invention.
  • the invention discloses an intelligent half-bridge sinusoidal voltage conversion circuit based on Vienna PFC, which is combined with FIG. 1 to FIG. 3 and includes:
  • a Vienna PFC boosting unit 20 includes a boosting inductor L2, a first switching transistor Q3, a first diode D1, a second diode D2, a third diode D3, a fourth diode D4, and a The fifth diode D5, the sixth diode D6, the first electrolytic capacitor C1 and the second electrolytic capacitor C2, the front end of the boosting inductor L2 is connected to the first output end of the input unit 10, and the boosting inductor L2 The back end is connected to the anode of the first diode D1 and the cathode of the second diode D2, and the drain of the first switching transistor Q3 and the cathode of the third diode D3 are both connected to the first diode The cathode of D1, the source of the first switching transistor Q3 and the anode of the fourth diode D4 are both connected to the anode of the second diode D2, and the gate of the first switching transistor Q3 is used for PWM a pulse signal, an
  • the connection point is a common ground end
  • the first An anode of an electrolytic capacitor C1 is used as an anode of the output end of the Vienna PFC boosting unit 20
  • a cathode of the second electrolytic capacitor C2 is used as a cathode of an output terminal of the Vienna PFC boosting unit 20;
  • the half bridge inverter unit 30 includes a second switch tube Q1, a third switch tube Q2, a third electrolytic capacitor C3, and a fourth electrolysis
  • the capacitor C4 and the filter inductor L3, the drain of the second switch transistor Q1 and the anode of the third electrolytic capacitor C3 are both connected to the positive terminal of the output of the Vienna PFC boost unit 20, and the source of the second switch transistor Q1 is connected.
  • the drain of the third switch transistor Q2, the source of the third switch transistor Q2 and the cathode of the fourth electrolytic capacitor C4 are both connected to the output terminal negative terminal of the Vienna PFC boost unit 20, and the second switch transistor Q1
  • the gates of the gates and the third switching transistors Q2 are respectively used to access the PWM control signals, so that the second switching transistor Q1 and the third switching transistor Q2 are alternately turned on, and the cathode and the third electrolytic capacitor C3 are respectively
  • the anode of the fourth electrolytic capacitor C4 is connected to the common ground terminal, and the anode of the fourth electrolytic capacitor C4 serves as the first output end of the half bridge inverter unit 30, and the source of the second switching transistor Q1 is connected to the filter inductor L3.
  • the front end of the filter inductor L3 serves as a second output terminal of the half bridge inverter unit 30.
  • the Vienna PFC boosting unit when the input unit 10 transmits the alternating current to the Vienna PFC boosting unit 20, the Vienna PFC boosting unit enters the boosting mode to increase the PF value of the switching topology circuit, and after boosting, passes the first electrolysis.
  • the filtered voltage of the capacitor C1 and the second electrolytic capacitor C2 is a positive and negative bus voltage.
  • the specific boosting principle is as follows: when the AC voltage output by the input unit 10 is up and down, when the first switching transistor Q3 is turned on, the input is The current outputted by the first output terminal of the unit 10 forms a loop through the boosting inductor L2, the first diode D1, the first switching transistor Q3, the fourth diode D4, and the second output end of the input unit 10, and the boosting inductor L2 The energy is stored; when the first switching transistor Q3 is turned off, the energy released by the boosting inductor L2 is returned to the boosting inductor via the first diode D1, the fifth diode D5, the first electrolytic capacitor C1, and the input unit 10
  • the first switch Q3 When the AC voltage outputted by the input unit 10 is up-down, the first switch Q3 is turned on, and the current output by the input unit 10 is passed through the boost inductor L2, the second diode D2, the first switch Q3, and the third.
  • Diode D3, input unit 10 forms a loop, boost inductor L2 stores energy; when first switch Q3 is turned off, boost inductor L2 releases energy through freewheeling diode second diode D2, sixth pole
  • the tube D6, the second electrolytic capacitor C2, and the input unit 10 are returned to the boosting inductor L2, so that the induced voltage generated by the boosting inductor L2 is rectified by the second diode D2 and the sixth diode D6.
  • a DC voltage that is positive and negative is formed on the electrolytic capacitor C2. Since the first electrolytic capacitor C1 and the second electrolytic capacitor C2 are connected in series, the voltage formed at the anode of the first electrolytic capacitor C1 is a voltage that is positive with respect to the intermediate point between the first electrolytic capacitor C1 and the second electrolytic capacitor C2. The voltage formed by the negative electrode of the second electrolytic capacitor C2 is a voltage that is negative with respect to the intermediate point between the first electrolytic capacitor C1 and the second electrolytic capacitor C2.
  • the on-time is adjusted by adjusting the duty ratio of the PWM signal at the gate of the first switching transistor Q3, so that the alternating current output from the voltage conversion circuit coincides with the current and voltage phases on the input side to increase the PF value.
  • the present invention not only improves the PF value of the voltage conversion circuit, but also improves the output voltage quality, making the voltage conversion process more secure and reliable.
  • the voltage conversion circuit of the invention has a simple structure and involves fewer unit modules, which not only reduces the failure rate of the product, but also saves the product volume and reduces the product cost.
  • the filter inductor L3 can be used to filter out the output signal of the half-bridge inverter unit.
  • the high-frequency pulse enables the load to obtain high-quality power-frequency sinusoidal AC, which in turn improves the output voltage quality to meet the power supply requirements.
  • a pull-down resistor R22 is connected between the gate and the source of the first switching transistor Q3.
  • the second switching transistor Q1 when the second switching transistor Q1 is turned on, the second switching transistor Q1, the filter inductor L3, the load, and the third electrolytic capacitor C3 form a loop, and the first high-frequency pulse level is generated to the load.
  • the freewheeling circuit is formed by the fourth electrolytic capacitor C4, the body diode of the third switching transistor Q2, and the filter inductor L3; when the third switching transistor Q2 is turned on, the third switching transistor Q2 is passed.
  • the fourth electrolytic capacitor C4, the load, and the filter inductor L3 form a loop, and a second high-frequency pulse level is formed on the load.
  • the body diode of the second switching transistor Q1 and the third The electrolytic capacitor C3, the load, and the filter inductor L3 form a freewheeling circuit.
  • the high frequency driving PWM signals of the second switching transistor Q1 and the third switching transistor Q2 are sent to the GATE poles of the second switching transistor Q1 and the third switching transistor Q2 after being changed by the power frequency modulation. Since the second switching transistor Q1 and the third switching transistor Q2 are driving signals after power frequency modulation, the high frequency pulse level after filtering by the filtered inductor L3 leaves only the power frequency sinusoidal alternating voltage to supply power to the load.
  • the third electrolytic capacitor C3 and the fourth electrolytic capacitor C4 also have a filtering function.
  • the phase and frequency in the inverter inverter circuit operate in accordance with the mode set in the control chip.
  • the inverter circuit is simple to control, and the circuit uses only two MOS tubes, and the cost is low.
  • the input unit 10 includes a socket, a first fuse F2, a lightning protection resistor RV1, a common mode suppression inductor L1, and a safety capacitor CX1.
  • the first fuse F2 is connected in series to the zero line or the fire line of the socket.
  • the front end of the common mode suppressing inductor L1 is connected in parallel to the socket, the lightning protection resistor RV1 is connected in parallel to the front end of the common mode suppressing inductor L1, and the safety capacitor CX1 is connected in parallel to the rear end of the common mode suppressing inductor L1, and the The rear end of the common mode rejection inductor L1 serves as the output terminal of the input unit 10.
  • the embodiment further includes a control unit 60.
  • the gate of the first switch tube Q3 is connected to the control unit 60, and the control unit 60 is used to the first switch tube Q3.
  • the gate is loaded with a PWM pulse signal.
  • the control unit 60 includes a single chip U1 and its peripheral circuits.
  • the source of the third switching transistor Q2 is connected in series with a finite current resistor (R3, R4, R5), and the source of the third switching transistor Q2 Connected to the control unit 60 to cause the control unit 60 to collect an electrical signal of the source of the third switching transistor Q2.
  • the half bridge inverter unit 30 further includes a second fuse F1 connected in series with the first output end of the half bridge inverter unit 30.
  • a voltage sampling unit 40 is further included.
  • the voltage sampling unit 40 includes a first sampling resistor 13 and a second sampling resistor R15 connected in series.
  • the front end of the first sampling resistor 13 is connected to the second switch.
  • the drain of the transistor Q1, the rear end of the second sampling resistor R15 is connected to the control unit 60, so that the control unit 60 collects an electrical signal of the drain of the second switching transistor Q1.
  • the embodiment further includes an AC sampling unit 50 connected between the input end of the input unit 10 and the control unit 60.
  • the sampling unit 50 is configured to collect the voltage of the AC side of the input unit 10 and feed back to the control unit 60.
  • the AC sampling unit 50 includes an operational amplifier U9B.
  • the two input ends of the operational amplifier U9B are respectively connected to the input end of the input unit 10 through a current limiting resistor, and the output end of the operational amplifier U9B is connected to Control unit 60.
  • the first switch tube Q3 increases or decreases the on-time of the first switch tube Q3 according to the input AC sine wave change obtained by the control unit, so that the current and the voltage phase are consistent to increase the PF value.
  • the invention discloses a Vienna PFC-based intelligent half-bridge sine wave voltage conversion circuit, which has a high PF value, is isolated from the output end, and has high safety.
  • the output voltage can be automatically adjusted within the input full voltage range, and the output frequency is fixed, and the output voltage is sinusoidal output, which has an automatic shaping function for the AC voltage.
  • the present invention includes a voltage and current sampling circuit capable of preventing surge voltage. With the current, and the control is simple, especially the inverter part uses only two switching tubes, which has the advantages of lower cost and the like.

Abstract

一种基于维也纳PFC的智能型半桥正弦波电压转换电路，包括有输入单元（10）、维也纳PFC升压单元（20）以及半桥逆变单元（30）。维也纳PFC升压单元包括升压电感（L2）、第一开关管（Q3）、第一二极管(D1)、第二二极管(D2)、第三二极管(D3)、第四二极管(D4)、第五二极管(D5)、第六二极管(D6)、第一电解电容(C1)和第二电解电容(C2)。半桥逆变单元包括第二开关管（Q1）、第三开关管（Q2）、第三电解电容（C3）、第四电解电容（C4）和滤波电感（L3）。第四电解电容的正极作为半桥逆变单元的第一输出端，第二开关管的源极连接于滤波电感的前端，滤波电感的后端作为半桥逆变单元的第二输出端。该电路可提高输出电压质量、减少高频串扰以及节约电路成本。

Description

一种基于维也纳PFC的智能型半桥正弦波电压转换电路
技术领域
本发明涉及电压转换电路，尤其涉及一种基于维也纳PFC的智能型半桥正弦波电压转换电路。
背景技术
现有技术中，由AC转AC的智能升降压转换装置又被称为旅行插排，该装置中，电压转换电路是其关键电路，是一种能实现AC-AC变换的电路，可以在AC-AC变换中实现升降压并稳定电压与频率的功能。然而目前的AC-AC便携式设备市场大多数采用复杂的拓扑电路结构，所涉及的单元模块较多，不仅成本较高，而且PF值低、输出电压质量低、安全可靠性差。实际应用中，由于电压转换过程中存在开关管的高速切换，使得电路的输出侧会存在一定的高频脉冲信号，进而影响输出电压的质量，因而难以满足转换要求。
发明内容
本发明要解决的技术问题在于，针对现有技术的不足，提供一种可简化电路结构、可滤除高频串扰、提高PF值、提高输出电压质量，并且节约成本的基于维也纳PFC的智能型半桥正弦波电压转换电路。
为解决上述技术问题，本发明采用如下技术方案。
一种基于维也纳PFC的智能型半桥正弦波电压转换电路，其包括有：一输入单元，用于接入电网交流电；一维也纳PFC升压单元，包括有升压电感、第一开关管、第一二极管、第二二极管、第三二极管、第四二极管、第五二极管、第六二极管、第一电解电容和第二电解电容，所述升压电感的前端连接于输入单元的第一输出端，所述升压电感的后端连接于第一二极管的阳极和第二二极管的阴极，所述第一开关管的漏极和第三二极管的阴极均连接于第一二极管的阴极，所述第一开关管的源极和第四二极管的阳极均连接于第二二极管的阳极，所述第一开关管的栅极用于接入PWM脉冲信号，所述第五二极管的阳极连接于第三二极管的阴极，所述第五二极管的阴极连接于第一电解电容的正极，所述第一电解电容的负极连接于第二电解电容的正极，所述第六二极管的阴极连接于第四二极管的阳极，所述第六二极管的阳极连接于第二电解电容负极，所述第四二极管的阴极、第二电解电容的正极和输入单元的第二输出端相连接且该连接点作为共地端，所述第一电解电容的正极作为维也纳 PFC升压单元的输出端正极，所述第二电解电容的负极作为维也纳PFC升压单元的输出端负极；一半桥逆变单元，包括有第二开关管、第三开关管、第三电解电容、第四电解电容和滤波电感，所述第二开关管的漏极和第三电解电容的正极均连接于维也纳PFC升压单元的输出端正极，所述第二开关管的源极连接于第三开关管的漏极，所述第三开关管的源极和第四电解电容的负极均连接于维也纳PFC升压单元的输出端负极，所述第二开关管的栅极和第三开关管的栅极分别用于接入PWM控制信号，以令所述第二开关管和第三开关管交替导通，所述第三电解电容的负极和第四电解电容的正极均连接于共地端，且该第四电解电容的正极作为半桥逆变单元的第一输出端，所述第二开关管的源极连接于滤波电感的前端，所述滤波电感的后端作为半桥逆变单元的第二输出端。
优选地，所述输入单元包括有插座、第一保险、防雷电阻、共模抑制电感和安规电容，所述第一保险串接于插座的零线或火线上，所述共模抑制电感的前端并联于插座，所述防雷电阻并联于共模抑制电感的前端，所述安规电容并联于共模抑制电感的后端，且所述共模抑制电感的后端作为输入单元的输出端。
优选地，还包括有一控制单元，所述第一开关管的栅极连接于控制单元，所述控制单元用于向第一开关管的栅极加载PWM脉冲信号。
优选地，所述控制单元包括有单片机及其外围电路。
优选地，所述第三开关管的源极串接有限流电阻，所述第三开关管的源极连接于控制单元，以令所述控制单元采集第三开关管源极的电信号。
优选地，还包括有第二保险，所述第二保险串接于半桥逆变单元的第一输出端。
优选地，还包括有一电压采样单元，所述电压采样单元包括有依次串联的第一采样电阻和第二采样电阻，所述第一采样电阻的前端连接于第二开关管的漏极，所述第二采样电阻的后端连接于控制单元，以令所述控制单元采集第二开关管漏极的电信号。
优选地，还包括有一交流采样单元，所述交流采样单元连接于输入单元的输入端与控制单元之间，所述交流采样单元用于采集输入单元交流侧的电压并反馈至控制单元。
优选地，所述交流采样单元包括有运放，所述运放的两个输入端分别通过限流电阻而连接于输入单元的输入端，所述运放的输出端连接于控制单元。
优选地，所述第一开关管的栅极与源极之间连接有下拉电阻。
本发明公开的基于维也纳PFC的智能型半桥正弦波电压转换电路中，当输入单元将交流电传输至维也纳PFC升压单元时，维也纳PFC升压单元进入升压模式，并通过调整第一开关管栅极的PWM信号的占空比来调整其导通时间，使得电压转换电路输出的交流电与 输入侧的电流、电压相位一致，以提高转换拓扑电路的PF值。基于上述结构，本发明不仅提高了电压转换电路的PF值，还提高了输出电压质量，使得电压转换过程更加安全可靠。同时本发明电压转换电路的结构简单，所涉及的单元模块较少，不仅降低了产品的故障率，而且节省了产品体积，降低了产品成本。在此基础上，利用滤波电感可滤除半桥逆变单元输出信号中的高频脉冲，使得负载能够获得优质的工频正弦交流电，进而提高输出电压质量，以满足供电需求。
附图说明
图1为本发明正弦波电压转换电路的原理图。
图2为本发明优选实施例中交流采样单元的电路原理图。
图3为本发明优选实施例中控制单元的电路原理图。
具体实施方式
下面结合附图和实施例对本发明作更加详细的描述。
本发明公开了一种基于维也纳PFC的智能型半桥正弦波电压转换电路，结合图1至图3所示，其包括有：
一输入单元10，用于接入电网交流电；
一维也纳PFC升压单元20，包括有升压电感L2、第一开关管Q3、第一二极管D1、第二二极管D2、第三二极管D3、第四二极管D4、第五二极管D5、第六二极管D6、第一电解电容C1和第二电解电容C2，所述升压电感L2的前端连接于输入单元10的第一输出端，所述升压电感L2的后端连接于第一二极管D1的阳极和第二二极管D2的阴极，所述第一开关管Q3的漏极和第三二极管D3的阴极均连接于第一二极管D1的阴极，所述第一开关管Q3的源极和第四二极管D4的阳极均连接于第二二极管D2的阳极，所述第一开关管Q3的栅极用于接入PWM脉冲信号，所述第五二极管D5的阳极连接于第三二极管D3的阴极，所述第五二极管D5的阴极连接于第一电解电容C1的正极，所述第一电解电容C1的负极连接于第二电解电容C2的正极，所述第六二极管D6的阴极连接于第四二极管D4的阳极，所述第六二极管D6的阳极连接于第二电解电容C2负极，所述第四二极管D4的阴极、第二电解电容C2的正极和输入单元10的第二输出端相连接且该连接点作为共地端，所述第一电解电容C1的正极作为维也纳PFC升压单元20的输出端正极，所述第二电解电容C2的负极作为维也纳PFC升压单元20的输出端负极；
一半桥逆变单元30，包括有第二开关管Q1、第三开关管Q2、第三电解电容C3、第四电解 电容C4和滤波电感L3，所述第二开关管Q1的漏极和第三电解电容C3的正极均连接于维也纳PFC升压单元20的输出端正极，所述第二开关管Q1的源极连接于第三开关管Q2的漏极，所述第三开关管Q2的源极和第四电解电容C4的负极均连接于维也纳PFC升压单元20的输出端负极，所述第二开关管Q1的栅极和第三开关管Q2的栅极分别用于接入PWM控制信号，以令所述第二开关管Q1和第三开关管Q2交替导通，所述第三电解电容C3的负极和第四电解电容C4的正极均连接于共地端，且该第四电解电容C4的正极作为半桥逆变单元30的第一输出端，所述第二开关管Q1的源极连接于滤波电感L3的前端，所述滤波电感L3的后端作为半桥逆变单元30的第二输出端。
上述正弦波电压转换电路中，当输入单元10将交流电传输至维也纳PFC升压单元20时，维也纳PFC升压单元进入升压模式，以提高转换拓扑电路的PF值，升压后通过第一电解电容C1和第二电解电容C2滤波后的电压为正负母线电压，具体的升压原理如下：当输入单元10输出的交流电压为上正下负时，第一开关管Q3导通时，输入单元10第一输出端输出的电流经升压电感L2、第一二极管D1、第一开关管Q3、第四二极管D4、输入单元10的第二输出端形成回路，升压电感L2储存能量；当第一开关管Q3关断时，升压电感L2释放的能量经第一二极管D1、第五二极管D5、第一电解电容C1、输入单元10再回到升压电感L2的前端，这样升压电感L2产生的感应电压经第一二极管D1、第五二极管D5整流后会在第一电解电容C1上形成上正下负的直流电压。当输入单元10输出的交流电压为上负下正时，第一开关管Q3导通，输入单元10输出的电流经升压电感L2、第二二极管D2、第一开关管Q3、第三二极管D3、输入单元10形成回路，升压电感L2储存能量；当第一开关管Q3关断时，升压电感L2释放的能量经续流管第二二极管D2、第六二极管D6、第二电解电容C2、输入单元10再回到升压电感L2，这样升压电感L2将产生的感应电压经第二二极管D2、第六二极管D6整流后会在第二电解电容C2上形成上正下负的直流电压。由于第一电解电容C1和第二电解电容C2串联，所以在第一电解电容C1的正极形成的电压是相对于第一电解电容C1和第二电解电容C2的中间点为正的电压，在第二电解电容C2的负极形成的电压是相对于第一电解电容C1和第二电解电容C2的中间点为负的电压。通过调整第一开关管Q3栅极的PWM信号的占空比来调整其导通时间，使得电压转换电路输出的交流电与输入侧的电流、电压相位一致来提高PF值。基于上述结构，本发明不仅提高了电压转换电路的PF值，还提高了输出电压质量，使得电压转换过程更加安全可靠。同时本发明电压转换电路的结构简单，所涉及的单元模块较少，不仅降低了产品的故障率，而且节省了产品体积，降低了产品成本。在此基础上，利用滤波电感L3可滤除半桥逆变单元输出信号 中的高频脉冲，使得负载能够获得优质的工频正弦交流电，进而提高输出电压质量，以满足供电需求。进一步地，所述第一开关管Q3的栅极与源极之间连接有下拉电阻R22。
上述半桥逆变单元30中，当第二开关管Q1导通时，第二开关管Q1、滤波电感L3、负载、第三电解电容C3形成回路，产生第一个高频脉冲电平给负载，当第二开关管Q1关闭时，通过第四电解电容C4、第三开关管Q2的体二极管、滤波电感L3形成续流回路；当第三开关管Q2导通时通过第三开关管Q2、第四电解电容C4、负载、滤波电感L3形成回路，在负载上就形成了第二个高频脉冲电平，当第三开关管Q2关断时，第二开关管Q1的体二极管、第三电解电容C3、负载、滤波电感L3形成续流回路。第二开关管Q1、第三开关管Q2的高频驱动PWM信号是经工频调制变化后再送给第二开关管Q1、第三开关管Q2的GATE极。由于第二开关管Q1、第三开关管Q2是工频调制后的驱动信号，所以经滤波电感L3滤除逆变后的高频脉冲电平只留下工频正弦交流电压，给负载供电。同时第三电解电容C3、第四电解电容C4还有滤波的作用。逆变倒相电路中的相位与频率按照控制芯片内部设定的模式进行工作。本逆变电路控制简单，电路只用两个MOS管，成本低廉。
关于输入部分，所述输入单元10包括有插座、第一保险F2、防雷电阻RV1、共模抑制电感L1和安规电容CX1，所述第一保险F2串接于插座的零线或火线上，所述共模抑制电感L1的前端并联于插座，所述防雷电阻RV1并联于共模抑制电感L1的前端，所述安规电容CX1并联于共模抑制电感L1的后端，且所述共模抑制电感L1的后端作为输入单元10的输出端。
作为一种优选方式，请参照图3，本实施例还包括有一控制单元60，所述第一开关管Q3的栅极连接于控制单元60，所述控制单元60用于向第一开关管Q3的栅极加载PWM脉冲信号。进一步地，所述控制单元60包括有单片机U1及其外围电路。
本实施例中，为了便于对逆变电路中电信号进行采集，所述第三开关管Q2的源极串接有限流电阻(R3、R4、R5)，所述第三开关管Q2的源极连接于控制单元60，以令所述控制单元60采集第三开关管Q2源极的电信号。
进一步地，该半桥逆变单元30还包括有第二保险F1，所述第二保险F1串接于半桥逆变单元30的第一输出端。
本实施例中，还包括有一电压采样单元40，所述电压采样单元40包括有依次串联的第一采样电阻13和第二采样电阻R15，所述第一采样电阻13的前端连接于第二开关管Q1的漏极，所述第二采样电阻R15的后端连接于控制单元60，以令所述控制单元60采集第二开关管Q1漏极的电信号。
为了便于对交流侧电信号进行检测，请参照图2，本实施例还包括有一交流采样单元50，所述交流采样单元50连接于输入单元10的输入端与控制单元60之间，所述交流采样单元50用于采集输入单元10交流侧的电压并反馈至控制单元60。
进一步地，所述交流采样单元50包括有运放U9B，所述运放U9B的两个输入端分别通过限流电阻而连接于输入单元10的输入端，所述运放U9B的输出端连接于控制单元60。其中，第一开关管Q3是根据控制单元采到的输入交流正弦波变化来加大或减少第一开关管Q3的导通时间，以使电流与电压相位变一致来提高PF值。
本发明公开的基于维也纳PFC的智能型半桥正弦波电压转换电路，其具有高PF值、电网与输出端隔离，安全性非常高。在输入全电压范围内能够能自动调节输出电压，并且固定输出频率，并且输出电压是以正弦波输出，对交流电压有自动整形功能，此外本发明含有电压与电流采样电路，能防浪涌电压与电流，并且控制简单，特别是逆变部分只用两个开关管，具有成本较低等优势。
以上所述只是本发明较佳的实施例，并不用于限制本发明，凡在本发明的技术范围内所做的修改、等同替换或者改进等，均应包含在本发明所保护的范围内。

Claims (10)

  1. 一种基于维也纳PFC的智能型半桥正弦波电压转换电路，其特征在于，包括有：
    一输入单元(10)，用于接入电网交流电；
    一维也纳PFC升压单元(20)，包括有升压电感(L2)、第一开关管(Q3)、第一二极管(D1)、第二二极管(D2)、第三二极管(D3)、第四二极管(D4)、第五二极管(D5)、第六二极管(D6)、第一电解电容(C1)和第二电解电容(C2)，所述升压电感(L2)的前端连接于输入单元(10)的第一输出端，所述升压电感(L2)的后端连接于第一二极管(D1)的阳极和第二二极管(D2)的阴极，所述第一开关管(Q3)的漏极和第三二极管(D3)的阴极均连接于第一二极管(D1)的阴极，所述第一开关管(Q3)的源极和第四二极管(D4)的阳极均连接于第二二极管(D2)的阳极，所述第一开关管(Q3)的栅极用于接入PWM脉冲信号，所述第五二极管(D5)的阳极连接于第三二极管(D3)的阴极，所述第五二极管(D5)的阴极连接于第一电解电容(C1)的正极，所述第一电解电容(C1)的负极连接于第二电解电容(C2)的正极，所述第六二极管(D6)的阴极连接于第四二极管(D4)的阳极，所述第六二极管(D6)的阳极连接于第二电解电容(C2)负极，所述第四二极管(D4)的阴极、第二电解电容(C2)的正极和输入单元(10)的第二输出端相连接且该连接点作为共地端，所述第一电解电容(C1)的正极作为维也纳PFC升压单元(20)的输出端正极，所述第二电解电容(C2)的负极作为维也纳PFC升压单元(20)的输出端负极；
    一半桥逆变单元(30)，包括有第二开关管(Q1)、第三开关管(Q2)、第三电解电容(C3)、第四电解电容(C4)和滤波电感(L3)，所述第二开关管(Q1)的漏极和第三电解电容(C3)的正极均连接于维也纳PFC升压单元(20)的输出端正极，所述第二开关管(Q1)的源极连接于第三开关管(Q2)的漏极，所述第三开关管(Q2)的源极和第四电解电容(C4)的负极均连接于维也纳PFC升压单元(20)的输出端负极，所述第二开关管(Q1)的栅极和第三开关管(Q2)的栅极分别用于接入PWM控制信号，以令所述第二开关管(Q1)和第三开关管(Q2)交替导通，所述第三电解电容(C3)的负极和第四电解电容(C4)的正极均连接于共地端，且该第四电解电容(C4)的正极作为半桥逆变单元(30)的第一输出端，所述第二开关管(Q1)的源极连接于滤波电感(L3)的前端，所述滤波电感(L3)的后端作为半桥逆变单元(30)的第二输出端。
  2. 如权利要求1所述的基于维也纳PFC的智能型半桥正弦波电压转换电路，其特征在于，所述输入单元(10)包括有插座、第一保险(F2)、防雷电阻(RV1)、共模抑制电感(L1)和安规电容(CX1)，所述第一保险(F2)串接于插座的零线或火线上，所述共模抑制电感 (L1)的前端并联于插座，所述防雷电阻(RV1)并联于共模抑制电感(L1)的前端，所述安规电容(CX1)并联于共模抑制电感(L1)的后端，且所述共模抑制电感(L1)的后端作为输入单元(10)的输出端。
  3. 如权利要求1所述的基于维也纳PFC的智能型半桥正弦波电压转换电路，其特征在于，还包括有一控制单元(60)，所述第一开关管(Q3)的栅极连接于控制单元(60)，所述控制单元(60)用于向第一开关管(Q3)的栅极加载PWM脉冲信号。
  4. 如权利要求3所述的基于维也纳PFC的智能型半桥正弦波电压转换电路，其特征在于，所述控制单元(60)包括有单片机(U1)及其外围电路。
  5. 5、如权利要求3所述的基于维也纳PFC的智能型半桥正弦波电压转换电路，其特征在于，所述第三开关管(Q2)的源极串接有限流电阻(R3、R4、R5)，所述第三开关管(Q2)的源极连接于控制单元(60)，以令所述控制单元(60)采集第三开关管(Q2)源极的电信号。
  6. 如权利要求1所述的基于维也纳PFC的智能型半桥正弦波电压转换电路，其特征在于，还包括有第二保险(F1)，所述第二保险(F1)串接于半桥逆变单元(30)的第一输出端。
  7. 如权利要求3所述的基于维也纳PFC的智能型半桥正弦波电压转换电路，其特征在于，还包括有一电压采样单元(40)，所述电压采样单元(40)包括有依次串联的第一采样电阻(13)和第二采样电阻(R15)，所述第一采样电阻(13)的前端连接于第二开关管(Q1)的漏极，所述第二采样电阻(R15)的后端连接于控制单元(60)，以令所述控制单元(60)采集第二开关管(Q1)漏极的电信号。
  8. 如权利要求3所述的基于维也纳PFC的智能型半桥正弦波电压转换电路，其特征在于，还包括有一交流采样单元(50)，所述交流采样单元(50)连接于输入单元(10)的输入端与控制单元(60)之间，所述交流采样单元(50)用于采集输入单元(10)交流侧的电压并反馈至控制单元(60)。
  9. 如权利要求8所述的基于维也纳PFC的智能型半桥正弦波电压转换电路，其特征在于，所述交流采样单元(50)包括有运放(U9B)，所述运放(U9B)的两个输入端分别通过限流电阻而连接于输入单元(10)的输入端，所述运放(U9B)的输出端连接于控制单元(60)。
  10. 如权利要求1所述的基于维也纳PFC的智能型半桥正弦波电压转换电路，其特征在于，所述第一开关管(Q3)的栅极与源极之间连接有下拉电阻(R22)。
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