WO2018099187A1 - Procédé de commande et dispositif de commande pour système d'entraînement de moteur et climatiseur à fréquence variable - Google Patents

Procédé de commande et dispositif de commande pour système d'entraînement de moteur et climatiseur à fréquence variable Download PDF

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WO2018099187A1
WO2018099187A1 PCT/CN2017/105300 CN2017105300W WO2018099187A1 WO 2018099187 A1 WO2018099187 A1 WO 2018099187A1 CN 2017105300 W CN2017105300 W CN 2017105300W WO 2018099187 A1 WO2018099187 A1 WO 2018099187A1
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value
axis
voltage
inverter
current
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PCT/CN2017/105300
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Chinese (zh)
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霍军亚
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广东美的制冷设备有限公司
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H02M1/143—Arrangements for reducing ripples from dc input or output using compensating arrangements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2201/00—Indexing scheme relating to controlling arrangements characterised by the converter used
    • H02P2201/15—Power factor Correction [PFC] circuit generating the DC link voltage for motor driving inverter

Definitions

  • the invention relates to the technical field of motor control, in particular to a control method, a control device and an inverter air conditioner of a motor drive system.
  • the conventional passive PFC (power factor correction) scheme variable frequency drive is widely used due to its advantages of low cost and high reliability.
  • Its passive PFC scheme uses the full bridge to rectify the AC voltage and then pass the large electrolysis.
  • the smoothing effect of the capacitor makes the DC bus voltage stable, but when the load of the driving motor is increased and the inverter part needs to output high power, the ripple on the DC bus voltage with the same phase as the input power AC voltage appears.
  • the ripple voltage affects the working life of the large electrolytic capacitor, which in turn affects the operational stability of the variable frequency drive.
  • variable frequency control stability In order to ensure that the large electrolytic capacitor meets the requirements of variable frequency control stability, it is mainly realized by the following two methods: (1) reducing the output power of the variable frequency controller; and (2) increasing the capacity of the large electrolytic capacitor.
  • (1) reducing the output power of the variable frequency controller By reducing the output power of the inverter controller, it is impossible to obtain a stable high-power output with an increased load; and increasing the capacity of the large electrolytic capacitor increases the cost accordingly.
  • the main object of the present invention is to provide a control method for a motor drive system, which aims to solve the problem that the motor drive system of the passive PFC scheme generates ripple due to an increase in output power, thereby causing the life of the electrolytic capacitor to be shortened to affect the operation of the motor drive system. Stable Sex.
  • the present invention provides a control method for a motor drive system including a rectifier, a passive PFC circuit, a DC smoothing circuit, an inverter, an arithmetic control unit, and a motor, the rectifier pairing
  • the input voltage is full-wave rectified, the passive PFC circuit having a reactor connected in series with the output of the rectifier, the AC input voltage outputting a DC bus voltage through the rectifier, a passive PFC circuit, a DC smoothing circuit
  • the inverter provides power, and the arithmetic control unit controls the inverter to drive the motor to operate, wherein the control method comprises the following steps:
  • a control signal is generated according to the voltage fluctuation amount, the DC bus voltage value, and the three-phase current value to control the inverter of the motor drive system to drive the motor to operate.
  • control unit generates a control signal according to the voltage fluctuation amount, the DC bus voltage value, and the three-phase current value to control the inverter of the motor drive system, and specifically includes:
  • the PWM control signal is generated according to the d-axis given voltage value, the q-axis given voltage value, the DC bus voltage value, and the motor rotor angle estimation value to control the inverter.
  • the step of acquiring the initial value of the q-axis current comprises:
  • the difference is calculated and PI control is performed to obtain the initial value of the q-axis current.
  • the obtaining is based on a DC bus voltage value and an output voltage amplitude of the inverter
  • the d-axis given current value steps include:
  • the d-axis current initial value is subjected to a clipping process to obtain the d-axis given current value.
  • the step of calculating the q-axis current compensation amount by the voltage fluctuation amount comprises:
  • PI control is performed according to the amount of voltage fluctuation to obtain a q-axis current compensation amount.
  • the present invention also provides a control device for a motor drive system, the control device comprising:
  • a current detecting module for detecting a three-phase current value of the driving motor
  • a voltage detecting module configured to detect a DC bus voltage value of the motor driving system
  • An average voltage obtaining module configured to obtain an average voltage value according to the DC bus voltage value
  • a voltage fluctuation quantity acquisition module configured to acquire a voltage fluctuation amount according to the DC bus voltage value and the average voltage value
  • the control signal generating module generates a control signal according to the voltage fluctuation amount, the DC bus voltage value and the three-phase current value to control the inverter of the motor drive system to drive the motor to operate.
  • control signal generating module specifically includes:
  • a q-axis current compensation calculator configured to calculate a q-axis current compensation amount according to the voltage fluctuation amount
  • the q-axis current initial value obtaining unit is configured to perform a difference calculation according to the motor target speed value and the actual motor speed estimation value, and then perform PI control to obtain an initial value of the q-axis current;
  • a q-axis given current value operation unit configured to obtain a q-axis given current value according to the q-axis current compensation amount and the initial value of the q-axis current;
  • a d-axis given current value operation unit configured to calculate a d-axis given current value according to the DC bus voltage value and an output voltage amplitude of the inverter
  • the dq axis current operation unit is configured to perform coordinate transformation on the three-phase current to obtain an actual current value of the d-axis and an actual current value of the q-axis;
  • the dq axis voltage operation unit is configured to calculate the d-axis given current value and the d-axis actual current value and the q-axis given current value and the q-axis actual current value respectively to obtain the d-axis given voltage value and the q-axis given voltage. value;
  • the PWM operation unit is configured to generate a PWM control signal to control the inverter according to the d-axis given voltage value, the q-axis given voltage value, the DC bus voltage value, and the motor rotor angle estimation value.
  • the q-axis current compensation calculator is further configured to:
  • PI control is performed according to the amount of voltage fluctuation to obtain a q-axis current compensation amount.
  • the d-axis given current value operation unit specifically includes:
  • a voltage amplitude calculation subunit configured to calculate an output voltage amplitude of the inverter according to a previous d-axis given voltage value and a q-axis given voltage value
  • the maximum output voltage value calculation sub-unit is configured to calculate the maximum output voltage value of the inverter according to the DC bus voltage value
  • a field weakening control subunit configured to calculate an initial value of the d-axis current according to a maximum output voltage of the inverter and an output voltage amplitude of the inverter
  • the limiting subunit is configured to perform a limiting process on the initial value of the d-axis current to obtain the d-axis given current value.
  • the present invention also provides an inverter air conditioner comprising the control device of the motor drive system.
  • the control method of the motor drive system detects the DC bus voltage value and the three-phase current value of the drive motor, and obtains an average voltage value according to the DC bus voltage, and then obtains the voltage fluctuation amount according to the DC bus voltage value and the average voltage value. Finally, the inverter of the motor drive system is controlled according to the voltage fluctuation amount, the DC bus voltage value and the three-phase current value generating control signals to drive the motor to operate.
  • the control method provided by the invention can detect the fluctuation of the DC bus voltage in real time, and adjust the Iq current value in the motor drive system in real time by detecting the fluctuation, thereby finally controlling the motor, thereby reducing the straightness
  • the fluctuation of the bus voltage makes it possible to realize high-power output without increasing the electrolytic capacitor, and solves the problem that the output power of the inverter is too large when the load is too large in the motor drive system of the passive PFC scheme.
  • the occurrence of the ripple voltage on the DC bus voltage causes the working life of the large electrolytic filter capacitor on the DC bus to decrease, which in turn affects the stability of the entire motor drive system.
  • FIG. 1 is a schematic structural diagram of a circuit of a motor drive system according to an embodiment of the present invention
  • FIG. 2 is a schematic flow chart of a method for controlling a motor drive system according to an embodiment of the present invention
  • FIG. 3 is a schematic structural diagram of a control device of a motor drive system according to an embodiment of the present invention.
  • FIG. 4 is a schematic diagram of signal generation of a voltage fluctuation amount acquisition module in a control device of a motor drive system according to an embodiment of the present invention
  • FIG. 5 is a schematic structural diagram of a control signal generating module in a control device of a motor drive system according to an embodiment of the present invention
  • FIG. 6 is a schematic structural diagram of a d-axis given current value operation unit in a control device for a motor drive system according to an embodiment of the present invention.
  • the motor drive system includes a rectifier 2, a passive PFC circuit 3, a DC smoothing circuit 4, an inverter 5, an arithmetic control unit 7, and a motor 6.
  • the passive PFC circuit 3 has a reactor L connected in series with the output terminal of the rectifier, and may further include a first capacitor C1 and a diode D5.
  • the DC smoothing circuit 4 is composed of a second capacitor C2, and the rectifier 2 is composed of diodes D1-D4. Full-bridge rectification, rectifying AC input voltage 1 and converting it to straight The pulsating voltage is connected in series to the reactor L on the rear side of the rectifier.
  • the first end of the reactor L is connected to the positive output terminal of the rectifier, the second end of the reactor L is connected to the anode of the diode D5, and the first capacitor C1 is connected in parallel to the reactor L.
  • the second capacitor C2 is connected in parallel with the cathode terminal of the diode and the cathode terminal of the rectifier, and the reactor L utilizes the characteristic of the current charge and discharge hysteresis voltage of the inductor to improve the power factor of the rectifier output current.
  • Capacitor C1 is a small-capacity filter capacitor that suppresses harmonics in the circuit.
  • the second capacitor is a large-capacity electrolytic capacitor that smoothes the DC ripple voltage output from the rectifier.
  • Diode D5 uses its isolation to increase the charging voltage on the second capacitor. Further increase the power factor.
  • the AC input voltage outputs a DC bus voltage through the rectifier 2, the passive PFC circuit 3, and the DC smoothing circuit 4, and supplies DC power to the inverter 5, and the arithmetic control unit 7 controls the inverter switch S1-through the control command.
  • S6 performs switching control to drive the motor 6 to operate, and the motor 6 is a permanent magnet synchronous motor, including a compressor for the inverter air conditioner.
  • control method of the motor drive system includes the following steps:
  • the DC bus voltage V dc of the motor drive system can be detected by the circuit structure of the voltage dividing resistor, and the three-phase current Iu, v, w of the motor is detected by a single-resistor or three-resistor sampling circuit structure. Belongs to the prior art.
  • the average voltage value V dc — ave of the period of time can be obtained by detecting the instantaneous value of the DC bus voltage value V dc for a predetermined period of time and then averaging.
  • S40 Generate a control signal according to the voltage fluctuation amount, the DC bus voltage value, and the three-phase current value to control the inverter of the motor drive system to drive the motor to operate.
  • controlling the inverter of the motor drive system according to the voltage fluctuation amount, the DC bus voltage value, and the three-phase current value generating control signal specifically includes:
  • the PWM control signal is generated according to the d-axis given voltage value, the q-axis given voltage value, the DC bus voltage value, and the motor rotor angle estimation value to control the inverter.
  • ⁇ V dc voltage fluctuation amount calculated q-axis current compensation amount according to the time I q_com1 by performing PI control of the voltage fluctuation amount ⁇ V dc, calculated q-axis current compensation amount I q_com1.
  • the initial value I q0 of the q-axis current can be obtained by calculating the difference between the motor target speed value ⁇ m * and the actual motor speed value ⁇ m and then performing PI control.
  • the actual motor speed value ⁇ m can pass through a position sensor such as a Hall switch in the motor. Detected, or for the motor without position sensor, the actual motor speed value ⁇ m is the estimated value. At this time, the acquisition of ⁇ m is as follows:
  • the rotor angle estimation value ⁇ est of the motor and the actual motor speed value ⁇ m are obtained by the flux linkage observation method. Specifically, first, an estimated value of the effective magnetic flux of the compressor motor in the directions of the two-phase stationary coordinate system ⁇ and ⁇ axes can be calculated according to the voltages V ⁇ , V ⁇ and the currents I ⁇ and I ⁇ on the two-phase stationary coordinate system. Specifically calculated according to formula (1) as follows:
  • V ⁇ and V ⁇ are the voltages in the ⁇ and ⁇ axis directions, respectively
  • I ⁇ and I ⁇ are the currents in the ⁇ and ⁇ axis directions, respectively.
  • L q is the q-axis flux linkage of the motor.
  • K p_pll and K i_pll are proportional integration parameters
  • ⁇ err is the deviation angle estimation value
  • ⁇ f is the bandwidth of the speed low-pass filter.
  • the q-axis current compensation amount I q_com1 and the q-axis current initial value I q0 are added to obtain a q-axis given current value I qref .
  • the weak magnetic control is performed on the difference between the maximum output voltage V max of the inverter and the output voltage amplitude V 1 of the inverter to obtain the initial value I d0 of the d-axis given current value; the initial value of the given current value of the d-axis I D0 performs clipping processing to obtain a d-axis given current value I dref .
  • the initial value I d0 of the d-axis given current value can be calculated by the following formula (3):
  • V d and V q are the d-axis given voltage value and the q-axis given voltage value, respectively, and V dc is the DC bus voltage of the motor drive system.
  • the d-axis given current value I dref is calculated by the following formula (4):
  • I demag is the motor demagnetization current limit value.
  • the coordinate transformation of the three-phase current to obtain the actual current values of the d-axis and the q-axis specifically includes:
  • I d I ⁇ cos ⁇ e +I ⁇ sin ⁇ e
  • q axis given current value and d, q axis actual current value to obtain the d, q axis given voltage value can be calculated by the following formula (7):
  • Vq is the Q axis given voltage
  • Vd is the D axis given voltage
  • Iqref is the Q axis given current
  • Idref is the D axis given current
  • Iq is the Q axis actual current
  • Id is the D axis actual current
  • Kpd and Kid is the D-axis current control proportional gain and integral gain respectively
  • Kpq and Kiq are Q-axis current control proportional gain and integral gain
  • ⁇ is the motor speed
  • Ke is the motor back-EMF coefficient
  • Ld and Lq are D-axis and Q-axis respectively.
  • the PWM control signal is generated to control the inverter as follows:
  • V ⁇ and V ⁇ After obtaining the given voltage value Vq of the Q axis and the given voltage value Vd of the D axis, the inverse inverse transformation of Vq and Vd according to the rotor angle ⁇ of the motor can be performed, and the voltage command on the fixed coordinate system is calculated by the following formula (8).
  • V ⁇ and V ⁇ After obtaining the given voltage value Vq of the Q axis and the given voltage value Vd of the D axis, the inverse inverse transformation of Vq and Vd according to the rotor angle ⁇ of the motor can be performed, and the voltage command on the fixed coordinate system is calculated by the following formula (8).
  • ⁇ is the rotor angle of the motor, and the above-mentioned estimated rotor angle ⁇ e can be taken here .
  • the Clark inverse transform is performed on the voltages V ⁇ and V ⁇ on the two-phase stationary coordinate system to obtain three-phase voltage values V u , V v , V w , which are calculated by the following formula (9):
  • the duty ratio calculation can be performed according to the DC bus voltage V dc and the three-phase voltage values V u , V v , V w to obtain a PWM control signal, that is, the three-phase duty ratios D u , D v , D w , specifically Calculated by the following formula (10):
  • the switching tube of the inverter is controlled according to the three-phase duty ratios D u , D v , D w to realize the control of the motor.
  • the control method of the motor drive system detects the DC bus voltage value and the three-phase current value of the drive motor, and obtains an average voltage value according to the DC bus voltage, and then obtains the voltage fluctuation amount according to the DC bus voltage value and the average voltage value. Finally, the inverter of the motor drive system is controlled according to the voltage fluctuation amount, the DC bus voltage value and the three-phase current value generating control signals to drive the motor to operate.
  • the control method provided by the invention can detect the fluctuation of the DC bus voltage in real time, and adjust the Iq current value in the motor drive system in real time by detecting the fluctuation, and finally control the motor, thereby reducing the fluctuation of the DC bus voltage, realizing the Realize high-power output when the electrolytic capacitor is increased, and solve the problem in the passive PFC scheme motor drive system when the load is too large
  • the output power of the transformer is too large, causing the ripple voltage on the DC bus voltage to cause the working life of the large electrolytic filter capacitor on the DC bus to decrease, which in turn affects the stability of the entire motor drive system.
  • the invention also provides a control device for a motor drive system.
  • control device of the motor drive system includes:
  • the current detecting module 10 is configured to detect a three-phase current value of the driving motor
  • the voltage detecting module 20 is configured to detect a DC bus voltage value of the motor driving system
  • the average voltage obtaining module 30 is configured to obtain an average voltage value according to the DC bus voltage value
  • the voltage fluctuation amount acquisition module 40 is configured to obtain a voltage fluctuation amount according to the DC bus voltage value and the average voltage value;
  • the control signal generating module 50 generates a control signal according to the voltage fluctuation amount, the DC bus voltage value, and the three-phase current value to control the inverter of the motor drive system to drive the motor to operate.
  • the current detecting module 10 can detect the DC bus voltage V dc of the motor driving system through the circuit structure of the voltage dividing resistor, and detect the three-phase current Iu, v, w of the motor through a single-resistor or three-resistor sampling circuit structure. These circuit structures belong to the prior art.
  • the average voltage acquisition module 30 can obtain the instantaneous voltage value V dc — ave of the period of time by detecting the instantaneous value of the DC bus voltage value V dc for a predetermined period of time and then averaging.
  • the voltage fluctuation amount acquisition module 40 obtains the voltage fluctuation amount ⁇ V dc by calculating the difference from the DC bus voltage V dc after detecting the average value V dc — ave of the DC bus voltage.
  • control signal generating module 50 specifically includes:
  • a q-axis current compensation calculation unit 501 configured to calculate a q-axis current compensation amount according to the voltage fluctuation amount
  • the q-axis current initial value obtaining unit 502 is configured to perform a difference calculation according to the motor target speed value and the actual motor speed estimation value, and then perform PI control to obtain an initial value of the q-axis current;
  • a q-axis given current value operation unit 503 for using the q-axis current compensation amount and The initial values of the q-axis currents are added to obtain a given current value of the q-axis;
  • the d-axis given current value operation unit 504 is configured to calculate a d-axis given current value according to the DC bus voltage value and the output voltage amplitude of the inverter;
  • the dq axis current operation unit 505 is configured to perform coordinate transformation on the three-phase current to obtain the d-axis and q-axis actual current values;
  • the dq axis voltage operation unit 506 is configured to calculate the d-axis given current value and the d-axis actual current value and the q-axis given current value and the q-axis actual current value respectively to obtain the d-axis given voltage value and the q-axis given Voltage value;
  • the PWM operation unit 507 is configured to generate a PWM control signal to control the inverter according to the d-axis given voltage value, the q-axis given voltage value, the DC bus voltage value, and the motor rotor angle estimation value.
  • ⁇ V dc voltage fluctuation amount calculated q-axis current compensation amount according to the time I q_com1 by performing PI control of the voltage fluctuation amount ⁇ V dc, calculated q-axis current compensation amount I q_com1.
  • the initial q-axis current value acquiring unit 502 acquires the initial value of the q-axis current I q0, it is possible, and the difference between the motor actual speed ⁇ m then calculated by the target motor speed value ⁇ m * PI control is obtained, wherein the actual value of the motor speed ⁇ m It can be detected by a position sensor in the motor, such as a Hall switch, or for a motor without a position sensor, the actual motor speed value ⁇ m is an estimated value. At this time, the acquisition of ⁇ m is as follows:
  • the rotor angle estimation value ⁇ est of the motor and the actual motor speed value ⁇ m are obtained by the flux linkage observation method. Specifically, first, an estimated value of the effective magnetic flux of the compressor motor in the directions of the two-phase stationary coordinate system ⁇ and ⁇ axes can be calculated according to the voltages V ⁇ , V ⁇ and the currents I ⁇ and I ⁇ on the two-phase stationary coordinate system.
  • the specific calculation formula is as follows:
  • V ⁇ and V ⁇ are the voltages in the ⁇ and ⁇ axis directions, respectively
  • I ⁇ and I ⁇ are the currents in the ⁇ and ⁇ axis directions, respectively.
  • R is the stator resistance
  • L q is the q-axis flux linkage of the compressor motor.
  • K p_pll and K i_pll are proportional integration parameters
  • ⁇ err is the deviation angle estimation value
  • ⁇ f is the bandwidth of the speed low-pass filter.
  • the q-axis given current value operation unit 503 adds the q-axis current compensation amount I q_com1 and the q-axis current initial value I q0 to obtain the q-axis given current value I qref .
  • the d-axis given current value operation unit 504 is further shown in FIG. 6.
  • the d-axis given current value operation unit 504 further includes a voltage amplitude calculation sub-unit 5041, a maximum output voltage value calculation sub-unit 5042, and a field weakening control sub-unit 5043.
  • the limiting subunit 5044, the d-axis given current value operation unit 504 calculates the d-axis given current value of the compressor motor according to the maximum output voltage of the inverter and the output voltage amplitude of the inverter, specifically including :
  • the field weakening control sub-unit 5043 performs field weakening control on the difference between the maximum output voltage V max of the inverter and the output voltage amplitude V 1 of the inverter to obtain an initial value I d0 of the d-axis given current value; the limiting subunit 5044 performs a limiting process on the initial value I d0 of the d-axis given current value to obtain a d-axis given current value I dref .
  • the weak magnetic control sub-unit 5043 can calculate the initial value I d0 of the d-axis given current value by the following formula (3):
  • K i is an integral control coefficient
  • the voltage amplitude calculation subunit 5041 passes the formula Calculating the output voltage amplitude V 1 of the inverter
  • the maximum output voltage value calculation subunit 5042 passes the formula
  • the maximum output voltage V max , V d and V q of the inverter are calculated as the d-axis given voltage value and the q-axis given voltage value, respectively, and V dc is the DC bus voltage of the motor drive system.
  • the limiting sub-unit 5044 performs limiting processing according to the initial value I d0 of the d-axis given current value, and calculates the d-axis given current value I dref by the following formula (4):
  • I demag is the motor demagnetization current limit value.
  • the dq axis current operation unit 505 performs coordinate transformation on the three-phase current to obtain the actual current values of the d-axis and the q-axis, and specifically includes:
  • the dq axis voltage operation unit 506 obtains the d and q axis given voltage values according to the d, q axis given current value and the d and q axis actual current values, which can be calculated by the following formula (7):
  • Vq is the Q axis given voltage
  • Vd is the D axis given voltage
  • Iqref is the Q axis given current
  • Idref is the D axis given current
  • Iq is the Q axis actual current
  • Id is the D axis actual current
  • Kpd and Kid is the D-axis current control proportional gain and integral gain respectively
  • Kpq and Kiq are Q-axis current control proportional gain and integral gain
  • ⁇ is the motor speed
  • Ke is the motor back-EMF coefficient
  • Ld and Lq are D-axis and Q-axis respectively.
  • the PWM operation unit 507 generates a PWM control signal according to the d, q axis given voltage value, the DC bus voltage value, and the motor rotor angle estimation value as follows:
  • the Park inverse transform can be performed on Vq and Vd according to the motor rotor angle ⁇ , and the voltage commands V ⁇ and V ⁇ on the fixed coordinate system are calculated by the following formula (8):
  • ⁇ is the rotor angle of the motor, and the above-mentioned estimated rotor angle ⁇ e can be taken here .
  • the Clark inverse transform is performed on the voltages V ⁇ and V ⁇ on the two-phase stationary coordinate system to obtain three-phase voltage commands V u , V v , V w , which are calculated by the following formula (9):
  • the duty ratio calculation can be performed according to the DC bus voltage V dc and the three-phase voltage commands V u , V v , V w to obtain a PWM control signal, that is, the three-phase duty ratios D u , D v , D w , specifically Calculated by the following formula (10):
  • the switching tube of the inverter is controlled according to the three-phase duty ratios D u , D v , D w to realize the control of the motor.
  • the DC bus voltage value and the three-phase current value of the drive motor are detected, and the average voltage value is obtained according to the DC bus voltage, and then the voltage fluctuation is obtained according to the DC bus voltage value and the average voltage value.
  • the inverter of the motor drive system is controlled according to the voltage fluctuation amount, the DC bus voltage value and the three-phase current value to generate a control signal to drive the motor to operate.
  • the control method provided by the invention can detect the fluctuation of the DC bus voltage in real time, and adjust the Iq current value in the motor drive system in real time by detecting the fluctuation, and finally control the motor, thereby reducing the fluctuation of the DC bus voltage, realizing the
  • the high-power output is realized when the electrolytic capacitor is increased, and the passive PFC scheme is applied to the motor drive system.
  • the load is too large, the output power of the inverter is too large, causing a ripple voltage on the DC bus voltage to cause DC.
  • the working life of the large electrolytic filter capacitor on the busbar is reduced, which in turn affects the stability of the entire motor drive system.
  • the present invention also provides an inverter air conditioner, including the above-mentioned control device of the motor drive system, and the motor of the inverter air conditioner may be a DC fan or a compressor.
  • the motor of the inverter air conditioner may be a DC fan or a compressor.
  • the inverter air conditioner provided by the embodiment of the invention can detect the fluctuation of the DC bus voltage in real time, and adjust the Iq current value in the motor drive system in real time by detecting the fluctuation, thereby reducing the fluctuation of the DC bus voltage, thereby achieving no increase
  • large electrolytic capacitors high-power output is realized, and the passive PFC scheme is solved in the motor drive system.
  • the load is too large, the output power of the inverter is too large, causing a waveform voltage on the DC bus voltage to cause a DC bus.
  • the working life of the large electrolytic filter capacitor is reduced, which in turn affects the stability of the entire motor drive system.

Abstract

L'invention concerne un procédé de commande et un dispositif de commande pour un système d'entraînement de moteur, et un climatiseur à fréquence variable. Au moyen de la détection d'une valeur de tension de bus CC et d'une valeur de courant triphasé permettant d'entraîner un moteur (S10), et selon une valeur de tension de bus CC, une valeur de tension moyenne est acquise (S20) ; ensuite, en fonction de la valeur de tension de bus CC et de la valeur de tension moyenne, un degré de fluctuation de tension est acquis (S30) ; et enfin, un signal de commande est généré en fonction du degré de fluctuation de tension, de la valeur de tension de bus CC et de la valeur de courant triphasé de manière à commander un onduleur du système d'entraînement de moteur, amenant ainsi le moteur à fonctionner (S40). Le procédé de commande peut détecter la fluctuation d'une tension de bus CC en temps réel, et régler une valeur de courant Iq dans le système d'entraînement de moteur en temps réel par détection de ladite fluctuation, ce qui permet de réduire le degré de fluctuation de la tension de bus CC.
PCT/CN2017/105300 2016-11-30 2017-10-09 Procédé de commande et dispositif de commande pour système d'entraînement de moteur et climatiseur à fréquence variable WO2018099187A1 (fr)

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