WO2018076491A1 - 一种高低频滤波阵子交织排列的紧凑型多波束天线阵列 - Google Patents

一种高低频滤波阵子交织排列的紧凑型多波束天线阵列 Download PDF

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WO2018076491A1
WO2018076491A1 PCT/CN2016/110020 CN2016110020W WO2018076491A1 WO 2018076491 A1 WO2018076491 A1 WO 2018076491A1 CN 2016110020 W CN2016110020 W CN 2016110020W WO 2018076491 A1 WO2018076491 A1 WO 2018076491A1
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array
sub
dielectric substrate
filter
column
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French (fr)
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章秀银
薛狄
吴裕锋
张垚
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South China University of Technology SCUT
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South China University of Technology SCUT
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/30—Combinations of separate antenna units operating in different wavebands and connected to a common feeder system

Definitions

  • the present invention relates to the field of mobile communications, and in particular to a compact multi-beam antenna array in which high and low frequency filter oscillators are interleaved.
  • channel capacity can be increased by in-band bandwidth or carrier bandwidth. Since the bandwidth of a single antenna is typically narrow, multi-passband base station antenna arrays are often used to simultaneously support multiple wireless system standards. On the other hand, it is also possible to increase the capacity of the channel by reducing the coverage of the base station antenna, that is, increasing the number of antennas. However, these methods often lead to an increase in the occupied area and construction costs. In order to solve the problem of communication capacity without increasing the occupied physical space, a multi-beam array can be used.
  • multi-beam base station arrays such as 3G (1710-2170MHz) and LTE (2490-2690MHz) are designed.
  • the cells form an array, and a duplexer is cascaded at the front end to decouple the operating frequency bands by designing a high isolation duplexer.
  • the duplexer will inevitably bring cascading losses, affecting the gain of the antenna.
  • this solution uses only one array, so independent ESC downtilt can not be performed for each band during WLAN optimization.
  • the second method is to use two sub-arrays covering the 3G frequency band and the LTE frequency band in parallel, and a decoupling network is added between the two sub-arrays to achieve the decoupling effect.
  • these decoupling networks will increase Adding the width of the antenna array also affects the radiation performance of the antenna such as radiation efficiency, front-to-back ratio, gain, and the like.
  • the present invention provides a high-low frequency filter oscillator. Interlaced array of compact multi-beam antennas.
  • a compact multi-beam antenna array in which high and low frequency filter oscillators are interlaced comprising a first sub-array operating on a substrate and a second sub-array operating on a second frequency band, the first sub-array And the second sub-array is interleaved, wherein the array elements of one sub-array are dispersedly distributed in a space between the other sub-array array elements, and the first sub-array is composed of at least one first filter antenna unit without an additional loss circuit.
  • the second sub-array is comprised of at least one second filtered antenna element without an additional loss circuit.
  • the first filter antenna unit and the second filter antenna unit are specifically a dual-polarization filter antenna with high selectivity and low cross-polarization, including a first dielectric substrate and a second dielectric substrate in order from top to bottom. Supporting the third dielectric substrate and the fourth dielectric substrate;
  • the upper surface of the first dielectric substrate prints a parasitic radiation metal patch for generating and controlling a radiation zero at a high frequency of the radiant passband;
  • the lower surface of the fourth dielectric substrate is a metal floor.
  • the main radiating metal patch is printed on the upper surface of the second dielectric substrate, the two feeding lines are respectively a first feeding line and a second feeding line, and the first and second feeding lines are all H-shaped and orthogonally coupled.
  • the first feed line is printed on a lower surface of the second dielectric substrate, and a part of two vertical lines and a middle horizontal line of the H-type in the second feed line are printed on a lower surface of the second dielectric substrate, and a second horizontal line of the second feed line
  • Another portion is printed on the upper surface of the second dielectric substrate and is joined to a portion printed on the lower surface by a metallized via, the geometric center of the second dielectric substrate coinciding with the geometric center of the main radiant metal patch.
  • the second dielectric substrate further includes an annular groove line for separating another portion of the second transverse line of the second feed line from the main radiating metal patch, and further comprising a supporting aluminum plate disposed on a lower surface of the metal floor.
  • the first sub-array and the second sub-array are arranged in parallel by a column or more of the filter antenna unit sub-columns.
  • the n-th sub-column and the n+1th sub-column are alternately staggered, nth The sub-column and the n+2 sub-column are arranged side by side in parallel.
  • first and second sub-arrays three adjacent array elements located in the nth, n+1th, and n+2th sub-columns The triangles are arranged to increase the distance between the elements.
  • the first sub-array is composed of 16 first filter antenna units arranged in a 4 ⁇ 4 arrangement
  • the second sub-array is composed of 16 second filter antenna units arranged in a 4 ⁇ 4 arrangement.
  • Each sub-array is fed by a beam-formed network containing a Butler matrix and a power divider.
  • Two or multiple beams are implemented by controlling the beamforming network for single or dual polarization.
  • the two high and low frequency patch arrays of the present invention have filtering characteristics, can realize efficient radiation in the band, and effectively suppress the out-of-band, and the passband edge of the gain is quickly rolled off, and the duplexer or the decoupling network can be omitted. In the case of the case, the mutual coupling between the operating frequency bands is reduced.
  • the interlaced array of the present invention can reduce the size compared to the high and low frequency array separation arrangement array, and the mutual coupling effect is small compared to the filterless array interlaced array, which can maintain good isolation performance, that is,
  • the antenna array of the high frequency filter array and the low frequency filter array filter array of the present invention takes into consideration the advantages of small size and good isolation performance.
  • FIG. 1 is a top plan view of a compact multi-beam antenna array in which high and low frequency filtering arrays are interleaved according to an embodiment of the present invention
  • FIG. 2 is a schematic diagram of a split structure of a filter antenna unit according to an embodiment of the present invention.
  • FIG. 3 is a side elevational view of the filter antenna unit shown in Figure 2;
  • Figure 4 is a front elevational view of the filter antenna unit shown in Figure 2;
  • Figure 5 is a plan view of the filter antenna unit shown in Figure 2;
  • Figure 6 is a diagram showing the upper surface of the second dielectric substrate of the filter antenna unit shown in Figure 2;
  • Figure 7 is a view showing the lower surface of the second dielectric substrate of the filter antenna unit shown in Figure 2
  • Figure 8 is a bottom plan view of the filter antenna unit shown in Figure 2;
  • FIG. 9 is a schematic diagram of a feed network including a Butler matrix and a power splitter in front of each 2 ⁇ 8 subarray in the compact multi-beam antenna array of the high and low frequency filter array interleaving shown in FIG. 1.
  • Figure 10 is the S parameter of the filtering unit in the 3G band.
  • Figure 11 is an S parameter of the filtering unit in the LTE band.
  • Figure 12 is the gain of the 3G band and the LTE band when the first port of the filtering unit is fed.
  • Figure 13 is a gain of the 3G band and the LTE band when the second port of the filtering unit is fed.
  • FIG. 14 is a reflection coefficient of four input ports of a feed network connected to a first sub-array of an array according to an embodiment of the present invention.
  • FIG. 15 is a reflection coefficient of four input ports of a feed network connected to a second sub-array of an array according to an embodiment of the present invention.
  • FIG. 16 is a diagram showing transmission coefficients between four input ports of a feed network connected to a first sub-array of an array according to an embodiment of the present invention.
  • 17 is a transmission coefficient of four input ports of a feed network connected to a second sub-array of an array according to an embodiment of the present invention.
  • FIG. 18 is a diagram showing transmission coefficients between four input ports of a feed network and a feed port of a feed network connected to a second sub-array of the first sub-array of the array according to an embodiment of the present invention.
  • 19 is a horizontal radiation pattern of a first beam of a first polarization mode at a second sub-array of an array according to an embodiment of the present invention.
  • 20 is a horizontal radiation pattern of a second beam of a first polarization mode at a second sub-array of an array according to an embodiment of the present invention
  • 21 is a horizontal radiation pattern of a first beam of a second polarization mode of the first sub-array of the array according to an embodiment of the present invention
  • 22 is a horizontal radiation pattern of a first beam of a second polarization mode of the first sub-array of the array according to an embodiment of the present invention
  • 23 is a horizontal radiation pattern of a first beam of a first polarization mode at 2.6 GHz of a second sub-array of an array according to an embodiment of the present invention
  • 24 is a horizontal radiation pattern of a second beam of a first polarization mode at 2.6 GHz of a second sub-array of an array according to an embodiment of the present invention
  • 25 is a horizontal radiation pattern of a first beam of a second polarization mode at 2.6 GHz of a second sub-array of an array according to an embodiment of the present invention
  • 26 is a horizontal radiation pattern of a second beam of a second polarization mode at 2.6 GHz of a second sub-array of an array according to an embodiment of the present invention.
  • a compact multi-beam antenna array in which high and low frequency filter oscillators are interleaved comprising being disposed on a substrate
  • the number of array elements of the two subarrays may be the same or different, and the first frequency band and the second frequency band are completely different.
  • the interlaced array is arranged, and the size can be reduced compared to the high-low frequency array separation arrangement, compared with the mutual interference array without the filter characteristic.
  • the coupling effect is small and can maintain good isolation performance. That is, the advantages of small size and good isolation performance are taken into consideration.
  • the embodiment of the present invention is not limited to the dual-frequency dual-polarized dual beam.
  • the base station antenna array should include all of the multi-frequency multi-beam dual-polarized or single-polarized base station antenna arrays having the features of the present invention.
  • the first sub-array 1 operating on the first frequency band and the second sub-array 2 operating in the second frequency band are disposed on the substrate 3, and the first sub-array and the second sub-array are interleaved.
  • the first frequency band is different from the second frequency band, for example, the first frequency band is the 3G frequency band (1710-2170MHz), and the second frequency band is the LTE frequency band (2490-2690MHz).
  • the two frequency bands are only used for illustration, and Not for use in restrictions.
  • the first sub-array and the second sub-array are interleaved, wherein array elements of one sub-array are dispersedly distributed in a space between another sub-array array element.
  • L1-L16 represent the array elements of the first sub-array
  • H1-H16 represent the array elements of the second sub-array.
  • the first sub-array is composed of at least one first filter antenna unit without an additional loss circuit
  • the second sub-array is composed of at least one second filter antenna unit without an external loss circuit
  • the filter characteristics of the filter antenna unit itself are two
  • the mutual coupling between the column sub-arrays is greatly reduced.
  • the first filter antenna unit and the second filter antenna unit have the same structure but different sizes due to different operating frequencies.
  • the first filtered antenna unit having a large size operates at a lower frequency first.
  • the second filter antenna unit having a small size operates in the second frequency band with higher frequency (for example, the LTE frequency band).
  • the size of the substrate 3 can also be set according to the number and size of the sub-arrays.
  • the first filter antenna unit and the second filter antenna unit are specifically a dual-polarization filter antenna with high selectivity and low cross-polarization, and include a first dielectric substrate 5 and a second dielectric substrate 10 in order from top to bottom. a third dielectric substrate 14 and a fourth dielectric substrate 15 for supporting;
  • the upper surface of the first dielectric substrate 5 is printed for generating and controlling radiation at a high frequency of the radiant passband Zero-point parasitic radiation metal patch 4;
  • the lower surface of the fourth dielectric substrate 15 is a metal floor 16.
  • the main radiating metal patch 9 is printed on the upper surface of the second dielectric substrate 10.
  • the two feeding lines are respectively a first feeding line 13 and a second feeding line, and the first and second feeding lines are all H-shaped and positive. Cross-coupling, the first feed line 13 is printed on a lower surface of the second dielectric substrate 10, and two vertical lines of the H-type and a portion 12 of the intermediate horizontal line of the second feed line are printed on a lower surface of the second dielectric substrate, Another portion 7 of the second transverse line of the second feed line is printed on the upper surface of the second dielectric substrate 10 and is connected to a portion printed on the lower surface by two metallized vias 6, the geometric center and the main radiation of the second dielectric substrate The geometric centers of the metal patches coincide.
  • the second dielectric substrate 10 further includes an annular groove line 8 for separating another portion of the second transverse line of the second feeder from the main radiant metal patch 9; further comprising a supporting aluminum plate 17 disposed on the metal floor 16 lower surface.
  • the first sub-array and the second sub-array are composed of a column or more of the filter antenna unit sub-columns arranged in parallel, and the n-th sub-column and the n+1th sub-column are arranged in parallel in the sub-array.
  • the nth sub-column and the n+2 sub-column are arranged side by side in parallel.
  • the first and second sub-arrays Preferably, in the first and second sub-arrays, three adjacent array elements located in the nth, n+1th, and n+th sub-columns are arranged in a triangle to increase the relationship between the array elements. distance.
  • only one sub-column of the second sub-array exists between the n-th sub-column and the n+2 sub-column of the first sub-array.
  • the first sub-array is composed of 16 first filter antenna units in a 4 ⁇ 4 arrangement
  • the second sub-array is composed of 16 second filter antenna units in a 4 ⁇ 4 arrangement.
  • each of the sub-arrays is fed by two beam-formed networks including a Butler matrix and a power divider, respectively controlling two polarization modes of the sub-array.
  • the compact multi-beam antenna array implements two or multiple beams by controlling a beamforming network for single polarization or dual polarization.
  • the structure of the first filter antenna unit and the second filter antenna unit will be described in detail below with reference to FIGS. 2-8.
  • the first filter antenna unit and the second filter antenna unit have substantially the same structure except for the difference in size.
  • the filter antenna unit is uniformly used to represent the first filter antenna unit and the second filter antenna unit.
  • the filter antenna units each include a first dielectric substrate 5, a second dielectric substrate 10, and a third dielectric plate 14 and a fourth dielectric plate 15 for supporting, and a supporting aluminum plate 17.
  • First medium base A parasitic radiation metal patch 4 is disposed on the upper surface of the board 5, and an upper surface portion 7 of the main radiation metal patch 9 and the second H-shaped feeder line is disposed on the upper surface of the second dielectric substrate 10, and the second dielectric substrate 10 is disposed on the upper surface of the second dielectric substrate 10.
  • a first H-shaped feeder 13 and a lower portion 12 of the second H-shaped feeder are disposed on the lower surface, and the lower surface of the fourth dielectric substrate 15 is provided with a metal floor 16.
  • the parasitic radiation metal patch 4, the main radiation metal patch 9 and the metal floor 16 are all metal plating.
  • a metal shorting probe 6 is connected between the upper surface portion 7 and the lower surface portion 12 of the second H-shaped feeder. Specifically, as shown in FIGS. 2, 3, and 4, two metal probes 6 are provided.
  • a supporting aluminum plate 17 is provided. As shown in Figures 2, 3 and 4, a supporting aluminum plate 17 is provided. As shown in Fig. 8, the center of the supporting aluminum plate has a square groove for the coaxial line of the input feeding, and the reference numeral 11 is the inside of the coaxial line.
  • the first dielectric substrate 5, the second dielectric substrate 10, and the third dielectric plate 14 and the fourth dielectric plate 15 for support are both made of F4B material and have a dielectric constant of 2.65.
  • the total length of the first feed line 13 and the second feed line is about one quarter of the wavelength, and the position of the zero point can be adjusted by adjusting the length of the feed line.
  • the beamforming network is composed of a Butler matrix and a power splitter.
  • the Butler matrix has two input ports (A, B) that control different beams of the same polarization mode of the sub-array.
  • the first sub-array first polarization mode Butler matrix has four output ports (C, D, E, F), each port of the Butler matrix and a one-fourth splitter ( H, M, N, P) connections.
  • the four output ports of the power splitter H are respectively connected to the filtering units of the four 3G frequency bands of the first sub-column of the first sub-array.
  • the four output ports of the power splitter M are respectively connected to the filtering units of the four 3G frequency bands of the second sub-column of the first sub-array.
  • the four output ports of the power splitter N are respectively connected to the filtering units of the four 3G frequency bands of the third sub-column of the first sub-array.
  • the four output ports of the power splitter P are respectively connected to the filtering units of the four 3G frequency bands of the fourth sub-column of the first sub-array.
  • the first sub-array second polarization mode, the second sub-array first polarization mode, and the second sub-array second polarization mode beamforming network are similar.
  • the two filter frequency antenna units in the 3G frequency band and the LTE frequency band, respectively, which do not have an external loss circuit, and the two filter antenna units adopt the circuit structure shown in FIG.
  • the working frequency bands are different, so the specific circuit size is different, and the circuit design dimensions of the corresponding filter antenna unit without the external loss circuit are as follows:
  • the working frequency bands of the two sub-arrays are 1710-2170 MHz and 2490-2690 MHz, and the sub-arrays of the 3G frequency band are efficiently radiated in the working frequency band 1710-2170 MHz, and the radiation is suppressed in the outband band, ie, the LTE frequency band (2490-2690 MHz);
  • the sub-array of the LTE frequency band radiates efficiently in its operating frequency range of 2490-2690 MHz MHz, and suppresses radiation in the out-of-band, ie, 3G frequency band (1710-2170 MHz). Therefore, the radiation between the two sub-arrays does not interfere with each other, thereby reducing mutual interference and achieving higher port isolation.
  • FIG. 10 it is a reflection coefficient S-parameter of a filter antenna unit of an external lossless circuit operating in the 3G frequency band according to an embodiment of the present invention. It can be seen that there are two resonance modes in the working frequency band of 1710-2170MHz, and in the S11-frequency curve, S11 is lower than -15dB in the 3G frequency band. In the S21-frequency curve, S21 is below -30 dB in the 3G band.
  • FIG. 11 it is a reflection coefficient S-parameter of a filter antenna unit of an LTE band without an external loss circuit provided by an embodiment of the present invention. It can be seen that there are also two resonance modes in the working frequency band of 2490-2690MHz. In the S11-frequency curve, S11 is lower than -15dB in the LTE frequency band. In the S21-frequency curve, S21 is below -30 dB in the LTE band.
  • one port ( FIG. 12 ) and two ports ( FIG. 13 ) of the filter antenna unit of the 3G band and the LTE band without the external loss circuit provided by the embodiment of the present invention are respectively excited.
  • the gain-frequency curve shows that the gain in the 3G band is about 8.5 dBi, while the gain in the LTE band is about 8.2 dBi, and the gain of the radiated zero is below -20 dBi.
  • the passband edge is steep, the sideband suppression is obvious, the selectivity is good, and the in-band gain is flat.
  • FIG. 14 15 16, 17, and 18, it is a simulation result graph of reflection coefficient-frequency, transmission coefficient-frequency of a compact multi-beam antenna array in which high and low frequency filter arrays are interleaved according to an example of the present invention.
  • the S11 of the array is lower than -22dB, indicating that the matching of the port is good.
  • the S12 of the array is lower than -25dB, indicating that the mutual coupling between the sub-arrays of the array is small and the port isolation is high.
  • the beam isolation of the array reaches 15 dB in the entire 3G frequency band (1710-2170 MHz) and the LTE frequency band (2490-2690 MHz), indicating that the beam isolation of the array is good.
  • Figure 19-26 shows the horizontal plane pattern of each beam of the antenna array at 2.0 GHz and 2.6 GHz, respectively, which also shows that the antenna array is stable. Radiation pattern.
  • the antenna array itself has filtering performance, the passband edge is steep, the sideband suppression is obvious, and the frequency selection characteristic is good. No additional duplexer or decoupling network circuit is needed, and the use of extra duplex is overcome. Or decoupling networks are prone to large losses;
  • the antenna array is suitable for the 3G frequency band and the LTE frequency band, and realizes high isolation of the port, suppresses the interference of the adjacent frequency, and improves the performance of the base transceiver station without the need of the decoupling circuit;
  • the sub-array of the antenna array is interleaved, and the array consisting of the high-frequency filtering matrix and the low-frequency filtering matrix filtering matrix interleaving arrangement is fed through a feeder network design including a Butler matrix, which can be compacted.
  • a feeder network design including a Butler matrix, which can be compacted.
  • Type multi-beam base station antenna array which reduces the size of the array compared to the split arrangement array;
  • the whole structure is mainly composed of metal patch, metalized via, dielectric plate through hole and ring groove, which has simple structure and simple design.
  • the antenna array is a multi-beam array with narrow beam and high gain, which is suitable for sector division and can cover a long distance.
  • the embodiments provided by the present invention are applicable to the field of wireless mobile communication base stations, and can be applied to receiving and transmitting devices of various types of wireless communication systems. Due to the filtering characteristics of the present invention, the invention is particularly suitable for use in an open complex multi-band multi-standard communication scenario. , base station antennas operating in the 3G band and the LTE band. At the same time, benefiting from the integration of the filtering characteristics and the radiation characteristics, the present invention is also applicable to the integration and integration of wireless mobile communication system equipment, reducing design requirements, and improving the ability of communication equipment to resist adjacent frequency interference.
  • a compact multi-beam base station antenna array can be realized by feeding through a feeding network including a Butler matrix.
  • An exemplary compact base station antenna array achieves two beam coverage 120[deg.] sectors in the horizontal plane, and the vertical plane forms a narrow beam radiation pattern of sidelobe suppression. Due to the filtering characteristics of the interleaved patch array, the mutual coupling between the high frequency array and the low frequency array is greatly reduced.

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Abstract

本发明公开了一种高低频滤波振子交织排列的紧凑型多波束天线阵列，包括设置于基板上的工作于第一频段的第一子阵列及工作于第二频段的第二子阵列，所述第一子阵列及第二子阵列交织排列，其中一个子阵列的阵元分散分布在另一个子阵列阵元之间的空间，所述第一子阵列由至少一个无外加损耗电路的第一滤波天线单元构成，所述第二子阵列由至少一个无外加损耗电路的第二滤波天线单元构成。整个阵列由两个频段的阵子交织排布组阵，相比高频阵子和低频阵子分离排布组阵的设计，可以减少尺寸；相比没有滤波特性的阵子交织组阵的设计，阵子之间的相互耦合作用更小，能够保持良好的隔离性能。

Description

一种高低频滤波阵子交织排列的紧凑型多波束天线阵列 技术领域
本发明涉及移动通信领域，具体涉及一种高低频滤波振子交织排列的紧凑型多波束天线阵列。
背景技术
随着数据信息量的爆炸式的增加，对通信系统的容量提出了越来越多的要求，尤其是在人流量特别大的地方，比如，广场，车站，景区，宿舍等地。一方面，可以通过带内带宽或载波带宽来增加信道容量。由于单天线的带宽通常比较窄，所以通常使用多通带基站天线阵列来同时支持多种无线系统标准。另一方面，也可以通过降低基站天线的覆盖范围，即增加天线的数量来增加信道的容量。但这些方法往往会导致占用面积和建设成本的增加。为了在解决通信容量的问题的同时又不增加所占的物理空间，可以使用多波束阵列。
对于减少天线阵列尺寸，已有人提出了一种交织排布的方式，参考文献《F.Hyjazie,P.Watson,and H.Boutayeb,“Dual band interleaved base station phased array antenna with optimized cross-dipole and EBG/AMC structure,”in Proc.IEEE Antennas Propag.Soc.Int.Symp.,2014,pp.1558-1559.》但是由于阵子没有滤波特性，相互耦合性能有所影响。为了克服耦合性和结构复杂性的缺陷，文献《Y.Zhang,X.Y.Zhang,L.Ye,and Y.-M.Pan,“Dual-band base-station array using filtering antenna elements for mutual coupling suppression,”IEEE Trans.Antennas Propag.,vol.64,no.8,pp.3423-3430,Aug.2016》提出一种紧凑型多频基站天线阵列，但该阵列每个频段仅拥有一个波束。
在工程运用中，设计多波束基站阵列如3G(1710-2170MHz)和LTE(2490-2690MHz)频段，常用的方法有两种，一是用一列覆盖3G和LTE整个频段(1710-2690MHz)的天线单元组成一个阵列，在前端级联一个双工器，通过设计高隔离度的双工器来进行工作频段之间的去耦合。然而，双工器必然会带来级联损耗，影响天线的增益。除此之外，该种方案仅仅使用一个阵列，因此在无线局域网优化的过程中无法对每个频段进行独立的电调下倾角。第二种方法是使用分别覆盖3G频段和LTE频段的两个子阵列并行排列，在两个子阵列之间加入去耦合网络，从而达到去耦合的效果。然而，这些去耦合网络会增 加天线阵列的宽度，也会影响天线的辐射性能如辐射效率、前后比、增益等等。
发明内容
为了克服现有技术中多频基站高低频阵子分离排布组阵的尺寸过大问题和没有滤波特性阵子交织组阵的相互耦合强、隔离性能差的缺陷，本发明提供一种高低频滤波振子交织排列的紧凑型多波束天线阵列。
本发明采用如下技术方案：
一种高低频滤波振子交织排列的紧凑型多波束天线阵列，包括设置于基板上的工作于第一频段的第一子阵列及工作于第二频段的第二子阵列，所述第一子阵列及第二子阵列交织排列，其中一个子阵列的阵元分散分布在另一个子阵列阵元之间的空间，所述第一子阵列由至少一个无外加损耗电路的第一滤波天线单元构成，所述第二子阵列由至少一个无外加损耗电路的第二滤波天线单元构成。
所述第一滤波天线单元及第二滤波天线单元具体为一种具有高选择性和低交叉极化的双极化滤波天线，由上至下依次包括第一介质基板、第二介质基板、用于支撑的第三介质基板及第四介质基板；
所述第一介质基板的上表面印刷用于产生和控制辐射通带高频处的辐射零点的寄生辐射金属贴片；
所述第二介质基板印刷主辐射金属贴片及两条馈线；
所述第四介质基板的下表面为金属地板。
所述主辐射金属贴片印刷在第二介质基板的上表面，所述两条馈线分别为第一馈线及第二馈线，所述第一及第二馈线均为H型，且正交耦合，所述第一馈线印刷在第二介质基板的下表面，所述第二馈线中H型的两条竖线及中间横线的一部分印刷在第二介质基板的下表面，第二馈线中间横线的另一部分印刷在第二介质基板的上表面，并通过金属化过孔与印刷在下表面的一部分连接，所述第二介质基板的几何中心与主辐射金属贴片的几何中心重合。
所述第二介质基板还包括用于隔开第二馈线中间横线的另一部分与主辐射金属贴片的环形槽线，还包括支撑铝板，支撑铝板设置在金属地板的下表面。
所述第一子阵列及第二子阵列由一列以上的滤波天线单元子纵列平行排布构成，子阵列中，第n子纵列和第n+1子纵列平行交错排布，第n子纵列和第n+2子纵列平行并列排布。
第一及第二子阵列中，位于第n、第n+1、第n+2子纵列的三个相邻阵元之 间成三角形排布，用以增加阵元之间的距离。
第一子阵列的第n子纵列和第n+2子纵列之间只存在第二子阵列的一个子纵列。
第一子阵列由16个第一滤波天线单元呈4×4排列构成，第二子阵列由16个第二滤波天线单元呈4×4排列构成。
每一个子阵列由含巴特勒矩阵和功分器的波束赋形的网络进行馈电。
通过控制波束赋形网络来实现两波束或多波束，用于单极化或双极化。
本发明的有益效果：
(1)本发明的两种高低频贴片阵子具有滤波特性，可实现在带内高效辐射，带外有效抑制，增益的通带边沿滚降很快，可以无需设计双工器或者去耦合网络的情况下减小工作频段间的相互耦合。
(2)本发明交织排布组阵，相比高低频阵子分离排布组阵可以减少尺寸，相比没有滤波特性阵子交织组阵的相互耦合作用小，能够保持良好的隔离性能，也就是说本发明的高频滤波阵子和低频滤波阵子滤波阵子交织的天线阵列兼顾了尺寸小和隔离性能好的优点。
附图说明
图1是本发明实施例提供的高低频滤波阵子交织的紧凑型多波束天线阵列的俯视图；
图2是本发明实施例提供的滤波天线单元的拆分结构示意图；
图3是图2所示的滤波天线单元的侧视图；
图4是图2所示的滤波天线单元的正视图；
图5是图2所示的滤波天线单元的俯视图；
图6是图2所示的滤波天线单元的第二介质基板上表面的图
图7是图2所示的滤波天线单元的第二介质基板下表面的图
图8是图2所示的滤波天线单元的仰视图；
图9是图1所示高低频滤波阵子交织的紧凑型多波束天线阵列中每个2×8的子阵列前面的含巴特勒矩阵和功分器的馈电网络示意图。
图10是滤波单元在3G频段的S参数。
图11是滤波单元在LTE频段的S参数。
图12是滤波单元第一端口馈电时在3G频段和LTE频段的增益。
图13是滤波单元第二端口馈电时在3G频段和LTE频段的增益。
图14是本发明一个实施例提供的阵列的第一子阵列所接馈电网络四个输入端口的反射系数。
图15是本发明一个实施例提供的阵列的第二子阵列所接馈电网络四个输入端口的反射系数。
图16是本发明一个实施例提供的阵列的第一子阵列所接馈电网络四个输入端口相互之间的传输系数。
图17是本发明一个实施例提供的阵列的第二子阵列所接馈电网络四个输入端口相互之间的传输系数。
图18是本发明一个实施例提供的阵列的第一子阵所列接馈电网络四个输入端口与第二子阵列所接馈电网络四个输入端口相互之间的传输系数。
图19是本发明一个实施例提供的阵列的第一子阵列在2.0GHz处的第一个极化方式的第一波束的水平辐射方向图；
图20是本发明一个实施例提供的阵列的第一子阵列在2.0GHz处的第一个极化方式的第二波束的水平辐射方向图；
图21是本发明一个实施例提供的阵列的第一子阵列在2.0GHz处的第二个极化方式的第一波束的水平辐射方向图；
图22是本发明一个实施例提供的阵列的第一子阵列在2.0GHz处的第二个极化方式的第一波束的水平辐射方向图；
图23是本发明一个实施例提供的阵列的第二子阵列在2.6GHz处的第一个极化方式的第一波束的水平辐射方向图；
图24是本发明一个实施例提供的阵列的第二子阵列在2.6GHz处的第一个极化方式的第二波束的水平辐射方向图；
图25是本发明一个实施例提供的阵列的第二子阵列在2.6GHz处的第二个极化方式的第一波束的水平辐射方向图；
图26是本发明一个实施例提供的阵列的第二子阵列在2.6GHz处的第二个极化方式的第二波束的水平辐射方向图。
具体实施方式
下面结合实施例及附图，对本发明作进一步地详细说明，但本发明的实施方式不限于此。
实施例
一种高低频滤波振子交织排列的紧凑型多波束天线阵列，包括设置于基板 上的工作于第一频段的第一子阵列及工作于第二频段的第二子阵列，所述第一子阵列及第二子阵列交织排列，其中一个子阵列的阵元分散分布在另一个子阵列阵元之间的空间，所述第一子阵列由至少一个无外加损耗电路的第一滤波天线单元构成，所述第二子阵列由至少一个无外加损耗电路的第二滤波天线单元构成，两个子阵的阵元数目可以相同，也可以不同，第一频段及第二频段完全不同。
通过运用无外加损耗电路的滤波天线单元作为多频基站天线阵列的阵子，交织排布组阵，相比高低频阵子分离排布组阵可以减少尺寸，相比没有滤波特性阵子交织组阵的相互耦合作用小，能够保持良好的隔离性能。即，兼顾了尺寸小和隔离性能好的优点。
为了便于描述，下文和附图都将以双频基站天线阵列为例来说明本发明实施例提供的天线阵列的机构，应当理解的是，本发明实施例并不限于双频双极化双波束基站天线阵列，而应包含所有具备本发明特征的所有多频多波束双极化或单极化基站天线阵列。
如图1所示，包括设置于基板3上的工作于第一频段的第一子阵列1及工作于第二频段的第二子阵列2，所述第一子阵列及第二子阵列交织排列，其中，第一频段与第二频段不同，例如第一频段是3G频段(1710-2170MHz)，第二频段是LTE频段(2490-2690MHz)，当然列举这两个频段仅用于举例说明，而不用于限制。所述第一子阵列及第二子阵列交织排列，其中一个子阵列的阵元分散分布在另一个子阵列阵元之间的空间。
图1中L1-L16表示第一子阵列的阵元，H1-H16表示第二子阵列的阵元。
第一子阵列由至少一个无外加损耗电路的第一滤波天线单元构成，所述第二子阵列由至少一个无外加损耗电路的第二滤波天线单元，滤波天线单元本身所具有的滤波特性使得两列子阵列之间的相互耦合大大减少。由于工作频率不同，第一滤波天线单元和第二滤波天线单元的结构相同，但是尺寸不同，在图1所示的实施例中，尺寸大的第一滤波天线单元工作在频率较低的第一频段(例如3G频段)，尺寸小的第二滤波天线单元工作在频率较高的第二频段(例如LTE频段)。基板3的尺寸也可以根据子阵列的数量和规模进行设置。
所述第一滤波天线单元及第二滤波天线单元具体为一种具有高选择性和低交叉极化的双极化滤波天线，由上至下依次包括第一介质基板5、第二介质基板10、用于支撑的第三介质基板14及第四介质基板15；
所述第一介质基板5的上表面印刷用于产生和控制辐射通带高频处的辐射 零点的寄生辐射金属贴片4；
所述第二介质基板印刷主辐射金属贴片9及两条馈线；
所述第四介质基板15的下表面为金属地板16。
所述主辐射金属贴片9印刷在第二介质基板10的上表面，所述两条馈线分别为第一馈线13及第二馈线，所述第一及第二馈线均为H型，且正交耦合，所述第一馈线13印刷在第二介质基板10的下表面，所述第二馈线中H型的两条竖线及中间横线的一部分12印刷在第二介质基板的下表面，第二馈线中间横线的另一部分7印刷在第二介质基板10的上表面，并通过两个金属化过孔6与印刷在下表面的一部分连接，所述第二介质基板的几何中心与主辐射金属贴片的几何中心重合。
所述第二介质基板10还包括用于隔开第二馈线中间横线的另一部分与主辐射金属贴片9的环形槽线8；还包括支撑铝板17，支撑铝板17设置在金属地板16的下表面。
优选地，所述第一子阵列及第二子阵列由一列以上的滤波天线单元子纵列平行排布构成，子阵列中，第n子纵列和第n+1子纵列平行交错排布，第n子纵列和第n+2子纵列平行并列排布。
优选地，第一及第二子阵列中，位于第n、第n+1、第n+2子纵列的三个相邻阵元之间成三角形排布，用以增加阵元之间的距离。
优选地，所述的紧凑型多波束天线阵列，第一子阵列的第n子纵列和第n+2子纵列之间只存在第二子阵列的一个子纵列。
优选地，所述的紧凑型多波束天线阵列，第一子阵列由16个第一滤波天线单元呈4×4排列构成，第二子阵列由16个第二滤波天线单元呈4×4排列构成。
优选地，所述每一个子阵列由两个含巴特勒矩阵和功分器的波束赋形的网络进行馈电，分别控制子阵列的两个极化方式。
优选地，所述的紧凑型多波束天线阵列，通过控制波束赋形网络来实现两波束或多波束，用于单极化或双极化。
下面将参考图2-8详细描述第一滤波天线单元和第二滤波天线单元的结构。第一滤波天线单元和第二滤波天线单元除了尺寸不同外，结构基本相同。为了方便描述，下文参考图2-8的举例说明中，统一使用滤波天线单元来表示第一滤波天线单元和第二滤波天线单元。
如图2、图3和图4所示，滤波天线单元均包括第一介质基板5、第二介质基板10和支撑用的第三介质板14和第四介质板15、支撑铝板17。第一介质基 板5的上表面上设置有寄生辐射金属贴片4，第二介质基板10的上表面上设置有主辐射金属贴片9和第二个H形馈线的上表面部分7，第二介质基板10的下表面上设置第一个H形馈线13和第二个H形馈线的下面部分12，第四介质基板15下表面设置有金属地板16。寄生辐射金属贴片4、主辐射金属贴片9和金属地板16均为金属镀层。第二个H形馈线的上表面部分7和下表面部分12之间连有金属短路探针6。具体地，如图2、3、4所示，设置有两个金属探针6。如图2、3、4所示，设有支撑铝板17，如图8所示，支撑铝板上的中心有一个正方形槽，供输入馈电的同轴线通过，标号11为同轴线的内芯，主辐射金属贴片9的几何中心位置处环形槽线8。
其中，第一介质基板5、第二介质基板10和支撑用的第三介质板14和第四介质板15，均采用F4B材料，介电常数为2.65。
优选地，如图2、3、4所示，所述第一馈线13和第二馈线的总长约为波长的四分之一，可以通过调节馈线的长度来调节零点的位置。
如图9所示，是本发明一个实施例的波束赋形网络及其和滤波单元的连接情况。优选的，所述波束赋形网络由巴特勒矩阵和功分器组成。所述巴特勒矩阵拥有两个输入端口(A、B)，所述端口A、B分别控制子阵列的同一极化方式的不同的波束。所述第一子阵列第一极化方式的巴特勒矩阵拥有四个输出端口(C、D、E、F)，所述巴特勒矩阵的每个端口分别与一个一分四的功分器(H、M、N、P)连接。所述功分器H的四个输出端口分别连接第一子阵列的第一子纵列的四个3G频段的滤波单元。所述功分器M的四个输出端口分别连接第一子阵列的第二子纵列的四个3G频段的滤波单元。所述功分器N的四个输出端口分别连接第一子阵列的第三子纵列的四个3G频段的滤波单元。所述功分器P的四个输出端口分别连接第一子阵列的第四子纵列的四个3G频段的滤波单元。第一子阵列第二极化方式、第二子阵列第一极化方式以及第二子阵列第二极化方式的波束赋形网络类似。
在本发明的一个示范性实施例中，有两个工作频段分别为3G频段和LTE频段的无外加损耗电路的滤波天线单元，这两个滤波天线单元均采用图2所示的电路结构，由于工作频段不同，所以具体的电路尺寸不同，其对应的无外加损耗电路的滤波天线单元的电路设计尺寸如下表所示：
Figure PCTCN2016110020-appb-000001
Figure PCTCN2016110020-appb-000002
阵列的设计尺寸如下：Lx＝1.10mm888888888888888888888888888888888888888888888
在该实施例中，两个子阵列的工作频段1710-2170MHz和2490-2690MHz，3G频段的子阵列在其工作频段1710-2170MHz内高效辐射，在带外即LTE频段(2490-2690MHz)抑制辐射；同时，LTE频段的子阵列在其工作频段2490-2690MHz MHz内高效辐射，在带外即3G频段(1710-2170MHz)抑制辐射。因此，两个子阵列之间的辐射互不干扰，从而减小了相互干扰，达到较高的端口隔离度。
如图10所示，是本发明一个实施例提供的工作在3G频段的无外加损耗电路的滤波天线单元的反射系数S参数-频率。可以看出工作频段为1710-2170MHz内有两个谐振模式，在S11-频率曲线中，S11在3G频段内低于-15dB。在S21-频率曲线中，S21在3G频段内低于-30dB。
如图11所示，是本发明一个实施例提供的工作在LTE频段的无外加损耗电路的滤波天线单元的反射系数S参数-频率。可以看出工作频段为2490-2690MHz内也有两个谐振模式，在S11-频率曲线中，S11在LTE频段内低于-15dB。在S21-频率曲线中，S21在LTE频段内低于-30dB。
如图12、13所示，分别是本发明一个实施例提供的工作在3G频段和LTE频段的无外加损耗电路的滤波天线单元的1端口(图12)和2端口(图13)分别激励时的增益-频率曲线，可以看到在3G频段内的增益约为8.5dBi，同时LTE频段内的增益约为8.2dBi，辐射零点的增益均低于-20dBi。通带边沿陡峭，边带抑制明显，选择性良好，并且带内增益平坦。
如图14、15、16、17、18所示，是本发明实例提供的高低频滤波阵子交织的紧凑型多波束天线阵列得反射系数-频率，传输系数-频率的仿真结果图。可以看出，在整个3G频段(1710-2170MHz)和LTE频段(2490-2690MHz)内，该阵列的S11低于-22dB，说明该端口的匹配良好。在整个3G频段(1710-2170MHz)和LTE频段(2490-2690MHz)内，该阵列的S12低于-25dB，说明该阵列的子阵列之间的相互耦合作用很小，端口隔离度高。同时，如图17、18所示，在整个3G频段(1710-2170MHz)和LTE频段(2490-2690MHz)内，该阵列的波束隔离达到15dB，说明该阵列的波束隔离好。图19-26分别给出了该天线阵列在2.0GHz和2.6GHz的每个波束的水平面方向图，同样说明该天线阵列具有稳定 的辐射方向图。
本发明实施例具有如下优点：
1、集成滤波特性和辐射特性，天线阵列自身有滤波性能，通带边缘陡峭，边带抑制明显，具有良好的频率选择特性，无需外加双工器或去耦合网络电路，克服了采用外加双工器或去耦合网络容易造成损耗大缺点；
2、该天线阵列适用于3G频段和LTE频段，在无需去耦合电路的情况下，实现了端口的高隔离度，抑制临频干扰，提高了基站收发信机的性能；
3、该天线阵列的子阵列之间交织排列，高频滤波阵子和低频滤波阵子滤波阵子交织排布所组成的阵列，通过含有巴特勒矩阵在内的馈电网络设计进行馈电，可以实现紧凑型多波束基站天线阵列，相比分离排布组阵减小了阵列的尺寸；
4、整个结构主要由金属贴片、金属化过孔、介质板通孔和环型槽组成，结构简单，设计简便。
5、该天线阵列为多波束阵列，波束窄，增益高，适用于扇区划分以及可以覆盖较远的距离。
6、该天线阵列的波束隔离效果好。
本发明提供的实施例适用于无线移动通信基站领域，可应用于各类无线通信系统的接收和发射设备中，由于本发明的滤波特性，特别适用于在开阔复杂的多频段多制式通信场景中，工作在3G频段以及LTE频段的基站天线。同时受益于滤波特性与辐射特性的集成，本发明也适用于无线移动通信系统设备的一体化和集成化，降低设计要求，提高通信设备抗邻频干扰的能力。
本发明实施例的高频滤波阵子和低频滤波阵子交织排布所组成的阵列，通过含有巴特勒矩阵在内的馈电网络进行馈电，可以实现紧凑型多波束基站天线阵列。示例的紧凑型基站天线阵列在水平面实现两波束覆盖120°扇区，垂直面形成旁瓣抑制的窄波束辐射方向图。由于交织的贴片阵子有滤波特性，高频阵子与低频阵子之间的相互耦合作用大大减小。
上述实施例为本发明较佳的实施方式，但本发明的实施方式并不受所述实施例的限制，其他的任何未背离本发明的精神实质与原理下所作的改变、修饰、替代、组合、简化，均应为等效的置换方式，都包含在本发明的保护范围之内。

Claims (10)

  1. 一种高低频滤波振子交织排列的紧凑型多波束天线阵列，其特征在于，包括设置于基板上的工作于第一频段的第一子阵列及工作于第二频段的第二子阵列，所述第一子阵列及第二子阵列交织排列，其中一个子阵列的阵元分散分布在另一个子阵列阵元之间的空间，所述第一子阵列由至少一个无外加损耗电路的第一滤波天线单元构成，所述第二子阵列由至少一个无外加损耗电路的第二滤波天线单元构成，第一频段及第二频段完全不同。
  2. 根据权利要求1所述的紧凑型多波束天线阵列，其特征在于，所述第一滤波天线单元及第二滤波天线单元具体为一种具有高选择性和低交叉极化的双极化滤波天线，由上至下依次包括第一介质基板、第二介质基板、用于支撑的第三介质基板及第四介质基板；
    所述第一介质基板的上表面印刷用于产生和控制辐射通带高频处的辐射零点的寄生辐射金属贴片；
    所述第二介质基板印刷主辐射金属贴片及两条馈线；
    所述第四介质基板的下表面为金属地板。
  3. 根据权利要求2所述的紧凑型多波束天线阵列，其特征在于，所述主辐射金属贴片印刷在第二介质基板的上表面，所述两条馈线分别为第一馈线及第二馈线，所述第一及第二馈线均为H型，且正交耦合，所述第一馈线印刷在第二介质基板的下表面，所述第二馈线中H型的两条竖线及中间横线的一部分印刷在第二介质基板的下表面，第二馈线中间横线的另一部分印刷在第二介质基板的上表面，并通过金属化过孔与印刷在下表面的一部分连接，所述第二介质基板的几何中心与主辐射金属贴片的几何中心重合。
  4. 根据权利要求3所述的紧凑型多波束天线阵列，其特征在于，所述第二介质基板还包括用于隔开第二馈线中间横线的另一部分与主辐射金属贴片的环形槽线，还包括支撑铝板，支撑铝板设置在金属地板的下表面。
  5. 根据权利要求1所述的紧凑型多波束天线阵列，其特征在于，所述第一子阵列及第二子阵列由一列以上的滤波天线单元子纵列平行排布构成，子阵列中，第n子纵列和第n+1子纵列平行交错排布，第n子纵列和第n+2子纵列平行并列排布。
  6. 根据权利要求5所述的紧凑型多波束天线阵列，其特征在于，第一及第二子阵列中，位于第n、第n+1、第n+2子纵列的三个相邻阵元之间成三角形排 布，用以增加阵元之间的距离。
  7. 根据权利要求1所述的紧凑型多波束天线阵列，其特征在于，第一子阵列的第n子纵列和第n+2子纵列之间只存在第二子阵列的一个子纵列。
  8. 根据权利要求1所述的紧凑型多波束天线阵列，其特征在于，第一子阵列由16个第一滤波天线单元呈4×4排列构成，第二子阵列由16个第二滤波天线单元呈4×4排列构成。
  9. 根据权利要求1所述的紧凑型多波束天线阵列，其特征在于，每一个子阵列由两个含巴特勒矩阵和功分器的波束赋形的网络进行馈电。
  10. 根据权利要求1所述的紧凑型多波束天线阵列，其特征在于，通过控制波束赋形网络来实现两波束或多波束，用于单极化或双极化。
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