WO2017118077A1 - 多输入多输出mimo的处理方法及装置 - Google Patents

多输入多输出mimo的处理方法及装置 Download PDF

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Publication number
WO2017118077A1
WO2017118077A1 PCT/CN2016/098603 CN2016098603W WO2017118077A1 WO 2017118077 A1 WO2017118077 A1 WO 2017118077A1 CN 2016098603 W CN2016098603 W CN 2016098603W WO 2017118077 A1 WO2017118077 A1 WO 2017118077A1
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Prior art keywords
base station
channel
terminal
column
state information
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PCT/CN2016/098603
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English (en)
French (fr)
Inventor
项飞
张国梅
李�杰
秦洪峰
王绍鹏
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中兴通讯股份有限公司
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H04B7/046—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting taking physical layer constraints into account
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0452—Multi-user MIMO systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
    • H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
    • H04L1/0618—Space-time coding
    • H04L1/0675—Space-time coding characterised by the signaling

Definitions

  • the present invention relates to the field of communications, and in particular to a method and apparatus for processing multiple input multiple output MIMO.
  • 3D-MIMO 3D-MIMO
  • the base station uses a 2D array active antenna, so that the signals of the user and the base station can be transmitted not only in the horizontal direction but also in the vertical direction, and the vertical degree of freedom of the channel can be tapped. Therefore, the 3D-MIMO precoding design is not limited to the traditional horizontal direction, and the user beamforming vector can be designed in the vertical direction to better achieve interference suppression.
  • Precoding methods in traditional MIMO systems such as Singular Value Decomposition (SVD), Zero Forcing (ZF), and Signal to Leakage and Noise Ratio (referred to as SLNR) and so on can achieve better performance.
  • Singular Value Decomposition SVD
  • ZF Zero Forcing
  • SLNR Signal to Leakage and Noise Ratio
  • 3D-MIMO precoding research in the related art one is to obtain a simpler solution form by mathematical approximation to reduce the computational complexity; the other idea is to use the structural features of the 2D area array to design two dimensions, thereby Achieve a reduction in complexity.
  • the complexity is generally achieved by a two-step precoding design in the vertical and horizontal directions. However, most of the current methods are discussed in a single-user MIMO scenario, which is not realistic.
  • the embodiments of the present invention provide a processing method and apparatus for multiple input multiple output MIMO to solve at least the problem of high complexity of 3D-MIMO precoding matrix operations in the related art.
  • a method for processing multiple input multiple output MIMO including: acquiring, by a base station, channel state information of a terminal on a column channel in a coverage of the base station, and selecting, according to the channel state information, a terminal that meets a preset condition, wherein the column channel is a transmission channel between the terminal and an antenna in a vertical direction of the base station; and the base station determines the multiple terminals according to the channel state information.
  • Pre-predicting in the vertical direction a beamforming vector calculated by the coding matrix; the base station obtains a horizontal channel corresponding to the beamforming vector according to the beamforming vector, and performs precoding in a horizontal direction of the horizontal channel by using a preset rule Matrix calculation.
  • the acquiring, by the base station, the channel state information of the terminal in the coverage of the base station includes: the base station transmitting a channel state information reference symbol CSI-RS to a terminal in the coverage of the base station; and receiving, by the base station, the terminal Channel state information transmitted after measuring the channel according to the CSI-RS.
  • CSI-RS channel state information reference symbol
  • the selecting, by the base station, the multiple terminals whose terminal correlation meets the preset condition according to the channel state information includes: determining, by the base station, a predetermined number of the multiple terminals that meet a preset condition; Determining, by the channel state information, a terminal having the best channel characteristic as an initial terminal; the base station acquiring a plurality of chord distances between the selected initial terminal and the plurality of to-be-selected terminals; A predetermined number of the plurality of terminals farthest from the initial terminal chord are selected among the plurality of chord distances.
  • the base station determines, according to the channel state information, a beamforming vector calculated by performing precoding matrix calculation in a vertical direction by using the channel state information: the base station according to each column channel information Calculating the beamforming vector in the vertical direction ((N h ⁇ N v ) ⁇ N h dimension), as shown in the following equation: Wherein, the channel information of each column is Indicates the i-th column channel matrix of the kth user (N r ⁇ N v dimension); the beamforming vector in the vertical direction ((N h ⁇ N v ) ⁇ N h dimension), The eigenvector corresponding to the largest generalized eigenvalue of (A, B), P is the transmission power, n k is the reception noise of each terminal, and ⁇ 2 is the noise power.
  • the base station obtains a horizontal channel corresponding to the beamforming vector according to the beamforming vector, and performs precoding matrix calculation in a horizontal direction of the horizontal channel by using a preset rule, where The base station forms the beamforming vector Applied to each column of vertical channels, the horizontal channel is calculated by the formula shown below: The dimension is N r ⁇ N h , and k is 1, 2, . . . , S; the base station calculates the plurality of terminal precoding matrices in the horizontal direction on the horizontal channel by using a zero-forcing ZF criterion.
  • each column represents the equivalent horizontal precoding matrix of the corresponding user, ie
  • the kth column of the above matrix represents an equivalent horizontal precoding matrix of the kth user, wherein Indicates the equivalent horizontal channel of the kth user, Yes Conjugate transposition.
  • a processing apparatus for multiple input multiple output MIMO which is applied to a base station side, and includes: an acquiring module, configured to acquire channel state information of a terminal on a column channel in a coverage area of the base station, And selecting, according to the channel state information, a plurality of terminals whose terminal correlation meets a preset condition, wherein the column channel is a transmission channel between the antennas in the vertical direction of the terminal and the base station; determining a module, setting the basis
  • the channel state information determines a beamforming vector calculated by the plurality of terminals in a vertical direction, and the processing module is configured to obtain a horizontal channel corresponding to the beamforming vector according to the beamforming vector Precoding matrix calculation is performed in the horizontal direction of the horizontal channel by a preset rule.
  • the acquiring module includes: a sending unit, configured to send a channel state information reference symbol CSI-RS to a terminal within the coverage of the base station; and a receiving unit configured to receive the terminal according to the CSI-RS pair Channel state information transmitted after the channel is measured.
  • a sending unit configured to send a channel state information reference symbol CSI-RS to a terminal within the coverage of the base station
  • a receiving unit configured to receive the terminal according to the CSI-RS pair Channel state information transmitted after the channel is measured.
  • the obtaining module further includes: a determining unit, configured to predetermine a predetermined number of the plurality of terminals that meet the preset condition; and the first selecting unit is configured to select the channel characteristic according to the channel state information.
  • a good terminal as an initial terminal
  • an obtaining unit configured to acquire a plurality of chord distances between the selected initial terminal and the plurality of terminals to be selected
  • a second selecting unit configured to be from the plurality of chord distances A predetermined number of the plurality of terminals farthest from the initial terminal chord are selected.
  • a first configuration module configured to Configur
  • the determining module is further configured to: according to each column channel information Calculating the beamforming vector in the vertical direction ((N h ⁇ N v ) ⁇ N h dimension), as shown in the following equation:
  • the channel information of each column is Indicates the i-th column channel matrix of the kth user (N r ⁇ N v dimension); the beamforming vector in the vertical direction ((N h ⁇ N v ) ⁇ N h dimension),
  • the eigenvector corresponding to the largest generalized eigenvalue of (A, B) P is the transmission power
  • n k is the reception noise of each terminal
  • ⁇ 2 is the noise power.
  • the processing module includes: a first calculating unit, configured to shape the beam vector Applied to each column of vertical channels, the horizontal channel shown in the following formula is calculated:
  • the dimension is N r ⁇ N h , k is 1, 2, . . .
  • the second calculating unit is configured to calculate the plurality of terminal precoding matrices in the horizontal direction on the horizontal channel by using a zero-forcing ZF criterion make ((N r ⁇ S) ⁇ N h dimension), and the formula for obtaining the precoding matrix is (N h ⁇ S dimension), where each column represents the equivalent horizontal precoding matrix of the corresponding user, ie The kth column of the above matrix represents an equivalent horizontal precoding matrix of the kth user, wherein Indicates the equivalent horizontal channel of the kth user, Yes Conjugate transposition.
  • the base station acquires channel state information of the terminal on the column channel in the coverage of the base station, and selects multiple terminals whose terminal correlation meets the preset condition according to the channel state information, where the column channel is the vertical direction of the terminal and the base station. a transmission channel between the upper antennas; the base station determines, according to the channel state information, a beamforming vector calculated by the precoding matrix of the plurality of terminals in the vertical direction, and obtains a horizontal channel corresponding to the beamforming vector according to the beamforming vector, The precoding matrix calculation is performed in the horizontal direction of the horizontal channel by using a preset rule.
  • the user precoding design can achieve better performance and reduce the computational complexity compared with the MIMO system in which only the horizontal direction precoding matrix is designed in the related art, thereby solving the complexity of the 3D-MIMO precoding matrix operation in the related art. High problem.
  • FIG. 1 is a flowchart of a method of processing multiple input multiple output MIMO according to an embodiment of the present invention
  • FIG. 2 is a structural block diagram of a processing apparatus for multiple input multiple output MIMO according to an embodiment of the present invention
  • FIG. 3 is a block diagram of an optional structure of a processing apparatus for multiple input multiple output MIMO according to an embodiment of the present invention
  • FIG. 4 is a block diagram 2 of an optional structure of a processing apparatus for multiple input multiple output MIMO according to an embodiment of the present invention
  • FIG. 5 is a block diagram 3 of an optional structure of a processing apparatus for multiple input multiple output MIMO according to an embodiment of the present invention
  • FIG. 6 is a structural diagram of a 3D MU-MIMO system in accordance with an alternative embodiment of the present invention.
  • FIG. 7 is a schematic diagram of comparison of CDF curves of SINRs of three schemes in a base station 8*8 uniform area array antenna configuration according to an alternative embodiment of the present invention
  • FIG. 8 is a schematic diagram of comparison of CDF curves of SINRs of three schemes in a base station 8*16 uniform area array antenna configuration according to an alternative embodiment of the present invention
  • FIG. 9 is a schematic diagram showing comparison of spectral efficiency per user of different schemes when a base station deploys different antenna numbers in a vertical direction according to an alternative embodiment of the present invention.
  • FIG. 10 is a schematic diagram of a CDF curve for different scheme SINRs when the second step precoding ZF criterion is replaced with a maximized SLNR criterion, in accordance with an alternative embodiment of the present invention.
  • FIG. 1 is a flowchart of a processing method of multiple input multiple output MIMO according to an embodiment of the present invention. As shown in FIG. 1 , the flow includes the following steps. :
  • Step S102 The base station acquires channel state information of the terminal on the column channel in the coverage of the base station, and selects, according to the channel state information, a plurality of terminals whose terminal correlation meets a preset condition, where the column channel is between the terminal and the antenna in the vertical direction of the base station.
  • Step S104 The base station determines, according to the channel state information, a beamforming vector obtained by performing precoding matrix calculation on a plurality of terminals in a vertical direction.
  • Step S106 The terminal obtains a horizontal channel corresponding to the beamforming vector according to the beamforming vector, and performs precoding matrix calculation in the horizontal direction of the horizontal channel by using a preset rule.
  • the base station acquires channel state information of the terminal on the column channel in the coverage of the base station, and according to the The channel state information selects a plurality of terminals whose terminal correlation meets a preset condition, wherein the column channel is a transmission channel between the antennas in the vertical direction between the terminal and the base station; and then the base station determines, according to the channel state information, that the plurality of terminals are precoded in the vertical direction.
  • the calculated beamforming vector is obtained by the matrix, and the horizontal channel corresponding to the beamforming vector is obtained according to the beamforming vector, and the precoding matrix is calculated in the horizontal direction of the horizontal channel by using a preset rule, which can be seen in this embodiment.
  • the method can be implemented as follows:
  • Step S102-1 The base station sends a channel state information reference symbol CSI-RS to the terminal within the coverage of the base station;
  • Step S102-2 The base station receives channel state information that is sent by the terminal after measuring the channel according to the CSI-RS.
  • the base station After the base station obtains the channel state information, the base station selects a plurality of terminals whose terminal relevance meets the preset condition according to the channel state information, and the manner of acquiring the multiple terminals includes:
  • Step S102-3 The base station determines in advance a predetermined number of the plurality of terminals that meet the preset condition
  • Step S102-4 The base station selects the terminal with the best channel characteristics as the initial terminal according to the channel state information.
  • Step S102-5 The base station acquires multiple chord distances between the selected initial terminal and multiple terminals to be selected.
  • Step S102-6 The base station selects a predetermined number of the plurality of terminals farthest from the initial terminal chord from the plurality of chord distances.
  • the method in this embodiment before the base station determines, according to the channel state information, the beamforming vector calculated by the precoding matrix in the vertical direction, the method in this embodiment further includes:
  • the base station in this embodiment determines, according to the channel state information, a beamforming vector calculated by the precoding matrix of the plurality of terminals in the vertical direction according to the following formula:
  • the channel information of each column is Indicates the i-th column channel matrix of the kth user (N r ⁇ N v dimension); the beamforming vector in the vertical direction ((N h ⁇ N v ) ⁇ N h dimension),
  • the eigenvector corresponding to the largest generalized eigenvalue of (A, B) P is the transmission power
  • n k is the reception noise of each terminal
  • ⁇ 2 is the noise power.
  • the base station involved in the embodiment obtains a horizontal channel corresponding to the beamforming vector according to the beamforming vector, and performs precoding matrix calculation in the horizontal direction of the horizontal channel by using a preset rule.
  • a preset rule Can be achieved by:
  • Step S21 The base station will form a beamforming vector Applied to each column of vertical channels, the horizontal channel shown in the following formula is calculated: The dimension is N r ⁇ N h , and k is 1, 2, ..., S;
  • Step S22 The base station calculates a plurality of terminal precoding matrices in the horizontal direction on the horizontal channel by using a zero-forcing ZF criterion. make ((N r ⁇ S) ⁇ N h dimension), and the formula for obtaining the precoding matrix is (N h ⁇ S dimension), where each column represents the equivalent horizontal precoding matrix of the corresponding user, ie For the kth column of the above matrix, the equivalent horizontal precoding matrix of the kth user is represented. among them, Indicates the equivalent horizontal channel of the kth user, Yes Conjugate transposition.
  • the method according to the above embodiment can be implemented by means of software plus a necessary general hardware platform, and of course, by hardware, but in many cases, the former is A better implementation.
  • the technical solution of the present invention which is essential or contributes to the prior art, may be embodied in the form of a software product stored in a storage medium (such as ROM/RAM, disk,
  • the optical disc includes a number of instructions for causing a terminal device (which may be a cell phone, a computer, a server, or a network device, etc.) to perform the methods described in various embodiments of the present invention.
  • a multi-input and multi-output MIMO processing device is also provided, which is used to implement the above-mentioned embodiments and preferred embodiments, and has not been described again.
  • the term “module” may implement a combination of software and/or hardware of a predetermined function.
  • the apparatus described in the following embodiments is preferably implemented in software, hardware, or a combination of software and hardware, is also possible and contemplated.
  • FIG. 2 is a structural block diagram of a processing apparatus for multiple-input multiple-output MIMO according to an embodiment of the present invention.
  • the apparatus is applied to a base station side.
  • the apparatus includes: an acquiring module 22 configured to acquire a terminal in a coverage area of the base station.
  • the determining module 24 is coupled with the obtaining module 22 And determining, according to the channel state information, a beamforming vector obtained by performing precoding matrix calculation by a plurality of terminals in a vertical direction; the processing module 26 is coupled to the determining module 24, and configured to obtain and beamform according to the beamforming vector.
  • the vector corresponds to the horizontal channel, and the precoding matrix is calculated in the horizontal direction of the horizontal channel by a preset rule.
  • the acquiring module 22 includes: a sending unit 302, configured to send a channel to a terminal in a coverage area of a base station.
  • the status information reference symbol CSI-RS; the receiving unit 304 is coupled to the transmitting unit 302, and is configured to receive channel state information that is sent by the terminal after measuring the channel according to the CSI-RS.
  • the obtaining module 22 further includes: a determining unit 306, coupled to the receiving unit 304, configured to predetermine a predetermined number of the plurality of terminals that meet the preset condition; the first selecting unit 308 is coupled to the determining unit 306, and is configured to be configured. The terminal that selects the best channel characteristic is selected as the initial terminal according to the channel state information; the obtaining unit 310 is coupled to the selecting unit 308, and is configured to acquire multiple strings between the selected initial terminal and the plurality of terminals to be selected.
  • the second selection unit 312 is coupled to the acquisition unit 310 and is configured to select a predetermined number of terminals from the plurality of chord distances that are furthest from the initial terminal chord.
  • the base station determines, according to channel state information, that a plurality of terminals perform precoding matrix calculation in a vertical direction.
  • the determining module 24 involved in this embodiment is further configured to channel information according to each column. Calculate the beamforming vector in the vertical direction ((N h ⁇ N v ) ⁇ N h dimension), as shown in the following equation:
  • the channel information of each column is Indicates the i-th column channel matrix of the kth user (N r ⁇ N v dimension); the beamforming vector in the vertical direction ((N h ⁇ N v ) ⁇ N h dimension),
  • the feature vector corresponding to the largest broad feature value of (A, B) P is the transmission power
  • n k is the reception noise of each terminal
  • ⁇ 2 is the noise power.
  • FIG. 5 is a block diagram 3 of an optional structure of a processing apparatus for multiple input multiple output MIMO according to an embodiment of the present invention.
  • the processing module 26 includes: a first calculating unit 52 configured to form a beamforming vector Applied to each column of vertical channels, the horizontal channel shown in the following formula is calculated:
  • the second calculating unit 54 is coupled to the first calculating unit 52 and configured to calculate a plurality of terminal precoding matrices in a horizontal direction on the horizontal channel by using a zero-forcing ZF criterion.
  • each column represents the equivalent horizontal precoding matrix of the corresponding user, ie
  • the equivalent horizontal precoding matrix of the kth user is represented. among them, Indicates the equivalent horizontal channel of the kth user, Yes Conjugate transposition.
  • each of the above modules may be implemented by software or hardware.
  • the foregoing may be implemented by, but not limited to, the foregoing modules are all located in the same processor; or, the modules are located in multiple In the processor.
  • This alternative embodiment provides a method for reducing system complexity.
  • the technical solution of the method is a two-step precoding and a user selection scheme suitable for a 3D scenario.
  • the detailed process may be: the base station performs user selection according to the column correlation of the user (corresponding to the terminal in the above embodiment), and selects a user whose column channel correlation is poor and is served on the same time-frequency resource.
  • the first step design the beamforming vector in the vertical direction according to the user's column channel information, to achieve the purpose of distinguishing the user in the vertical direction first; the second step: using the vertical design in the first step
  • the beamforming vector calculates the equivalent horizontal channel, and then uses the zero-forcing (ZF) method to design the horizontal precoding matrix according to the equivalent horizontal channel.
  • ZF zero-forcing
  • the column channel refers to a transmission channel between a user and a column of antennas in the vertical direction of the base station.
  • a base station deploys a 2D uniform area array (UPA), a BS represents a base station, an MS represents a user, and the system includes a base station.
  • UPA 2D uniform area array
  • the received signal y k of user k can be expressed as:
  • xk is a transmission signal of the kth user; a vertical precoding matrix representing the kth user, where Is a N v ⁇ 1 dimensional vector, and (N h ⁇ 1 dimension, ) A precoding matrix representing the horizontal direction of the kth user.
  • SINR received signal to interference and noise ratio
  • the base station sends a CSI-RS to the user, and the user measures channel state information according to the received CSI-RS, and then feeds the channel state information to the base station, and the base station uses the chord distance method according to the channel state information fed back by the user.
  • the user selects, the user selecting the vertical correlation of small S (S ⁇ N h) set of user services.
  • the method steps selected by the user include:
  • PF proportional fair
  • Step S44 After the Sth user is selected, the loop ends and the algorithm terminates.
  • chord distance is an amount that characterizes the correlation between matrices (vectors). The larger the chord distance, the smaller the correlation between matrices (vectors). The definition is as follows:
  • the calculation of the two-step precoding matrix is performed on the selected user set at the base station side, which is divided into the following two steps:
  • the first step the base station according to the user's column information of each column Calculate each column beamforming vector in the vertical direction by maximizing the vertical direction signal to noise and noise ratio (SLNR) (N v ⁇ 1 dimension), as shown below:
  • the final vertical direction precoding matrix is:
  • Step 2 The vertical beamforming vector obtained in the first step Applied to each column of vertical channels, the equivalent horizontal channel is obtained as follows:
  • Base station channel state information acquisition :
  • Step S31 The base station sends a channel state information reference symbol (CSI-RS) to the user;
  • CSI-RS channel state information reference symbol
  • Step S32 The user performs channel measurement according to the received CSI-RS.
  • Step S33 The user feeds back the measured channel to the base station
  • the base station obtains a vertical direction beamforming vector according to the solution of (5) above.
  • Base station obtains vertical beamforming vector Then calculate the horizontal direction precoding matrix according to formulas (8) to (10)
  • the signal transmission is performed according to the signal model of equation (1).
  • the signal leakage ratio refers to the ratio of the signal power of the target user to the sum of the interference power and the noise power leaked to other users.
  • the user selection is performed according to the channel correlation of the user column before the precoding is performed, and the channel correlation of the user column is selected. The user then performs the service.
  • a new two-step 3D multi-user precoding scheme with different and traditional single-step precoding and different from the existing two-step precoding is given: First, according to the vertical direction SLNR maximization criterion, design Beamforming is performed in the vertical direction, and the weight vectors of the columns are the same. In the second step, MU-MIMO precoding is performed in the horizontal direction using the equivalent channel.
  • Embodiment 1 is a diagrammatic representation of Embodiment 1:
  • the 100-user of the 3D-UMi single cell is taken as an example, and the channel WINNERII/+3D channel model between the base station and the user.
  • the base station is configured with an 8*8 uniform area array, that is, 8 lines of antennas in the horizontal direction and 8 columns of antennas in the vertical direction, and the horizontal and vertical antenna spacings are both 0.5 ⁇ ( ⁇ represents the wavelength).
  • Each user is equipped with a single antenna.
  • the antenna downtilt angle is set to 16 degrees.
  • FIG. 7 is a schematic diagram of comparison of CDF curves of SINR for three schemes of a base station 8*8 uniform area array antenna configuration according to an alternative embodiment of the present invention.
  • the simulation does not make a vertical beam with the scheme.
  • the shaping scheme (labeled as: NV scheme in FIG. 7) and the random beamforming scheme in the vertical direction (labeled as: RV scheme in FIG. 7) are compared; comparing the alternative embodiment scheme with the NV scheme and the RV scheme .
  • the cumulative distribution of signal to noise ratio (SINR) curves (CDF) curves for these three schemes are compared as shown in FIG.
  • SINR signal to noise ratio
  • Table 1 shows the average spectral efficiency per user in the 8*8 antenna configuration. It can be seen that the scheme of the alternative embodiment is 20.64% higher than the NV scheme, and the RV scheme can only increase 10.04% compared with the NV scheme.
  • Embodiment 2 is a diagrammatic representation of Embodiment 1:
  • This alternative embodiment has the same application scenario as the first embodiment, except that the base station antenna configuration is changed to an 8*16 uniform area array, that is, the number of vertical antennas is changed to 16.
  • FIG. 8 is a schematic diagram of comparison of CDF curves of SINRs of three schemes in a base station 8*16 uniform area array antenna configuration according to an alternative embodiment of the present invention, comparing the scheme of the second embodiment with an NV scheme and an RV, three The CDF curve for the user SINR of the scheme is shown in Figure 8.
  • This alternative embodiment enables better performance in an 8*16 antenna configuration.
  • FIG. 9 is a schematic diagram showing comparison of spectral efficiency per user of different schemes when a base station deploys different antenna numbers in a vertical direction according to an alternative embodiment of the present invention. As shown in FIG. 9, the number of vertical antennas is 8 and 16.
  • Table 2 is an average spectral efficiency table per user in an 8*16 antenna configuration. As can be seen from Table 2, when the number of vertical antennas is 16, the average spectral efficiency performance per user of the alternative embodiment is improved compared with the NV scheme. 38.57%, and the RV solution can only improve performance by 21.17% compared with the NV solution.
  • Embodiment 3 is a diagrammatic representation of Embodiment 3
  • the base station adopts an alternative maximizing SLNR criterion, and other application scenario parameters are the same as in the first embodiment.
  • FIG. 10 is a schematic diagram of a CDF curve of different scheme SINRs when a maximum SLLR criterion is used instead of a second step precoding ZF criterion, as shown in FIG. 10, comparing the signal to interference and noise ratios of the three schemes according to an alternative embodiment of the present invention.
  • Table 3 is a table for precoding to replace the average spectral efficiency per user by maximizing the SLNR criterion.
  • the step gives the average spectral efficiency per user in this scenario. It can be seen that the scheme of the present invention is improved over the NV scheme. With 22.12%, the RV solution is 11.20% higher than the NV solution, which shows that the second step can use the SLNR criterion instead of the ZF criterion.
  • the main computational complexity of the 3D precoding algorithm of the inventive scheme lies in the eigenvalue decomposition of the first step on the N v ⁇ N v dimensional matrix, and the second step on the N h ⁇ N h dimensional matrix.
  • the total computational complexity is The complexity of the traditional one-step precoding algorithm is ⁇ ((N v ⁇ N h ) 3 ).
  • the complexity is much higher than the solution of the present invention.
  • the user selection of the inventive scheme is only performed on a column channel (1 x N v dimension), whereas if the same user selection scheme is used, the conventional scheme is to the overall channel (1 x (N h ⁇ N v
  • the computational complexity is also much higher than that of the present embodiment.
  • the optional embodiment can greatly reduce the complexity of the system when the number of antennas is large while ensuring performance.
  • Embodiments of the present invention also provide a storage medium.
  • the foregoing storage medium may be configured to store program code for performing the following steps:
  • the base station acquires channel state information of the terminal on the column channel in the coverage of the base station, and selects, according to the channel state information, a plurality of terminals whose terminal correlation meets a preset condition, where the column channel is between the terminal and the antenna in the vertical direction of the base station.
  • the base station determines, according to the channel state information, a beamforming vector obtained by performing precoding matrix calculation by multiple terminals in a vertical direction;
  • S3 The terminal obtains a horizontal channel corresponding to the beamforming vector according to the beamforming vector, and performs precoding matrix calculation in a horizontal direction of the horizontal channel by using a preset rule.
  • modules or steps of the present invention described above can be implemented by a general-purpose computing device that can be centralized on a single computing device or distributed across a network of multiple computing devices. Alternatively, they may be implemented by program code executable by the computing device such that they may be stored in the storage device by the computing device and, in some cases, may be different from the order herein.
  • the steps shown or described are performed, or they are separately fabricated into individual integrated circuit modules, or a plurality of modules or steps thereof are fabricated as a single integrated circuit module.
  • the invention is not limited to any specific combination of hardware and software.
  • the base station acquires channel state information of the terminal on the column channel in the coverage of the base station, and selects multiple terminals whose terminal correlation meets the preset condition according to the channel state information, where the column channel is the vertical direction of the terminal and the base station. a transmission channel between the upper antennas; the base station determines, according to the channel state information, a beamforming vector calculated by the precoding matrix of the plurality of terminals in the vertical direction, and obtains a horizontal channel corresponding to the beamforming vector according to the beamforming vector, The precoding matrix calculation is performed in the horizontal direction of the horizontal channel by using a preset rule.
  • the user precoding design can achieve better performance and reduce the computational complexity compared with the MIMO system in which only the horizontal direction precoding matrix is designed in the related art, thereby solving the complexity of the 3D-MIMO precoding matrix operation in the related art. High problem.

Abstract

本发明提供了一种多输入多输出MIMO的处理方法及装置，其中，该方法包括：基站获取基站覆盖范围内终端在列信道上的信道状态信息，并依据信道状态信息选择终端相关性满足预设条件的多个终端，其中，列信道为终端与基站垂直方向上天线间的传输信道；基站依据信道状态信息确定多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量；基站依据波束赋形矢量得到与波束赋形矢量对应的水平信道，并通过预设规则在水平信道的水平方向上进行预编码矩阵计算。通过本发明，解决了相关技术中3D-MIMO预编码矩阵运算的复杂度高的问题。

Description

多输入多输出MIMO的处理方法及装置 技术领域
本发明涉及通信领域，具体而言，涉及一种多输入多输出MIMO的处理方法及装置。
背景技术
大规模多输入多输出(Multiple-Input Multiple-Output，简称为MIMO)系统能够带来系统频谱效率和系统容量的大大提升，但是实际系统中受天线尺寸及基站空间限制，不可能在水平方向上摆放大量天线。为解决这个问题，引入3D-MIMO(3-Dimension MIMO)，也可以称为(Full-Dimension MIMO，简称为FD-MIMO)以解决大规模MIMO的实际实现问题。3D-MIMO系统中基站采用2D面阵有源天线，这样，用户与基站端的信号不但可以在水平方向上传输，也可以在垂直方向上传输，信道的垂直自由度就可以被挖掘。因此，3D-MIMO预编码设计也不只局限于传统的水平方向，也可以在垂直方向设计用户波束赋形矢量，从而更好的实现干扰抑制。
传统MIMO系统中的预编码方法，如奇异值分解(Singular Value Decomposition，简称为SVD)、迫零(Zero Forcing，简称为ZF)、最大化信漏噪比(Signal to Leakage and Noise Ratio，简称为SLNR)等都能够实现较好的性能。然而在天线数较多的3D-MIMO中，随着天线数的增加，这些算法的计算复杂度也会随之增加。因此非常有必要进行低复杂度的3D-MIMO的预编码算法的研究。相关技术中的3D-MIMO预编码研究，一种是通过数学近似求得更简单的解形式来降低计算复杂度；另一种思路是利用2D面阵的结构特点进行两个维度的设计，从而实现复杂度的降低。第一种虽然能够在某种程度上降低运算复杂度，但是天线数增多，信道矩阵维度非常大，这必然导致矩阵运算的复杂度仍然很高；第二种是从根本上降低3D-MIMO的复杂度，一般是通过垂直、水平方向两步预编码设计来实现，但是目前这种方法的探讨大多是在单用户MIMO场景下的展开的，这并不符合实际。
针对相关技术中3D-MIMO预编码矩阵运算的复杂度高的问题，目前尚未存在有效的解决方案。
发明内容
本发明实施例提供了多输入多输出MIMO的处理方法及装置，以至少解决相关技术中3D-MIMO预编码矩阵运算的复杂度高的问题。
根据本发明实施例的一个方面，提供了一种多输入多输出MIMO的处理方法，包括：基站获取所述基站覆盖范围内终端在列信道上的信道状态信息，并依据所述信道状态信息选择终端相关性满足预设条件的多个终端，其中，所述列信道为所述终端与所述基站垂直方向上天线间的传输信道；所述基站依据所述信道状态信息确定所述多个终端在垂直方向上进行预 编码矩阵计算得到的波束赋形矢量；所述基站依据所述波束赋形矢量得到与所述波束赋形矢量对应的水平信道，并通过预设规则在所述水平信道的水平方向上进行预编码矩阵计算。
可选地，所述基站获取所述基站覆盖范围内终端的信道状态信息包括：所述基站向所述基站覆盖范围内的终端发送信道状态信息参考符号CSI-RS；所述基站接收所述终端依据所述CSI-RS对信道进行测量后发送的信道状态信息。
可选地，所述基站依据所述信道状态信息选择终端相关性满足预设条件的多个终端包括：所述基站预先确定满足预设条件的所述多个终端的预定数量；所述基站依据所述信道状态信息选择出信道特性最好的终端作为初始终端；所述基站获取已选出的所述初始终端与多个待选择的终端之间的多个弦距离；所述基站从所述多个弦距离中选择出与所述初始终端弦距离最远的预定数量的所述多个终端。
可选地，在所述基站依据所述信道状态信息确定所述多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量之前，所述方法还包括：所述基站配置2D均匀面阵UPA，其中，所述2D均匀面阵UPA包括：Nt＝Nh×Nv根天线，Nh为水平方向列天线个数，Nv为垂直方向行天线个数，所述基站为所述基站的每个小区中随机分布的k个终端中的每一个终端配置Nr＝1根天线；Hk表示第k个终端到所述基站的3D信道矩阵(Nr×(Nh×Nv)维)，所述
Figure PCTCN2016098603-appb-000001
表示用户到基站第i列天线的信道矩阵(Nr×Nv维)，i＝1,2...Nh，k为正整数，取值为1，2，…，S，其中S表示当前组内的用户数。
可选地，所述基站通过如下公式依据所述信道状态信息确定所述多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量：所述基站根据各列信道信息
Figure PCTCN2016098603-appb-000002
计算所述垂直方向的波束赋形矢量
Figure PCTCN2016098603-appb-000003
((Nh×Nv)×Nh维)，如下式所示：
Figure PCTCN2016098603-appb-000004
其中，各列信道信息为
Figure PCTCN2016098603-appb-000005
表示第k个用户的第i列信道矩阵(Nr×Nv维)；垂直方向的波束赋形矢量
Figure PCTCN2016098603-appb-000006
((Nh×Nv)×Nh维)，
Figure PCTCN2016098603-appb-000007
(A，B)的最大广义特征值对应的特征向量，
Figure PCTCN2016098603-appb-000008
Figure PCTCN2016098603-appb-000009
P为发射功率，nk为各终端接收噪声，σ2为噪声功率。
可选地，所述基站依据所述波束赋形矢量得到与所述波束赋形矢量对应的水平信道，并通过预设规则在所述水平信道的水平方向上进行预编码矩阵计算包括：所述基站将所述波束 赋形矢量
Figure PCTCN2016098603-appb-000010
应用于各列垂直信道，通过如下所示公式计算得到水平信道：
Figure PCTCN2016098603-appb-000011
维度为Nr×Nh，k取值为1，2，…，S；所述基站采用迫零ZF准则计算所述水平信道上水平方向的所述多个终端预编码矩阵
Figure PCTCN2016098603-appb-000012
令
Figure PCTCN2016098603-appb-000013
((Nr×S)×Nh维)，进而得到所述预编码矩阵的公式为
Figure PCTCN2016098603-appb-000014
(Nh×S维)，其中，每一列代表对应用户的等效水平预编码矩阵，即
Figure PCTCN2016098603-appb-000015
为上述矩阵的第k列，表示第k个用户的等效水平预编码矩阵，其中，
Figure PCTCN2016098603-appb-000016
表示第k个用户的等效水平信道，
Figure PCTCN2016098603-appb-000017
是
Figure PCTCN2016098603-appb-000018
的共轭转置。
根据本发明的另一个方面，提供了一种多输入多输出MIMO的处理装置，应用于基站侧，包括：获取模块，设置为获取所述基站覆盖范围内终端在列信道上的信道状态信息，并依据所述信道状态信息选择终端相关性满足预设条件的多个终端，其中，所述列信道为所述终端与所述基站垂直方向上天线间的传输信道；确定模块，设置为依据所述信道状态信息确定所述多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量；处理模块，设置为依据所述波束赋形矢量得到与所述波束赋形矢量对应的水平信道，并通过预设规则在所述水平信道的水平方向上进行预编码矩阵计算。
可选地，所述获取模块包括：发送单元，设置为向所述基站覆盖范围内的终端发送信道状态信息参考符号CSI-RS；接收单元，设置为接收所述终端依据所述CSI-RS对信道进行测量后发送的信道状态信息。
可选地，所述获取模块还包括：确定单元，设置为预先确定满足预设条件的所述多个终端的预定数量；第一选择单元，设置为依据所述信道状态信息选择出信道特性最好的终端作为初始终端；获取单元，设置为获取已选出的所述初始终端与多个待选择的终端之间的多个弦距离；第二选择单元，设置为从所述多个弦距离中选择出与所述初始终端弦距离最远的预定数量的所述多个终端。
可选地，在所述基站依据所述信道状态信息确定所述多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量之前，所述装置还包括：第一配置模块，设置为配置2D均匀面阵UPA，其中，所述2D均匀面阵UPA包括：Nt＝Nh×Nv根天线，Nh为水平方向列天线个数，Nv为垂直方向行天线个数，第二配置模块，设置为为所述基站的每个小区中随机分布的k个终端中的每一个终端配置Nr＝1根天线；Hk表示第k个终端到所述基站的3D信道矩阵(Nr×(Nh×Nv)维)，所述
Figure PCTCN2016098603-appb-000019
表示用户到基站第i列天线的信道矩阵(Nr×Nv维)，i＝1,2...Nh，k为正整数。
可选地，所述确定模块，还设置为根据各列信道信息
Figure PCTCN2016098603-appb-000020
计算所述垂直 方向的波束赋形矢量
Figure PCTCN2016098603-appb-000021
((Nh×Nv)×Nh维)，如下式所示：
Figure PCTCN2016098603-appb-000022
其中，各列信道信息为
Figure PCTCN2016098603-appb-000023
表示第k个用户的第i列信道矩阵(Nr×Nv维)；垂直方向的波束赋形矢量
Figure PCTCN2016098603-appb-000024
((Nh×Nv)×Nh维)，
Figure PCTCN2016098603-appb-000025
(A，B)的最大广义特征值对应的特征向量，
Figure PCTCN2016098603-appb-000026
P为发射功率，nk为各终端接收噪声，σ2为噪声功率。
可选地，所述处理模块包括：第一计算单元，设置为将所述波束赋形矢量
Figure PCTCN2016098603-appb-000027
应用于各列垂直信道，计算得到如下公式所示的水平信道：
Figure PCTCN2016098603-appb-000028
维度为Nr×Nh，k取值为1，2，…，S；第二计算单元，设置为采用迫零ZF准则计算所述水平信道上水平方向的所述多个终端预编码矩阵
Figure PCTCN2016098603-appb-000029
令
Figure PCTCN2016098603-appb-000030
((Nr×S)×Nh维)，进而得到所述预编码矩阵的公式为
Figure PCTCN2016098603-appb-000031
(Nh×S维)，其中每一列代表了对应用户的等效水平预编码矩阵，即
Figure PCTCN2016098603-appb-000032
为上述矩阵的第k列，表示第k个用户的等效水平预编码矩阵，其中，
Figure PCTCN2016098603-appb-000033
表示第k个用户的等效水平信道，
Figure PCTCN2016098603-appb-000034
是
Figure PCTCN2016098603-appb-000035
的共轭转置。
通过本发明实施例，基站获取基站覆盖范围内终端在列信道上的信道状态信息，并依据信道状态信息选择终端相关性满足预设条件的多个终端，其中，列信道为终端与基站垂直方向上天线间的传输信道；进而基站依据信道状态信息确定多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量，并依据波束赋形矢量得到与波束赋形矢量对应的水平信道，并通过预设规则在水平信道的水平方向上进行预编码矩阵计算，可见在本实施例中通过分析信道特性，选出合适的服务终端集合，然后采用对信道降维的两步预编码实现多用户预编码设计，与相关技术中只设计水平方向预编码矩阵的MIMO系统相比能够实现较好的性能，同时降低了计算复杂度，从而解决了相关技术中3D-MIMO预编码矩阵运算的复杂度高的问题。
附图说明
此处所说明的附图用来提供对本发明的进一步理解，构成本申请的一部分，本发明的示意性实施例及其说明用于解释本发明，并不构成对本发明的不当限定。在附图中：
图1是根据本发明实施例的多输入多输出MIMO的处理方法的流程图；
图2是根据本发明实施例的多输入多输出MIMO的处理装置结构框图；
图3是根据本发明实施例的多输入多输出MIMO的处理装置可选结构框图一；
图4是根据本发明实施例的多输入多输出MIMO的处理装置可选结构框图二；
图5是根据本发明实施例的多输入多输出MIMO的处理装置可选结构框图三；
图6是根据本发明可选实施例的3D MU-MIMO系统结构图；
图7是根据本发明可选实施例的基站8*8均匀面阵天线配置下三种方案的SINR的CDF曲线的比较示意图；
图8是根据本发明可选实施例的基站8*16均匀面阵天线配置下三种方案的SINR的CDF曲线的比较示意图；
图9是根据本发明可选实施例的基站在垂直方向上部署不同天线数时，不同方案的每用户频谱效率的对比示意图；
图10是根据本发明可选实施例的采用最大化SLNR准则替代第二步预编码ZF准则时不同方案SINR的CDF曲线示意图。
具体实施方式
下文中将参考附图并结合实施例来详细说明本发明。需要说明的是，在不冲突的情况下，本申请中的实施例及实施例中的特征可以相互组合。
需要说明的是，本发明的说明书和权利要求书及上述附图中的术语“第一”、“第二”等是用于区别类似的对象，而不必用于描述特定的顺序或先后次序。
在本实施例中提供了一种多输入多输出MIMO的处理方法，图1是根据本发明实施例的多输入多输出MIMO的处理方法的流程图，如图1所示，该流程包括如下步骤：
步骤S102：基站获取基站覆盖范围内终端在列信道上的信道状态信息，并依据信道状态信息选择终端相关性满足预设条件的多个终端，其中，列信道为终端与基站垂直方向上天线间的传输信道；
步骤S104：基站依据信道状态信息确定多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量；
步骤S106：终端依据波束赋形矢量得到与波束赋形矢量对应的水平信道，并通过预设规则在水平信道的水平方向上进行预编码矩阵计算。
通过本发明实施例，基站获取基站覆盖范围内终端在列信道上的信道状态信息，并依据 信道状态信息选择终端相关性满足预设条件的多个终端，其中，列信道为终端与基站垂直方向上天线间的传输信道；进而基站依据信道状态信息确定多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量，并依据波束赋形矢量得到与波束赋形矢量对应的水平信道，并通过预设规则在水平信道的水平方向上进行预编码矩阵计算，可见在本实施例中通过分析信道特性，选出合适的服务终端集合，然后采用对信道降维的两步预编码实现多用户预编码设计，与相关技术中只设计水平方向预编码矩阵的MIMO系统相比能够实现较好的性能，同时降低了计算复杂度，从而解决了相关技术中3D-MIMO预编码矩阵运算的复杂度高的问题。
对于本实施例步骤S102中涉及到的基站获取基站覆盖范围内终端的信道状态信息的方式，在本实施例的可选实施方式中，可以通过如下方式来实现：
步骤S102-1：基站向基站覆盖范围内的终端发送信道状态信息参考符号CSI-RS；
步骤S102-2：基站接收终端依据CSI-RS对信道进行测量后发送的信道状态信息。
基于上述步骤S102-1和步骤S102-2，在基站在获取到信道状态信息后，依据信道状态信息选择终端相关性满足预设条件的多个终端，而该获取多个终端的方式包括：
步骤S102-3：基站预先确定满足预设条件的多个终端的预定数量；
步骤S102-4：基站依据信道状态信息选择出信道特性最好的终端作为初始终端；
步骤S102-5：基站获取已选出的初始终端与多个待选择的终端之间的多个弦距离；
步骤S102-6：基站从多个弦距离中选择出与初始终端弦距离最远的预定数量的多个终端。
在本实施例的另一个可选实施方式中，在基站依据信道状态信息确定多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量之前，本实施例的方法还包括：
步骤S11：基站配置2D均匀面阵UPA，其中，2D均匀面阵UPA包括：Nt＝Nh×Nv根天线，Nh为水平方向列天线个数，Nv为垂直方向行天线个数，
步骤S12：基站为基站的每个小区中随机分布的k个终端中的每一个终端配置Nr＝1根天线；Hk表示第k个终端到基站的3D信道矩阵(Nr×(Nh×Nv)维)，
Figure PCTCN2016098603-appb-000036
Figure PCTCN2016098603-appb-000037
表示用户到基站第i列天线的信道矩阵(Nr×Nv维)，i＝1,2...Nh，k为正整数，k的取值为1，2，…，S，其中S表示当前组内的用户数。
基于上述步骤S11和步骤S12，本实施例中的基站通过如下公式依据信道状态信息确定多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量：
基站根据各列信道信息
Figure PCTCN2016098603-appb-000038
计算垂直方向的波束赋形矢量
Figure PCTCN2016098603-appb-000039
((Nh×Nv)×Nh维)，如下式所示：
Figure PCTCN2016098603-appb-000040
其中，各列信道信息为
Figure PCTCN2016098603-appb-000041
表示第k个用户的第i列信道矩阵(Nr×Nv维)；垂直方向的波束赋形矢量
Figure PCTCN2016098603-appb-000042
((Nh×Nv)×Nh维)，
Figure PCTCN2016098603-appb-000043
(A，B)的最大广义特征值对应的特征向量，
Figure PCTCN2016098603-appb-000044
P为发射功率，nk为各终端接收噪声，σ2为噪声功率。
基于上述波束赋形矢量，本实施例中涉及到的基站依据波束赋形矢量得到与波束赋形矢量对应的水平信道，并通过预设规则在水平信道的水平方向上进行预编码矩阵计算的方式，可以通过如下方式来实现：
步骤S21：基站将波束赋形矢量
Figure PCTCN2016098603-appb-000045
应用于各列垂直信道，计算得到如下公式所示的水平信道：
Figure PCTCN2016098603-appb-000046
维度为Nr×Nh，k取值为1，2，…，S；
步骤S22：基站采用迫零ZF准则计算水平信道上水平方向的多个终端预编码矩阵
Figure PCTCN2016098603-appb-000047
令
Figure PCTCN2016098603-appb-000048
((Nr×S)×Nh维)，进而得到所述预编码矩阵的公式为
Figure PCTCN2016098603-appb-000049
(Nh×S维)，其中每一列代表了对应用户的等效水平预编码矩阵，即
Figure PCTCN2016098603-appb-000050
为上述矩阵的第k列，表示第k个用户的等效水平预编码矩阵。其中，
Figure PCTCN2016098603-appb-000051
表示第k个用户的等效水平信道，
Figure PCTCN2016098603-appb-000052
是
Figure PCTCN2016098603-appb-000053
的共轭转置。
通过以上的实施方式的描述，本领域的技术人员可以清楚地了解到根据上述实施例的方法可借助软件加必需的通用硬件平台的方式来实现，当然也可以通过硬件，但很多情况下前者是更佳的实施方式。基于这样的理解，本发明的技术方案本质上或者说对现有技术做出贡献的部分可以以软件产品的形式体现出来，该计算机软件产品存储在一个存储介质(如ROM/RAM、磁碟、光盘)中，包括若干指令用以使得一台终端设备(可以是手机，计算机，服务器，或者网络设备等)执行本发明各个实施例所述的方法。
在本实施例中还提供了一种多输入多输出MIMO的处理装置，该装置用于实现上述实施例及优选实施方式，已经进行过说明的不再赘述。如以下所使用的，术语“模块”可以实现预定功能的软件和/或硬件的组合。尽管以下实施例所描述的装置较佳地以软件来实现，但是硬件，或者软件和硬件的组合的实现也是可能并被构想的。
图2是根据本发明实施例的多输入多输出MIMO的处理装置结构框图，该装置应用于基站侧，如图2所示，该装置包括：获取模块22，设置为获取基站覆盖范围内终端在列信道上 的信道状态信息，并依据信道状态信息选择终端相关性满足预设条件的多个终端，其中，列信道为终端与基站垂直方向上天线间的传输信道；确定模块24，与获取模块22耦合连接，设置为依据信道状态信息确定多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量；处理模块26，与确定模块24耦合连接，设置为依据波束赋形矢量得到与波束赋形矢量对应的水平信道，并通过预设规则在水平信道的水平方向上进行预编码矩阵计算。
图3是根据本发明实施例的多输入多输出MIMO的处理装置可选结构框图一，如图3所示，该获取模块22包括：发送单元302，设置为向基站覆盖范围内的终端发送信道状态信息参考符号CSI-RS；接收单元304，与发送单元302耦合连接，设置为接收终端依据CSI-RS对信道进行测量后发送的信道状态信息。
此外，该获取模块22还包括：确定单元306，与接收单元304耦合连接，设置为预先确定满足预设条件的多个终端的预定数量；第一选择单元308，与确定单元306耦合连接，设置为依据信道状态信息选择出信道特性最好的终端作为初始终端；获取单元310，与选择单元308耦合连接，设置为获取已选出的初始终端与多个待选择的终端之间的多个弦距离；第二选择单元312，与获取单元310耦合连接，设置为从多个弦距离中选择出与初始终端弦距离最远的预定数量的多个终端。
图4是根据本发明实施例的多输入多输出MIMO的处理装置可选结构框图二，如图4所示，在基站依据信道状态信息确定多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量之前，装置还包括：第一配置模块42，与第二配置模块44耦合连接，设置为配置2D均匀面阵UPA，其中，2D均匀面阵UPA包括：Nt＝Nh×Nv根天线，Nh为水平方向列天线个数，Nv为垂直方向行天线个数；第二配置模块44，与获取模块22耦合连接，设置为为基站的每个小区中随机分布的k个终端中的每一个终端配置Nr＝1根天线；Hk表示第k个终端到基站的3D信道矩阵(Nr×(Nh×Nv)维)，
Figure PCTCN2016098603-appb-000054
表示用户到基站第i列天线的信道矩阵(Nr×Nv维)，i＝1,2...Nh，k为正整数。
基于图4中的第一配置模块42与第二配置模块，本实施例中涉及到的确定模块24，还设置为根据各列信道信息
Figure PCTCN2016098603-appb-000055
计算垂直方向的波束赋形矢量
Figure PCTCN2016098603-appb-000056
((Nh×Nv)×Nh维)，如下式所示：
Figure PCTCN2016098603-appb-000057
其中，各列信道信息为
Figure PCTCN2016098603-appb-000058
表示第k个用户的第i列信道矩阵(Nr×Nv维)；垂直方向的波束赋形矢量
Figure PCTCN2016098603-appb-000059
((Nh×Nv)×Nh维)，
Figure PCTCN2016098603-appb-000060
(A，B)的最大广 义特征值对应的特征向量，
Figure PCTCN2016098603-appb-000061
P为发射功率，nk为各终端接收噪声，σ2为噪声功率。
图5是根据本发明实施例的多输入多输出MIMO的处理装置可选结构框图三，如图5所示，该处理模块26包括：第一计算单元52，设置为将波束赋形矢量
Figure PCTCN2016098603-appb-000062
应用于各列垂直信道，计算得到如下公式所示的水平信道：
Figure PCTCN2016098603-appb-000063
第二计算单元54，与第一计算单元52耦合连接，设置为采用迫零ZF准则计算水平信道上水平方向的多个终端预编码矩阵
Figure PCTCN2016098603-appb-000064
令
Figure PCTCN2016098603-appb-000065
((Nr×S)×Nh维)，进而得到所述预编码矩阵的公式为
Figure PCTCN2016098603-appb-000066
(Nh×S维)，其中每一列代表了对应用户的等效水平预编码矩阵，即
Figure PCTCN2016098603-appb-000067
为上述矩阵的第k列，表示第k个用户的等效水平预编码矩阵。其中，
Figure PCTCN2016098603-appb-000068
表示第k个用户的等效水平信道，
Figure PCTCN2016098603-appb-000069
是
Figure PCTCN2016098603-appb-000070
的共轭转置。
需要说明的是，上述各个模块是可以通过软件或硬件来实现的，对于后者，可以通过以下方式实现，但不限于此：上述模块均位于同一处理器中；或者，上述模块分别位于多个处理器中。
下面将结合本发明的可选实施例对本发明进行举例说明；
本可选实施例提供了一种降低系统复杂度的方法，该方法技术方案的概述为两步预编码及适用于3D场景下的用户选择方案。详细的过程可以是：基站依据用户(对应于上述实施例中的终端)列信道相关性进行用户选择，选出列信道相关性差且在同一时频资源上服务的用户。然后进行两步预编码：第一步：根据用户的列信道信息，设计垂直方向的波束赋形矢量，达到先在垂直方向上区分用户的目的；第二步：利用第一步中设计的垂直波束赋形矢量，计算出等效水平信道，再根据等效水平信道，利用迫零(ZF)的方法进行水平方向的预编码矩阵设计。需要说明的是，列信道指用户与基站垂直方向上某一列天线间的传输信道。通过本可选实施例的上述方法，使得用户间的干扰可以大大降低。
下面对上述本可选实施例的降低系统复杂度的传输方法的过程进一步地进行描述：
图6是根据本发明可选实施例的3D MU-MIMO系统结构图，如图6所示，基站部署的是2D均匀面阵(UPA)，BS表示基站；MS表示用户；该系统含有一个基站和K个随机分布的用户，基站配置2D均匀面阵(UPA)，包含Nt＝Nh×Nv根天线，Nh为水平方向列天线个数，Nv为垂直方向行天线个数，每个用户配备Nr＝1根天线。Hk表示第k个用户到基站的3D信道矩阵(Nr×(Nh×Nv)维)，为了后续表示的方便，令
Figure PCTCN2016098603-appb-000071
其中
Figure PCTCN2016098603-appb-000072
(i＝1,2...Nh)表示用户到第i列天线的信道矩阵(Nr×Nv维)。假设基站发射功率为P，各用户接收噪声为nk，噪声功率为σ2。
用户k的接收信号yk可以表示为：
Figure PCTCN2016098603-appb-000073
其中，公式(1)中，xk为第k个用户的发送信号；
Figure PCTCN2016098603-appb-000074
表示第k个用户的垂直预编码矩阵，其中
Figure PCTCN2016098603-appb-000075
为Nv×1维矢量，且
Figure PCTCN2016098603-appb-000076
(Nh×1维，
Figure PCTCN2016098603-appb-000077
)表示第k个用户的水平方向的预编码矩阵。由公式(1)可以得到第k个用户的接收信干噪比(SINR)，如公式(2)所示：
Figure PCTCN2016098603-appb-000078
系统总频谱效率和每用户平均频谱效率分别为公式(3)和公式(4)所示：
Figure PCTCN2016098603-appb-000079
Figure PCTCN2016098603-appb-000080
基于上述分析，本可选实施例中提供的低复杂度的3D MU-MIMO传输方案的技术方案如下：
第一个阶段，基站向用户发送CSI-RS，用户根据接收到的CSI-RS测量信道状态信息，然后将信道状态信息反馈给基站，基站根据用户反馈的信道状态信息，利用弦距离的方法进行用户选择，选出垂直方向用户相关性小的S(S≤Nh)个用户集合进行服务。该用户选择的方法步骤包括：
步骤S41：定义初始用户集合Ω＝{1,2,...K}，初始化已选用户集合
Figure PCTCN2016098603-appb-000081
步骤S42：利用比例公平(PF)准则选出第一个用户，即：
Figure PCTCN2016098603-appb-000082
更新剩余用户集合Ω＝Ω-{s1}及已选用户集合γ＝γ+{s1}，并且令
Figure PCTCN2016098603-appb-000083
表示初始用户的信道矩阵的第i列；
步骤S43：对于l＝2:S个用户，根据弦距离最大准则进行选择
Figure PCTCN2016098603-appb-000084
更新剩余用户及已选用集合Ω＝Ω-{sl}，γ＝γ+{sl}，并更新
Figure PCTCN2016098603-appb-000085
步骤S44：选出第S个用户后循环结束，算法终止。
需要说明的是，弦距离：是一个表征矩阵(向量)间相关性的一个量，弦距离越大表示矩阵(向量)间相关性越小。定义如下：
Figure PCTCN2016098603-appb-000086
其中
Figure PCTCN2016098603-appb-000087
是矩阵(向量)H1，H2经过施密特正交化之后得到的标准正交基。
第二个阶段，在基站端对已选出的用户集合进行两步预编码矩阵的计算，分以下两步：
第一步：基站根据用户的各列信道信息
Figure PCTCN2016098603-appb-000088
以最大化垂直方向信漏噪比(SLNR)为准则，计算垂直方向的每列波束赋形矢量
Figure PCTCN2016098603-appb-000089
(Nv×1维)，如下式所示：
Figure PCTCN2016098603-appb-000090
其中，s.t.
Figure PCTCN2016098603-appb-000091
k＝1,...,S
该问题的解为：
Figure PCTCN2016098603-appb-000092
(A，B)的最大广义特征值对应的特征向量     (6)
其中，
Figure PCTCN2016098603-appb-000093
表示第k个用户的第i列信道矩阵(Nr×Nv维)。
从而，最终的垂直方向的预编码矩阵为：
Figure PCTCN2016098603-appb-000094
第二步：将第一步得到的垂直波束赋形矢量
Figure PCTCN2016098603-appb-000095
应用于各列垂直信道，得到等效水平信道如下式所示：
Figure PCTCN2016098603-appb-000096
再采用迫零(ZF)准则设计水平方向的多用户预编码矩阵
Figure PCTCN2016098603-appb-000097
令
Figure PCTCN2016098603-appb-000098
其中
Figure PCTCN2016098603-appb-000099
表示第k个用户的等效水平信道，
Figure PCTCN2016098603-appb-000100
是
Figure PCTCN2016098603-appb-000101
的共轭转置。那么水平预编码矩阵如下所示：
Figure PCTCN2016098603-appb-000102
下面结合本可选实施例的流程对上述过程进行说明；
1、基站信道状态信息获取：
步骤S31：基站向用户发送信道状态信息参考符号(CSI-RS)；
步骤S32：用户根据收到的CSI-RS进行信道测量；
步骤S33：用户将测得的信道反馈给基站；
2、用户选择，该过程可以是：
基站根据服务的用户数，定义初始用户集合Ω＝{1,2,...K}，初始化已选用户集合
Figure PCTCN2016098603-appb-000103
根据获得的用户信道状态信息，首先选出列信道范数最大的一个用户作为已选初始用户，即
Figure PCTCN2016098603-appb-000104
并更新剩余用户及已选用户集合，U1＝Hs1，Ω＝Ω-{s1}，γ＝γ+{s1}；
对于l＝2:S个用户，根据弦距离最大准则进行选择
Figure PCTCN2016098603-appb-000105
更新剩余用户及已选用集合
Figure PCTCN2016098603-appb-000106
Ω＝Ω-{sl}，γ＝γ+{sl}
选出第S个用户后循环结束，算法终止。
最3、预编码：
基站根据上述(5)的解得到垂直方向波束赋形矢量
Figure PCTCN2016098603-appb-000107
基站得到垂直波束赋形矢量
Figure PCTCN2016098603-appb-000108
后根据公式(8)至(10)，计算水平方向预编码矩阵
Figure PCTCN2016098603-appb-000109
用户选择及预编码操作完成后按照公式(1)的信号模型进行信号传输。需要说明的是，信漏噪比是指目标用户的信号功率与其泄露到其他用户的干扰功率和噪声功率之和的比值。
可见，通过本可选实施例提供的适用于3DMIMO系统中两步预编码的用户选择方案，采用在做预编码之前，先按照用户列信道相关性进行用户选择，选出用户列信道相关性差的用户再进行服务。2)给出一种既不同与传统单步预编码，又不同于现有的两步预编码的新的两步3D多用户预编码方案：第一步，根据垂直方向SLNR最大化准则，设计垂直方向做波束赋形，且各列天线的加权矢量相同；第二步，利用等效信道在水平方向做MU-MIMO预编码。
下面结合本发明可选实施例的具体实施例对本可选实施例进行详细说明；
实施例一：
在本可选实施例中以3D-UMi单小区有100用户为例，基站与用户间信道WINNERⅡ/+3D信道模型。基站配置天线为8*8均匀面阵，即水平方向8行天线，垂直方向8列天线，且水平垂直天线间距均为0.5λ(λ表示波长)。每用户配备单根天线。天线下倾角设为16度。基站发射功率Power＝44dBm，噪声功率Noise＝-174dBm/Hz。仿真20个Drop，每个Drop包含100个TTI。
图7是根据本发明可选实施例的基站8*8均匀面阵天线配置下三种方案的SINR的CDF曲线的比较示意图，如图7所示，该仿真将本方案与传统不做垂直波束赋形方案(图7中标为：NV方案)、垂直方向上做随机波束赋形方案(图7中标为：RV方案)进行了对比；将本可选实施例方案与NV方案以及RV方案进行比较。如图7所示比较了这三种方案的信干噪比(SINR)的累积分布(CDF)曲线。在8*8天线配置下，本可选实施例方案的用户SINR分布明显要比NV方案和RV方案好。表1给出了在8*8天线配置下每用户平均频谱效率，可以看到本可选实施例的方案比NV方案提升了20.64％，RV方案较NV方案只能提升10.04％。
表1
算法 每用户平均频谱效率(bit/s/Hz) 较NV方案增长百分比(％)
本可选实施例一 1.1760 20.64
RV方案 1.0727 10.04
NV方案 0.9748  
实施例二：
本可选实施例与实施例一具有相同的应用场景，仅仅是将基站天线配置改为8*16均匀面阵，即将垂直方向天线数改为16。
图8是根据本发明可选实施例的基站8*16均匀面阵天线配置下三种方案的SINR的CDF曲线的比较示意图，将本实施例二的方案与NV方案以及RV进行比较，三种方案的用户SINR的CDF曲线如图8所示，在8*16天线配置下本可选实施例能够实现更好的性能。图9是根据本发明可选实施例的基站在垂直方向上部署不同天线数时，不同方案的每用户频谱效率的对比示意图，如图9所示，给出了垂直方向天线数为8和16时，每用户平均频谱效率的比较，可以看出垂直方向天线数为16时比垂直天线为8时能够实现更高的用户频谱效率。进一步，表2为8*16天线配置下每用户平均频谱效率表，从表2可以看出，当垂直方向天线数为16时，本可选实施例的每用户平均频谱效率性能比NV方案提升了38.57％，而RV方案与NV方案相比，性能只能提升21.17％。
表2
算法 每用户平均频谱效率(bit/s/Hz) 较NV方案增长百分比(％)
本实施例二 1.3508 38.57
RV方案 1.1812 21.17
NV方案 0.9748  
实施例三：
对于上述涉及到的预编码，在本实施例中基站采用可替代的最大化SLNR准则，其它应用场景参数与实施例一相同。
将该场景下本实施例与NV方案以及RV方案进行比较。图10是根据本发明可选实施例的采用最大化SLNR准则替代第二步预编码ZF准则时不同方案SINR的CDF曲线示意图，如图10所示，比较了这三种方案的信干噪比(SINR)的累积分布(CDF)曲线。可以看出在采用最大化SLNR准则的情况下，能够实现与实施例一中采用ZF准则时相似的性能。表3为预编码采用最大化SLNR准则替代下每用户平均频谱效率的表，如表3所示，步给出了在该场景下每用户平均频谱效率，可以看到本发明方案比NV方案提升了22.12％，RV方案较NV方案提升11.20％，这更体现出了第二步可以采用SLNR准则替代ZF准则。
表3
算法 每用户平均频谱效率(bit/s/Hz) 较NV方案增长百分比(％)
本实施例三 1.1797 22.12
RV方案 1.0742 11.20
NV方案 0.9660  
系统计算复杂度分析：
从计算复杂度来看，本发明方案的3D预编码算法的主要计算复杂度在于第一步对Nv×Nv维矩阵的特征值分解，以及第二步对Nh×Nh维矩阵的求逆(用最大化SLNR时，求特征值分解)，总的计算复杂度为
Figure PCTCN2016098603-appb-000110
而等天线数下，传统的一步预编码算法的复杂度为：Ο((Nv×Nh)3)。假设Nv＝8，Nh＝8，那么本发明方案的复杂度为Ο(2×83)，传统算法的复杂度为Ο(643)＝Ο(85)，由此可见传统算法的复杂度要比本发明方案高得多。除此之外，本发明方案的用户选择只是按列信道(1×Nv维)进行的，而如果用同样的用户选择 方案，传统方案则要对整体信道(1×(Nh×Nv)维)进行，其计算复杂度也远比本实施例方案高。综上可知，本可选实施例在保证性能的同时，还大大降低了天线数较多时系统的复杂度。
本发明的实施例还提供了一种存储介质。可选地，在本实施例中，上述存储介质可以被设置为存储用于执行以下步骤的程序代码：
S1：基站获取基站覆盖范围内终端在列信道上的信道状态信息，并依据信道状态信息选择终端相关性满足预设条件的多个终端，其中，列信道为终端与基站垂直方向上天线间的传输信道；
S2：基站依据信道状态信息确定多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量；
S3：终端依据波束赋形矢量得到与波束赋形矢量对应的水平信道，并通过预设规则在水平信道的水平方向上进行预编码矩阵计算。
可选地，本实施例中的具体示例可以参考上述实施例及可选实施方式中所描述的示例，本实施例在此不再赘述。
显然，本领域的技术人员应该明白，上述的本发明的各模块或各步骤可以用通用的计算装置来实现，它们可以集中在单个的计算装置上，或者分布在多个计算装置所组成的网络上，可选地，它们可以用计算装置可执行的程序代码来实现，从而，可以将它们存储在存储装置中由计算装置来执行，并且在某些情况下，可以以不同于此处的顺序执行所示出或描述的步骤，或者将它们分别制作成各个集成电路模块，或者将它们中的多个模块或步骤制作成单个集成电路模块来实现。这样，本发明不限制于任何特定的硬件和软件结合。
以上所述仅为本发明的优选实施例而已，并不用于限制本发明，对于本领域的技术人员来说，本发明可以有各种更改和变化。凡在本发明的精神和原则之内，所作的任何修改、等同替换、改进等，均应包含在本发明的保护范围之内。
工业实用性
通过本发明实施例，基站获取基站覆盖范围内终端在列信道上的信道状态信息，并依据信道状态信息选择终端相关性满足预设条件的多个终端，其中，列信道为终端与基站垂直方向上天线间的传输信道；进而基站依据信道状态信息确定多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量，并依据波束赋形矢量得到与波束赋形矢量对应的水平信道，并通过预设规则在水平信道的水平方向上进行预编码矩阵计算，可见在本实施例中通过分析信道特性，选出合适的服务终端集合，然后采用对信道降维的两步预编码实现多用户预编码设计，与相关技术中只设计水平方向预编码矩阵的MIMO系统相比能够实现较好的性能，同时降低了计算复杂度，从而解决了相关技术中3D-MIMO预编码矩阵运算的复杂度高的问题。

Claims (12)

  1. 一种多输入多输出MIMO的处理方法，包括：
    基站获取所述基站覆盖范围内终端在列信道上的信道状态信息，并依据所述信道状态信息选择终端相关性满足预设条件的多个终端，其中，所述列信道为所述终端与所述基站垂直方向上天线间的传输信道；
    所述基站依据所述信道状态信息确定所述多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量；
    所述基站依据所述波束赋形矢量得到与所述波束赋形矢量对应的水平信道，并通过预设规则在所述水平信道的水平方向上进行预编码矩阵计算。
  2. 根据权利要求1所述的方法，其中，所述基站获取所述基站覆盖范围内终端的信道状态信息包括：
    所述基站向所述基站覆盖范围内的终端发送信道状态信息参考符号CSI-RS；
    所述基站接收所述终端依据所述CSI-RS对信道进行测量后发送的信道状态信息。
  3. 根据权利要求2所述的方法，其中，所述基站依据所述信道状态信息选择终端相关性满足预设条件的多个终端包括：
    所述基站预先确定满足预设条件的所述多个终端的预定数量；
    所述基站依据所述信道状态信息选择出信道特性最好的终端作为初始终端；
    所述基站获取已选出的所述初始终端与多个待选择的终端之间的多个弦距离；
    所述基站从所述多个弦距离中选择出与所述初始终端弦距离最远的预定数量的所述多个终端。
  4. 根据权利要求1所述的方法，其中，在所述基站依据所述信道状态信息确定所述多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量之前，所述方法还包括：
    所述基站配置2D均匀面阵UPA，其中，所述2D均匀面阵UPA包括：Nt＝Nh×Nv根天线，Nh为水平方向列天线个数，Nv为垂直方向行天线个数，
    所述基站为所述基站的每个小区中随机分布的k个终端中的每一个终端配置Nr＝1根天线；Hk表示第k个终端到所述基站的3D信道矩阵(Nr×(Nh×Nv)维)，所述
    Figure PCTCN2016098603-appb-100001
    表示用户到基站第i列天线的信道矩阵(Nr×Nv维)，i＝1,2...Nh，k为正整数，取值为1，2，…，S，其中S表示当前组内的用户数。
  5. 根据权利要求4所述的方法，其中，所述基站通过如下公式依据所述信道状态信息确定所述多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量：
    所述基站根据各列信道信息
    Figure PCTCN2016098603-appb-100002
    计算所述垂直方向的波束赋形矢量
    Figure PCTCN2016098603-appb-100003
    ((Nh×Nv)×Nh维)，如下式所示：
    Figure PCTCN2016098603-appb-100004
    其中，各列信道信息为
    Figure PCTCN2016098603-appb-100005
    表示第k个用户的第i列信道矩阵(Nr×Nv维)；垂直方向的波束赋形矢量
    Figure PCTCN2016098603-appb-100006
    ((Nh×Nv)×Nh维)，
    Figure PCTCN2016098603-appb-100007
    (A，B)的最大广义特征值对应的特征向量，
    Figure PCTCN2016098603-appb-100008
    P为发射功率，nk为各终端接收噪声，σ2为噪声功率。
  6. 根据权利要求5所述的方法，其中，所述基站依据所述波束赋形矢量得到与所述波束赋形矢量对应的水平信道，并通过预设规则在所述水平信道的水平方向上进行预编码矩阵计算包括：
    所述基站将所述波束赋形矢量
    Figure PCTCN2016098603-appb-100009
    应用于各列垂直信道，通过如下所示公式计算得到水平信道：
    Figure PCTCN2016098603-appb-100010
    维度为Nr×Nh，k取值为1，2，…，S；
    所述基站采用迫零ZF准则计算所述水平信道上水平方向的所述多个终端预编码矩阵
    Figure PCTCN2016098603-appb-100011
    令
    Figure PCTCN2016098603-appb-100012
    ((Nr×S)×Nh维)，进而得到所述预编码矩阵的公式为
    Figure PCTCN2016098603-appb-100013
    (Nh×S维)，其中，每一列代表对应用户的等效水平预编码矩阵，即
    Figure PCTCN2016098603-appb-100014
    为上述矩阵的第k列，表示第k个用户的等效水平预编码矩阵，其中，
    Figure PCTCN2016098603-appb-100015
    表示第k个用户的等效水平信道，
    Figure PCTCN2016098603-appb-100016
    是
    Figure PCTCN2016098603-appb-100017
    的共轭转置。
  7. 一种多输入多输出MIMO的处理装置，应用于基站侧，包括：
    获取模块，设置为获取所述基站覆盖范围内终端在列信道上的信道状态信息，并依据所述信道状态信息选择终端相关性满足预设条件的多个终端，其中，所述列信道为所述终端与所述基站垂直方向上天线间的传输信道；
    确定模块，设置为依据所述信道状态信息确定所述多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量；
    处理模块，设置为依据所述波束赋形矢量得到与所述波束赋形矢量对应的水平信道，并通过预设规则在所述水平信道的水平方向上进行预编码矩阵计算。
  8. 根据权利要求7所述的装置，其中，所述获取模块包括：
    发送单元，设置为向所述基站覆盖范围内的终端发送信道状态信息参考符号CSI-RS；
    接收单元，设置为接收所述终端依据所述CSI-RS对信道进行测量后发送的信道状态信息。
  9. 根据权利要求8所述的装置，其中，所述获取模块还包括：
    确定单元，设置为预先确定满足预设条件的所述多个终端的预定数量；
    第一选择单元，设置为依据所述信道状态信息选择出信道特性最好的终端作为初始终端；
    获取单元，设置为获取已选出的所述初始终端与多个待选择的终端之间的多个弦距离；
    第二选择单元，设置为从所述多个弦距离中选择出与所述初始终端弦距离最远的预定数量的所述多个终端。
  10. 根据权利要求7所述的装置，其中，在所述基站依据所述信道状态信息确定所述多个终端在垂直方向上进行预编码矩阵计算得到的波束赋形矢量之前，所述装置还包括：
    第一配置模块，设置为配置2D均匀面阵UPA，其中，所述2D均匀面阵UPA包括：Nt＝Nh×Nv根天线，Nh为水平方向列天线个数，Nv为垂直方向行天线个数，
    第二配置模块，设置为为所述基站的每个小区中随机分布的k个终端中的每一个终端配置Nr＝1根天线；Hk表示第k个终端到所述基站的3D信道矩阵(Nr×(Nh×Nv)维)，所述
    Figure PCTCN2016098603-appb-100018
    表示用户到基站第i列天线的信道矩阵(Nr×Nv维)，i＝1,2...Nh，k为正整数。
  11. 根据权利要求10所述的装置，其中，
    所述确定模块，还设置为根据各列信道信息
    Figure PCTCN2016098603-appb-100019
    计算所述垂直方向的波束赋形矢量
    Figure PCTCN2016098603-appb-100020
    ((Nh×Nv)×Nh维)，如下式所示：
    Figure PCTCN2016098603-appb-100021
    其中，各列信道信息为
    Figure PCTCN2016098603-appb-100022
    表示第k个用户的第i列信道矩阵(Nr×Nv维)；垂直方向的波束赋形矢量
    Figure PCTCN2016098603-appb-100023
    ((Nh×Nv)×Nh维)，
    Figure PCTCN2016098603-appb-100024
    (A，B)的 最大广义特征值对应的特征向量，
    Figure PCTCN2016098603-appb-100025
    P为发射功率，nk为各终端接收噪声，σ2为噪声功率。
  12. 根据权利要求11所述的装置，其中，所述处理模块包括：
    第一计算单元，设置为将所述波束赋形矢量
    Figure PCTCN2016098603-appb-100026
    应用于各列垂直信道，计算得到如下公式所示的水平信道：
    Figure PCTCN2016098603-appb-100027
    维度为Nr×Nh，k取值为1，2，…，S；
    第二计算单元，设置为采用迫零ZF准则计算所述水平信道上水平方向的所述多个终端预编码矩阵
    Figure PCTCN2016098603-appb-100028
    令
    Figure PCTCN2016098603-appb-100029
    ((Nr×S)×Nh维)，进而得到所述预编码矩阵的公式为
    Figure PCTCN2016098603-appb-100030
    (Nh×S维)，其中每一列代表了对应用户的等效水平预编码矩阵，即
    Figure PCTCN2016098603-appb-100031
    为上述矩阵的第k列，表示第k个用户的等效水平预编码矩阵，其中，
    Figure PCTCN2016098603-appb-100032
    表示第k个用户的等效水平信道，
    Figure PCTCN2016098603-appb-100033
    是
    Figure PCTCN2016098603-appb-100034
    的共轭转置。
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