WO2017054339A1 - 一种迭代信道估计方法及装置、计算机存储介质 - Google Patents

一种迭代信道估计方法及装置、计算机存储介质 Download PDF

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WO2017054339A1
WO2017054339A1 PCT/CN2015/098506 CN2015098506W WO2017054339A1 WO 2017054339 A1 WO2017054339 A1 WO 2017054339A1 CN 2015098506 W CN2015098506 W CN 2015098506W WO 2017054339 A1 WO2017054339 A1 WO 2017054339A1
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noise ratio
output signal
signal
channel
demodulated
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English (en)
French (fr)
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叶峰
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中兴通讯股份有限公司
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/024—Channel estimation channel estimation algorithms

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  • the present invention relates to the field of wireless communication technologies, and in particular, to an iterative channel estimation method and apparatus, and a computer storage medium.
  • GSM Global System for Mobile Communication
  • the transmitting end usually adopts coding and interleaving techniques to resist the multipath fading existing in the air interface transmission; the receiving end uses the estimated channel impulse response.
  • the inter-symbol interference introduced in the transmission process is removed by an equalizer based on the Maximum Likelihood (ML) or Maximum a Posteriori probability (MAP), thereby detecting a useful signal.
  • ML Maximum Likelihood
  • MAP Maximum a Posteriori probability
  • the conventional conventional receiver for iterative equalization generally performs de-interleaving and decoding of the post-decoded bit data, and then performs inverse coding and re-interleaving processing, and then sends the channel estimator to the channel estimator for secondary channel impulse response estimation, thereby completing the iterative process.
  • Signal Detection Therefore, it is not difficult to find that the existing iterative receiver works based on the demodulation and decoding joint detection technology, the algorithm is more complicated, and the network delay is large.
  • the embodiments of the present invention provide an iterative channel estimation method and apparatus, and a computer storage medium, which are used to reduce the complexity of the iterative channel estimation algorithm and reduce the network delay.
  • An embodiment of the present invention provides an iterative channel estimation method, including:
  • Detecting the detection signal acquiring demodulation hard bits and demodulating soft bits
  • the feedback channel signal is acquired, and the iterative output signal is obtained by using the demodulated hard bit and the feedback channel signal.
  • the demodulation output signal to noise ratio parameter is a demodulation output signal to noise ratio
  • the demodulating output signal to noise ratio parameter according to the demodulation soft bit includes:
  • the soft demodulation statistical characteristics are estimated to obtain a demodulated output signal to noise ratio.
  • the demodulated output signal to noise ratio parameter is a demodulated output signal to noise ratio metric; and the demodulating output SNR parameter according to the demodulated soft bit includes:
  • the obtaining an iterative decision threshold includes:
  • the link performance in a variety of test environments and obtain the test signal-to-noise ratio when the frame-cut rate is preset in each test environment.
  • the frame-cut rate there is a frame-cut rate for the voice service (FER, frame).
  • the error rate indicates that the decoded voice frame needs to be discarded; the corresponding statement in the data service transmission refers to the block error rate (BLER).
  • the feedback channel signal is a channel impulse response, and if it is determined according to the comparison result, channel iteration is required, a feedback channel signal is acquired, and the iterative output signal is obtained by using the demodulation hard bit and the feedback channel signal.
  • the acquiring the feedback channel signal includes:
  • l is the multipath channel tap coefficient
  • L is the channel dispersion length, which is a constant
  • l is a value of [0 to L-1]
  • r(n+L-1) is received at the n+L-1th time.
  • An iterative output signal is obtained by performing iterative channel estimation using the demodulated hard bits and the feedback channel signal.
  • the acquiring the feedback channel signal further includes: responding to the k+1th channel impulse according to an effective length of the detection signal Perform time dimension expansion as follows to obtain the extended k+1th channel impulse response
  • r [r(L-1)r(L).....r(147)] T ;
  • r represents the detected signal vector received from time L-1 to time 147
  • D k represents the k-th iteration, the reconstructed signal matrix from time L-1 to time 147
  • L represents the channel dispersion length, which is a constant.
  • the method further includes:
  • the demodulation soft bit is used for decoding.
  • the method further includes:
  • the soft bits are demodulated for decoding.
  • An embodiment of the present invention further provides an iterative channel estimation apparatus, including:
  • a receiving unit configured to receive a detection signal sent by the transmitting end
  • a detecting unit configured to detect the detection signal, obtain demodulation hard bits and demodulate soft bits
  • An acquiring unit configured to obtain a demodulated output signal to noise ratio parameter according to the demodulated soft bit
  • Comparing unit configured to obtain an iterative decision threshold, and compare the demodulated output signal to noise ratio parameter with the decision threshold;
  • a processing unit configured to: when determining that channel iteration is required according to the comparison result, acquiring a feedback channel signal, and acquiring the iterative output signal by using the demodulation hard bit and the feedback channel signal.
  • a calculation module configured to calculate a soft demodulation statistical characteristic of the demodulation soft bit according to the demodulation soft bit
  • the obtaining module is configured to estimate the soft demodulation statistical characteristic to obtain a demodulated output signal to noise ratio.
  • the demodulation output signal to noise ratio parameter is a demodulation output signal to noise ratio metric
  • the obtaining unit is configured to: according to the demodulation soft bit search mapping relationship, obtain according to the search result of the mapping relationship Demodulating an output signal to noise ratio metric, wherein the mapping relationship stores a correspondence between a demodulated soft bit and a demodulated output signal to noise ratio metric.
  • the comparing unit includes:
  • the first obtaining module is configured to test the link performance in a plurality of test environments, and obtain a test signal to noise ratio when the frame deletion rate is a preset value in each test environment;
  • the second obtaining module is configured to obtain a demodulated output SNR parameter corresponding to the test signal to noise ratio in each test environment, and obtain a probability density distribution curve of the demodulated output SNR parameter in each test environment;
  • a third acquiring module configured to obtain a value corresponding to an intersection of each demodulated output signal to noise ratio parameter probability density distribution curve, and use a minimum value of the values as the iterative decision threshold value;
  • a comparison module configured to compare the demodulated output signal to noise ratio parameter with the decision threshold.
  • the processing unit includes:
  • the parameter obtaining module is configured to: when the demodulation output signal to noise ratio parameter is less than the threshold value, acquire a feedback channel signal, including:
  • l is the multipath channel tap coefficient
  • L is the channel dispersion length, which is a constant
  • l is a value of [0 to L-1]
  • r(n+L-1) is received at the n+L-1th time.
  • a signal generating module configured to perform iterative channel estimation by using the demodulated hard bit and the feedback channel signal to obtain an iterative output signal.
  • the parameter obtaining module is further configured to respond to the k+1th channel impulse according to the effective length of the detection signal. Perform time dimension expansion as follows to obtain the extended k+1th channel impulse response
  • r [r(L-1)r(L).....r(147)] T ;
  • r represents the detected signal vector received from time L-1 to time 147
  • D k represents the k-th iteration, the reconstructed signal matrix from time L-1 to time 147
  • L represents the channel dispersion length, which is a constant.
  • the apparatus further includes: a decoding unit configured to perform decoding by using the demodulation soft bit when it is determined that channel iteration is not required according to the comparison result.
  • the acquiring unit is further configured to acquire the next and the next next letter respectively.
  • the processing unit is further configured to compare the demodulated output signal to noise ratio parameter, the second demodulated output signal to noise ratio parameter, and the third demodulated output signal to noise ratio parameter;
  • the device also includes:
  • the decoding unit is configured to: the difference between the demodulated output signal to noise ratio parameter, the second demodulated output signal to noise ratio parameter, and the third demodulated output signal to noise ratio parameter is less than a preset value At the time, the demodulation soft bits are used for decoding.
  • the third obtaining module, the comparing module, the parameter obtaining module, the signal generating module, and the decoding unit may use a central processing unit (CPU) and a digital signal processor when performing processing.
  • CPU central processing unit
  • DSP Digital Singnal Processor
  • FPGA Field-Programmable Gate Array
  • Embodiments of the present invention also provide a computer storage medium storing computer executable instructions for performing the iterative channel estimation method described above.
  • the detection signal sent by the transmitting end is received, and the signal is detected to obtain a demodulated hard bit and a demodulated soft bit. Then, a demodulated output signal to noise ratio parameter is obtained according to the demodulation soft bit, and then an iterative decision threshold value is obtained, and the demodulated output signal to noise ratio parameter is compared with the decision threshold value. If it is determined according to the comparison result that channel iteration is needed, a feedback channel signal is acquired, and the iterative output signal is obtained by using the demodulation hard bit and the feedback channel signal.
  • the demodulation output signal to noise ratio parameter can be obtained according to the demodulation soft bit, and the solution is obtained.
  • the output signal-to-noise ratio parameter is compared with the obtained decision threshold value, and when the channel iteration is determined according to the comparison result, the feedback channel signal is acquired, and the demodulation is utilized.
  • the hard bits and the feedback channel signal acquire an iterative output signal, thereby avoiding the cumbersome processing in prior iterative schemes using the scheme of embodiments of the present invention. Therefore, the algorithm of the embodiment of the present invention is simple, and the network delay is small.
  • Embodiment 1 is a flowchart of an iterative channel estimation method according to Embodiment 1 of the present invention
  • FIG. 2 is a structural diagram of a conventional burst of a GSM system in the prior art
  • Embodiment 2 of the present invention is a schematic structural diagram of an implementation principle of Embodiment 2 of the present invention.
  • FIG. 5 is a schematic diagram of an iterative channel estimation apparatus according to Embodiment 3 of the present invention.
  • FIG. 6 is a structural diagram of an iterative channel estimation apparatus according to Embodiment 3 of the present invention.
  • an iterative channel estimation method includes:
  • Step 11 Receive a detection signal sent by the sending end.
  • Step 12 Detect the detection signal, and obtain demodulation hard bits and demodulation soft bits.
  • the detection of the detection signal in the embodiment of the present invention can be performed by any of the detection methods in the prior art.
  • the hard bits and the demodulated soft bits are demodulated by detecting the detection signal.
  • Step 13 Acquire a demodulated output signal to noise ratio parameter according to the demodulated soft bit.
  • the demodulated output signal to noise ratio parameter may be a demodulated output signal to noise ratio or a demodulated output signal to noise ratio metric.
  • the demodulated output signal to noise ratio parameter is a demodulated output signal to noise ratio
  • the soft demodulation statistical characteristics of the demodulated soft bit such as the mean value and the variance, may be calculated according to the demodulated soft bit. And then, estimating the soft demodulation statistical characteristics to obtain a demodulated output signal to noise ratio (eg Mean squared by variance, etc.).
  • the mapping relationship may be searched according to the demodulation soft bit, and the demodulated output is obtained according to the search result of the mapping relationship.
  • a signal to noise ratio metric in which a correspondence relationship between a demodulation soft bit and a demodulated output signal to noise ratio metric is stored in the mapping relationship.
  • Step 14 Acquire an iterative decision threshold, and compare the demodulated output SNR parameter with the decision threshold.
  • the iterative decision threshold can be obtained by testing link performance in various test environments (such as static, TU (urban), RA (rural) channel), and deleting each test environment.
  • the test signal-to-noise ratio when the frame rate is the preset value.
  • the preset value can be taken as 1%.
  • the demodulation output SNR parameters corresponding to the test signal-to-noise ratio in each test environment are obtained, and the probability density distribution curve of the demodulated output SNR parameter in each test environment is obtained. Obtaining a value corresponding to an intersection of each demodulated output SNR parameter probability density distribution curve, and using a minimum value of the values as the iterative decision threshold.
  • the demodulated output SNR parameter can be compared to the decision threshold. Specifically, the demodulated output signal to noise ratio or the demodulated output signal to noise ratio metric is compared with the decision threshold.
  • Step 15 If it is determined according to the comparison result that channel iteration is required, the feedback channel signal is acquired, and the iterative output signal is obtained by using the demodulation hard bit and the feedback channel signal.
  • FIG. 2 shows the structure of a conventional burst (NB) in the GSM system.
  • the training sequence code (TSC, Training Sequence Code) occupies 26 bits, and the effective signal (Data) and the tail bit (Trail) occupy 58 bits and 3 bits respectively on the left and right sides of the training sequence code, and the protection bits (GP) Accounted for 8.25 bits.
  • the tail bits are filled with all "0"s, and the training sequence code segments provide 16 pattern selections.
  • the receiving end needs to detect 116 symbols of the valid signal part.
  • Step 151 Obtain a channel impulse response after the kth channel iteration among them,
  • Step 152 Acquire an error signal e k (n+L-1) at the time of n+L-1 and the kth channel iteration, where
  • Step 153 Acquire the k+1th channel impulse response by using the error signal according to an LMS (least mean square) criterion.
  • Step 154 Perform iterative channel estimation by using the demodulation hard bit and the feedback channel signal to obtain an iterative output signal.
  • the channel in addition to the LMS criterion that can be utilized for channel iterative estimation, the channel can be iterated using RLS (Recurrence Least Square) criteria.
  • RLS Recurrence Least Square
  • the demodulation output signal to noise ratio parameter can be obtained according to the demodulation soft bit, and the solution is obtained. Comparing the output signal-to-noise ratio parameter with the obtained decision threshold value, and then, when determining that the channel iteration is required according to the comparison result, acquiring the feedback channel signal, and using the demodulation hard ratio And the feedback channel signal acquires an iterative output signal, thereby avoiding the cumbersome processing in the existing iterative scheme using the scheme of the embodiment of the present invention. Therefore, the algorithm of the embodiment of the present invention is simple, and the network delay is small.
  • FIG. 3 is a schematic diagram of an implementation principle of an iterative channel estimation method according to Embodiment 2 of the present invention.
  • the signal used for signal detection is a signal received by the transmitting end.
  • the signal used for signal detection is the signal received by the transmitting end and the iterative output signal generated by the last channel iteration.
  • the detection signal sent by the transmitting end is subjected to signal detection, and the demodulated hard bit and the demodulated soft bit are obtained.
  • the demodulated output signal to noise ratio parameter is then compared to the decision threshold.
  • the demodulated output signal to noise ratio parameter as the demodulation output signal to noise ratio as an example, if the demodulated output signal to noise ratio is smaller than the iterative determination threshold, the feedback channel signal is acquired, and the demodulated hard bit and the feedback channel signal are utilized. Get the iterative output signal. The iterative output signal is combined with the received detection signal for signal detection.
  • the demodulated soft bits are decoded.
  • a demodulated output signal-to-noise ratio of three consecutive times can be obtained. That is, the second demodulated output signal to noise ratio and the third demodulated output signal to noise ratio of the next and next channel iterations are respectively acquired, and the current demodulated output signal to noise ratio and the second demodulated output signal are obtained.
  • the noise ratio and the third demodulated output signal to noise ratio are compared between two. If the difference between the current demodulated output signal to noise ratio, the second demodulated output signal to noise ratio parameter, and the third demodulated output signal to noise ratio parameter is less than a preset value, the solution is utilized Soft bits are decoded for decoding.
  • the k+1th channel impulse response acquired in the first embodiment is obtained.
  • further time dimension expansion can be performed to obtain the expanded k+1 channel impulse response The way is as follows:
  • r represents the detected signal vector received from time L-1 to time 147
  • D k represents the k-th iteration, the reconstructed signal matrix from time L-1 to time 147
  • L represents the channel dispersion length, which is a constant.
  • Figure 4 shows the single-interference simulation performance of the TU50 adjacent frequency 200KHz. It can be seen from the simulation results that with the method of the embodiment of the present invention, the channel estimation algorithm in the 1st iteration has a performance gain of about 0.5 dB under adjacent channel interference, which is in line with expectations. It can be seen that the solution of the embodiment of the present invention can effectively improve the user perception of the actual application scenario in which the frequency planning is a closely multiplexed cell, without significantly increasing the load of the device.
  • the solution of the embodiment of the present invention is not limited to the GSM system, and is also applicable to, for example, WCDMA (Wideband Code Division Multiple Access) system, TD-SCDMA (Time Division-Synchronous Code Division Multiple Access, Time division synchronous code division multiple access) system, etc.
  • WCDMA Wideband Code Division Multiple Access
  • TD-SCDMA Time Division-Synchronous Code Division Multiple Access
  • Time division synchronous code division multiple access Time division synchronous code division multiple access
  • the iterative channel estimation apparatus of the third embodiment of the present invention includes:
  • the receiving unit 51 is configured to receive the detection signal sent by the transmitting end; the detecting unit 52, configured To obtain the demodulation hard bit and the demodulation soft bit, the acquiring unit 53 is configured to obtain a demodulated output signal to noise ratio parameter according to the demodulated soft bit; and the comparing unit 54 is configured to acquire an iteration. Determining a threshold value, and comparing the demodulated output signal to noise ratio parameter with the decision threshold value; the processing unit 55 is configured to: when determining that a channel iteration is required according to the comparison result, acquiring a feedback channel signal, and utilizing The demodulated hard bit and the feedback channel signal acquire an iterative output signal.
  • the demodulated output signal to noise comparable parameter is a demodulated output signal to noise ratio.
  • the obtaining unit 53 includes: a calculating module, configured to calculate a soft demodulation statistical characteristic of the demodulated soft bit according to the demodulated soft bit; and an acquiring module configured to perform the soft demodulation statistical characteristic It is estimated that the demodulated output signal to noise ratio is obtained.
  • the demodulated output signal to noise ratio parameter may be a demodulated output signal to noise ratio metric.
  • the acquiring unit 53 is configured to: according to the demodulation soft bit search mapping relationship, obtain a demodulated output signal to noise ratio metric according to the search result of the mapping relationship, where the solution is stored in the mapping relationship The correspondence between the soft-coded bits and the demodulated output signal-to-noise ratio metric.
  • the comparing unit 54 includes: a first acquiring module configured to test link performance in a plurality of test environments, and obtain a test signal to noise ratio when the frame deletion rate is a preset value in each test environment;
  • the module is configured to obtain a demodulation output SNR parameter corresponding to the test signal to noise ratio in each test environment, and obtain a demodulation output SNR parameter probability density distribution curve in each test environment;
  • the third acquisition module is configured as Obtaining a value corresponding to an intersection of each demodulated output SNR parameter probability density distribution curve, and using a minimum value of the value as the iterative decision threshold; and a comparison module configured to perform the demodulation output signal to noise ratio The parameter is compared to the decision threshold.
  • the processing unit 55 includes:
  • the parameter obtaining module is configured to: when the demodulation output signal to noise ratio parameter is less than the threshold value, acquire a feedback channel signal, including:
  • l is the multipath channel tap coefficient
  • L is the channel dispersion length, which is a constant
  • l is a value of [0 to L-1]
  • r(n+L-1) is received at the n+L-1th time.
  • a signal generating module configured to perform iterative channel estimation by using the demodulated hard bit and the feedback channel signal to obtain an iterative output signal.
  • the parameter obtaining module is further configured to respond to the k+1th channel impulse according to an effective length of the detection signal. Perform time dimension expansion as follows to obtain the extended k+1th channel impulse response
  • r represents the detected signal vector received from time L-1 to time 147
  • D k represents the k-th iteration, the reconstructed signal matrix from time L-1 to time 147
  • L represents the channel dispersion length, which is a constant.
  • the device further includes:
  • the decoding unit 56 is configured to, when it is determined that channel iteration is not required according to the comparison result, The demodulation soft bits are used for decoding.
  • the obtaining unit 53 is further configured to acquire a second demodulated output signal to noise ratio parameter and a third demodulated output signal to noise ratio parameter when the channel iteration is next and the next time respectively;
  • the processing unit 55 is further configured And comparing the demodulated output signal to noise ratio parameter, the second demodulated output signal to noise ratio parameter, and the third demodulated output signal to noise ratio parameter.
  • the decoding unit 56 is configured to perform a difference between the demodulated output signal to noise ratio parameter, the second demodulated output signal to noise ratio parameter, and the third demodulated output signal to noise ratio parameter. When the value is less than the preset value, the demodulation soft bit is used for decoding.
  • Embodiments of the present invention also provide a computer storage medium storing computer executable instructions for performing the iterative channel estimation method described above.
  • the demodulation output signal to noise ratio parameter can be obtained according to the demodulation soft bit, and the solution is obtained. And comparing the output signal to noise ratio parameter with the obtained decision threshold value, and then, when determining that the channel iteration is required according to the comparison result, acquiring a feedback channel signal, and acquiring the iterative output by using the demodulated hard bit and the feedback channel signal.
  • the detection signal sent by the transmitting end is received, and the signal is detected to obtain a demodulated hard bit and a demodulated soft bit. Then, obtaining a demodulated output signal to noise ratio parameter according to the demodulation soft bit, and then acquiring an iterative decision threshold value, and outputting the demodulated output signal to noise ratio parameter Compare with the decision threshold. If it is determined according to the comparison result that channel iteration is needed, a feedback channel signal is acquired, and the iterative output signal is obtained by using the demodulation hard bit and the feedback channel signal.
  • the demodulation output signal to noise ratio parameter can be obtained according to the demodulation soft bit, and the solution is obtained. And comparing the output signal to noise ratio parameter with the obtained decision threshold value, and then, when determining that the channel iteration is required according to the comparison result, acquiring a feedback channel signal, and acquiring the iterative output by using the demodulated hard bit and the feedback channel signal.

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Abstract

本发明提供一种迭代信道估计方法及装置、计算机存储介质，涉及通信技术领域，用以降低迭代信道估计算法的复杂性，减小网络时延。所述包括：接收发送端发送的检测信号；对所述检测信号进行检测，获取解调硬比特和解调软比特；根据所述解调软比特获取解调输出信噪比参数；获取迭代判决门限值，并将所述解调输出信噪比参数与所述判决门限值进行比较；若根据比较结果确定需要进行信道迭代，则获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号。

Description

一种迭代信道估计方法及装置、计算机存储介质 技术领域
本发明涉及无线通信技术领域，尤其涉及一种迭代信道估计方法及装置、计算机存储介质。
背景技术
全球移动通信系统(GSM，Global System for Mobile Communication)系统作为第2代(2G)移动通信系统的典型代表，已经历二十余年的发展。如何在不明显增加设备负荷、降低系统容量的条件下进一步提升用户感知、改善通话质量，是现阶段2G系统维护改进的重点课题。
对于基于时分多址(TDMA，Time Division Multiple Access)帧结构类型的通信系统而言，发送端通常采用编码、交织技术以抵抗空口传输中存在的多径衰落；接收端则利用估计的信道脉冲响应，采用基于最大似然(ML，Most Likelihood)或最大后验概率(MAP，maximum a posteriori probability)准则的均衡器将传输过程中引入的符号间干扰去除，从而检测出有用信号。
现有的用于迭代均衡的传统接收机，一般是将后级解交织、解码后的比特数据进行反编码及再交织处理后送入信道估计器进行二次信道脉冲响应估计，从而完成迭代的信号检测。由此不难发现，现有的迭代接收机的工作基于解调、解码联合检测技术，算法较为复杂，网络时延大。
发明内容
有鉴于此，本发明实施例提供一种迭代信道估计方法及装置、计算机存储介质，用以降低迭代信道估计算法的复杂性，减小网络时延。
本发明实施例提供一种迭代信道估计方法，包括：
接收发送端发送的检测信号；
对所述检测信号进行检测，获取解调硬比特和解调软比特；
根据所述解调软比特获取解调输出信噪比参数；
获取迭代判决门限值，并将所述解调输出信噪比参数与所述判决门限值进行比较；
若根据比较结果确定需要进行信道迭代，则获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号。
上述方案中，所述解调输出信噪比参数为解调输出信噪比；所述根据所述解调软比特获取解调输出信噪比参数包括：
根据所述解调软比特计算所述解调软比特的软解调统计特性；
对所述软解调统计特性进行估计，获取解调输出信噪比。
上述方案中，所述解调输出信噪比参数为解调输出信噪比度量；所述根据所述解调软比特获取解调输出信噪比参数包括：
根据所述解调软比特查找映射关系，根据对所述映射关系的查找结果获取解调输出信噪比度量，其中所述映射关系中存储有解调软比特和解调输出信噪比度量的对应关系。
上述方案中，所述获取迭代判决门限值包括：
在多种测试环境下测试链路性能，获取各测试环境下删帧率为预设值时的测试信噪比；这里，针对删帧率而言，对于语音业务存在删帧率(FER，frame error rate)指解码错误的语音帧需要被丢弃；在数据业务传输中对应的说法指误块率(BLER，block error rate)。
获取各测试环境下的测试信噪比对应的解调输出信噪比参数，并获得各测试环境下的解调输出信噪比参数概率密度分布曲线；
获取各解调输出信噪比参数概率密度分布曲线的交点对应的数值，并将所述数值中的最小值作为所述迭代判决门限值。
上述方案中，所述反馈信道信号为信道脉冲响应，所述若根据比较结果确定需要进行信道迭代，获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号包括：
若所述解调输出信噪比参数小于所述判决门限值，所述获取反馈信道信号，包括：
获取第k次信道迭代后的信道脉冲响应
Figure PCTCN2015098506-appb-000001
其中，
Figure PCTCN2015098506-appb-000002
获取在n+L-1时刻、第k次信道迭代时的误差信号ek(n+L-1)，其中，148-L；
Figure PCTCN2015098506-appb-000003
利用所述误差信号获取第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000004
Figure PCTCN2015098506-appb-000005
其中，l表示多径信道抽头系数；L表示信道弥散长度，为常数；l取值为[0～L-1]；r(n+L-1)表示在第n+L-1时刻接收到的检测信号，其中n＝(0，1，2…155)，μ为跟踪步长，为常数；
Figure PCTCN2015098506-appb-000006
表示用于重构第n+L-1时刻、第k次迭代无噪信号的输入向量；
利用所述解调硬比特和所述反馈信道信号进行迭代信道估计，获得迭代输出信号。
上述方案中，所述获取反馈信道信号还包括：根据所述检测信号的有效长度，对所述第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000007
按照如下方式做时间维度扩展，获得扩展后的第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000008
Figure PCTCN2015098506-appb-000009
r＝[r(L-1)r(L).....r(147)]T；
Figure PCTCN2015098506-appb-000010
其中，r表示从L-1时刻到147时刻接收的检测信号向量；Dk表示第k次迭代，从L-1时刻到147时刻的重构信号矩阵；L表示信道弥散长度，为常数。
上述方案中，所述方法还包括：
若根据比较结果确定不需要进行信道迭代，则利用所述解调软比特进行解码。
上述方案中，所述方法还包括：
分别获取下一次和再下一次信道迭代时的第二解调输出信噪比参数和第三解调输出信噪比参数；
若所述解调输出信噪比参数、所述第二解调输出信噪比参数和所述第三解调输出信噪比参数两两之间的差值小于预设值，则利用所述解调软比特进行解码。
本发明实施例还提供一种迭代信道估计装置，包括：
接收单元，配置为接收发送端发送的检测信号；
检测单元，配置为对所述检测信号进行检测，获取解调硬比特和解调软比特；
获取单元，配置为根据所述解调软比特获取解调输出信噪比参数；
比较单元，配置为获取迭代判决门限值，并将所述解调输出信噪比参数与所述判决门限值进行比较；
处理单元，配置为在根据比较结果确定需要进行信道迭代时，获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号。
上述方案中，所述解调输出信噪比参数为解调输出信噪比；所述获取 单元包括：
计算模块，配置为根据所述解调软比特计算所述解调软比特的软解调统计特性；
获取模块，配置为对所述软解调统计特性进行估计，获取解调输出信噪比。
上述方案中，所述解调输出信噪比参数为解调输出信噪比度量；所述获取单元配置为：根据所述解调软比特查找映射关系，根据对所述映射关系的查找结果获取解调输出信噪比度量，其中所述映射关系中存储有解调软比特和解调输出信噪比度量的对应关系。
上述方案中，所述比较单元包括：
第一获取模块，配置为在多种测试环境下测试链路性能，获取各测试环境下删帧率为预设值时的测试信噪比；
第二获取模块，配置为获取各测试环境下的测试信噪比对应的解调输出信噪比参数，并获得各测试环境下的解调输出信噪比参数概率密度分布曲线；
第三获取模块，配置为获取各解调输出信噪比参数概率密度分布曲线的交点对应的数值，并将所述数值中的最小值作为所述迭代判决门限值；
比较模块，配置为所述解调输出信噪比参数与所述判决门限值进行比较。
上述方案中，所述处理单元包括：
参数获取模块，配置为在若所述解调输出信噪比参数小于所述判决门限值时，获取反馈信道信号，包括：
获取第k次信道迭代后的信道脉冲响应
Figure PCTCN2015098506-appb-000011
其中，
Figure PCTCN2015098506-appb-000012
获取在n+L-1时刻、第k次信道迭代时的误差信号ek(n+L-1)，其中，148-L；
Figure PCTCN2015098506-appb-000013
利用所述误差信号获取第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000014
Figure PCTCN2015098506-appb-000015
其中，l表示多径信道抽头系数；L表示信道弥散长度，为常数；l取值为[0～L-1]；r(n+L-1)表示在第n+L-1时刻接收到的检测信号，其中n＝(0，1，2…155)，μ为跟踪步长，为常数；
Figure PCTCN2015098506-appb-000016
表示用于重构第n+L-1时刻、第k次迭代无噪信号的输入向量；
信号生成模块，配置为利用所述解调硬比特和所述反馈信道信号进行迭代信道估计，获得迭代输出信号。
上述方案中，所述参数获取模块，还配置为根据所述检测信号的有效长度，对所述第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000017
按照如下方式做时间维度扩展，获得扩展后的第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000018
Figure PCTCN2015098506-appb-000019
r＝[r(L-1)r(L).....r(147)]T；
Figure PCTCN2015098506-appb-000020
其中，r表示从L-1时刻到147时刻接收的检测信号向量；Dk表示第k次迭代，从L-1时刻到147时刻的重构信号矩阵；L表示信道弥散长度，为常数。
上述方案中，所述装置还包括：解码单元，配置为在根据比较结果确定不需要进行信道迭代时，利用所述解调软比特进行解码。
上述方案中，所述获取单元，还配置为分别获取下一次和再下一次信 道迭代时的第二解调输出信噪比参数和第三解调输出信噪比参数；
所述处理单元，还配置为将所述解调输出信噪比参数、所述第二解调输出信噪比参数和所述第三解调输出信噪比参数两两之间进行比较；
所述装置还包括：
解码单元，配置为在所述解调输出信噪比参数、所述第二解调输出信噪比参数和所述第三解调输出信噪比参数两两之间的差值小于预设值时，则利用所述解调软比特进行解码。
所述接收单元、所述检测单元、所述获取单元、所述比较单元、所述处理单元、所述计算模块、所述获取模块、所述第一获取模块、所述第二获取模块、所述第三获取模块、所述比较模块、所述参数获取模块、所述信号生成模块、所述解码单元在执行处理时，可以采用中央处理器(CPU，Central Processing Unit)、数字信号处理器(DSP，Digital Singnal Processor)或可编程逻辑阵列(FPGA，Field－Programmable Gate Array)实现。
本发明实施例还提供一种计算机存储介质，其中存储有计算机可执行指令，该计算机可执行指令用于执行上述迭代信道估计方法。
本发明实施例的上述技术方案的有益效果如下：
在本发明实施例中，接收发送端发送的检测信号，并对该信号进行检测获取解调硬比特和解调软比特。然后，根据所述解调软比特获取解调输出信噪比参数，继而获取迭代判决门限值，并将所述解调输出信噪比参数与所述判决门限值进行比较。若根据比较结果确定需要进行信道迭代，获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号。由此可以看出，利用本发明实施例的方案，在获取了检测信号的解调硬比特和解调软比特后，即可根据解调软比特获取解调输出信噪比参数，并将解调输出信噪比参数和获取的判决门限值进行比较，进而在根据比较结果确定需要进行信道迭代时，获取反馈信道信号，并利用所述解调 硬比特和所述反馈信道信号获取迭代输出信号，从而利用本发明实施例的方案避免了现有迭代方案中的繁琐处理。因而，利用本发明实施例的方案算法简单，网络时延小。
附图说明
图1为本发明实施例一的迭代信道估计方法的流程图；
图2为现有技术中GSM系统的常规突发脉冲的结构图；
图3为本发明实施例二的实现原理框架图；
图4为利用本发明实施例进行仿真后的仿真结果示意图；
图5本发明实施例三的迭代信道估计装置的示意图；
图6本发明实施例三的迭代信道估计装置的结构图。
具体实施方式
下面将结合附图和实施例，对本发明的具体实施方式作进一步详细描述。以下实施例用于说明本发明，但不用来限制本发明的范围。
如图1所示，本发明实施例一的迭代信道估计方法，包括：
步骤11、接收发送端发送的检测信号。
步骤12、对所述检测信号进行检测，获取解调硬比特和解调软比特。
在本发明实施例中对检测信号进行检测可利用现有技术中的任一检测方法执行。通过对检测信号进行检测，解调硬比特和解调软比特。
步骤13、根据所述解调软比特获取解调输出信噪比参数。
在本发明实施例中，解调输出信噪比参数可以为解调输出信噪比或解调输出信噪比度量。
如果所述解调输出信噪比参数为解调输出信噪比，那么在此步骤中，可根据所述解调软比特计算所述解调软比特的软解调统计特性，如均值、方差等，然后，对所述软解调统计特性进行估计，获取解调输出信噪比(如 均值平方除方差等)。
如果所述解调输出信噪比参数为解调输出信噪比度量，那么在此步骤中，可根据所述解调软比特查找映射关系，根据对所述映射关系的查找结果获取解调输出信噪比度量，其中所述映射关系中存储有解调软比特和解调输出信噪比度量的对应关系。
步骤14、获取迭代判决门限值，并将所述解调输出信噪比参数与所述判决门限值进行比较。
在此步骤中，所述迭代判决门限值可通过如下方式获取：在多种测试环境下(如静态、TU(城区)、RA(农村)信道)测试链路性能，获取各测试环境下删帧率为预设值时的测试信噪比。在此该预设值可取为1％。然后，获取各测试环境下的测试信噪比对应的解调输出信噪比参数，并获得各测试环境下的解调输出信噪比参数概率密度分布曲线。获取各解调输出信噪比参数概率密度分布曲线的交点对应的数值，并将所述数值中的最小值作为所述迭代判决门限值。
在获取了迭代判决门限值后，即可将所述解调输出信噪比参数与所述判决门限值进行比较。具体的，是将解调输出信噪比或解调输出信噪比度量与所述判决门限值进行比较。
步骤15、若根据比较结果确定需要进行信道迭代，则获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号。
如图2所示为GSM系统中常规突发脉冲(Normal Burst，NB)的结构。其中，训练序列码(TSC，Training Sequence Code)占26比特，有效信号(Data)及尾比特(Trail)在训练序列码的左右两侧，分别各占58比特及3比特，保护位(GP)占8.25比特。特别地，尾比特填充全“0”，训练序列码段提供16种图样选择。接收端需检出有效信号部分的116个符号。
若所述解调输出信噪比参数小于所述判决门限值，则执行下述过程。
具体的，在获取反馈信道信号时，包括如下过程：
步骤151、获取第k次信道迭代后的信道脉冲响应
Figure PCTCN2015098506-appb-000021
其中，
Figure PCTCN2015098506-appb-000022
步骤152、获取在n+L-1时刻、第k次信道迭代时的误差信号ek(n+L-1)，其中，
148-L；
Figure PCTCN2015098506-appb-000023
其中，l表示多径信道抽头系数；L表示信道弥散长度，为常数；l取值为[0～L-1]。通常L的取值为6。
步骤153、依据LMS(least mean square，最小均方差)准则，利用所述误差信号获取第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000024
Figure PCTCN2015098506-appb-000025
其中，r(n+L-1)表示在第n+L-1时刻接收到的检测信号，其中n＝(0，1，2…155)，μ为跟踪步长，为常数，在本实施例中可取0.008；
Figure PCTCN2015098506-appb-000026
表示用于重构第n+L-1时刻、第k次迭代无噪信号的输入向量。
步骤154、利用所述解调硬比特和所述反馈信道信号进行迭代信道估计，获得迭代输出信号。
在此步骤中，除了可以利用的LMS准则进行信道迭代估计外，还可采用RLS(Recurrence Least Square,递推最小二乘)准则对信道进行跟踪迭代。该RLS准则算法收敛速度快，但同时增加的复杂度也相对较大。
由此可以看出，利用本发明实施例的方案，在获取了检测信号的解调硬比特和解调软比特后，即可根据解调软比特获取解调输出信噪比参数，并将解调输出信噪比参数和获取的判决门限值进行比较，进而在根据比较结果确定需要进行信道迭代时，获取反馈信道信号，并利用所述解调硬比 特和所述反馈信道信号获取迭代输出信号，从而利用本发明实施例的方案避免了现有迭代方案中的繁琐处理。因而，利用本发明实施例的方案算法简单，网络时延小。
如图3所示，为本发明实施例二的迭代信道估计方法实施原理框架图。在本发明实施例中，对于第一次迭代而言，用于信号检测的信号为由发送端接收来的信号。对于第二迭代以后的信道迭代而言，用于信号检测的信号为由发送端接收来的信号以及上次信道迭代产生的迭代输出信号。根据该原理框架图，将发送端发送的检测信号进行信号检测，获取解调硬比特和解调软比特。然后，将所述解调输出信噪比参数与所述判决门限值进行比较。
根据比较结果的不同，可按照如下不同的方式处理：
以解调输出信噪比参数为解调输出信噪比为例，若解调输出信噪比小于迭代判断门限，则获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号。该迭代输出信号和接收到的检测信号一起再进行信号检测。
若解调输出信噪比大于迭代判断门限，则将所述解调软比特进行解码。此外，还可以获得连续三次的解调输出信噪比。也即，分别获取下一次和再下一次信道迭代时的第二解调输出信噪比和第三解调输出信噪比，并将当前的解调输出信噪比、第二解调输出信噪比和第三解调输出信噪比两两之间进行比较。若当前的解调输出信噪比、所述第二解调输出信噪比参数和所述第三解调输出信噪比参数两两之间的差值小于预设值，则利用所述解调软比特进行解码。
在此实施例中，与实施例中的不同的是，在实施例一的获取的第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000027
的基础上，为进一步优化系统性能，依据GSM系统脉冲的有效长度n＝0，1，…148-L，在本发明实施例中还可对其进行进一步 的时间维度扩展，获得扩展后的第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000028
方式如下：
Figure PCTCN2015098506-appb-000029
r＝[r(L-1)r(L).....r(147)]T，那么，
Figure PCTCN2015098506-appb-000030
其中，r表示从L-1时刻到147时刻接收的检测信号向量；Dk表示第k次迭代，从L-1时刻到147时刻的重构信号矩阵；L表示信道弥散长度，为常数。
从算法角度看，虽然LMS本身收敛速度较慢，但由于信道迭代估计时引入包括已知训练序列码以外的解调数据段所有硬判信息，有效地规避了算法瓶颈、使得至少一次迭代后的信道跟踪性能更可靠，提升接收机信号检测能力。而且该算法简单，网络时延小。
图4所示为TU50邻频200KHz单干扰仿真性能。根据仿真结果可以看出，利用本发明实施例的方法，在1次迭代信道估计算法在邻频干扰下存在0.5dB左右性能增益，符合预期。可见，利用本发明实施例的方案可在不明显增加设备负荷的同时，可有效改善频率规划为紧密复用小区的实际应用场景的用户感知度。当然，本发明实施例的方案并不局限于GSM系统，还可同样适用于诸如WCDMA(Wideband Code Division Multiple Access，宽带码分多址)系统、TD-SCDMA(Time Division-Synchronous Code Division Multiple Access，时分同步码分多址)系统等。
如图5所示，本发明实施例的三的迭代信道估计装置，包括：
接收单元51，配置为接收发送端发送的检测信号；检测单元52，配置 为对所述检测信号进行检测，获取解调硬比特和解调软比特；获取单元53，配置为根据所述解调软比特获取解调输出信噪比参数；比较单元54，配置为获取迭代判决门限值，并将所述解调输出信噪比参数与所述判决门限值进行比较；处理单元55，配置为在根据比较结果确定需要进行信道迭代时，获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号。
在本发明实施例中，所述解调输出信噪可比参数为解调输出信噪比。此时，所述获取单元53包括：计算模块，配置为根据所述解调软比特计算所述解调软比特的软解调统计特性；获取模块，配置为对所述软解调统计特性进行估计，获取解调输出信噪比。
或者，所述解调输出信噪比参数可为解调输出信噪比度量。此时，所述获取单元53具体配置为：根据所述解调软比特查找映射关系，根据对所述映射关系的查找结果获取解调输出信噪比度量，其中所述映射关系中存储有解调软比特和解调输出信噪比度量的对应关系。
具体的，所述比较单元54包括：第一获取模块，配置为在多种测试环境下测试链路性能，获取各测试环境下删帧率为预设值时的测试信噪比；第二获取模块，配置为获取各测试环境下的测试信噪比对应的解调输出信噪比参数，并获得各测试环境下的解调输出信噪比参数概率密度分布曲线；第三获取模块，配置为获取各解调输出信噪比参数概率密度分布曲线的交点对应的数值，并将所述数值中的最小值作为所述迭代判决门限值；比较模块，配置为所述解调输出信噪比参数与所述判决门限值进行比较。
具体的，所述处理单元55包括：
参数获取模块，配置为在若所述解调输出信噪比参数小于所述判决门限值时，获取反馈信道信号，包括：
获取第k次信道迭代后的信道脉冲响应
Figure PCTCN2015098506-appb-000031
其中，
Figure PCTCN2015098506-appb-000032
获取在n+L-1时刻、第k次信道迭代时的误差信号ek(n+L-1)，其中，148-L；
Figure PCTCN2015098506-appb-000033
利用所述误差信号获取第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000034
Figure PCTCN2015098506-appb-000035
其中，l表示多径信道抽头系数；L表示信道弥散长度，为常数；l取值为[0～L-1]；r(n+L-1)表示在第n+L-1时刻接收到的检测信号，其中n＝(0，1，2…155)，μ为跟踪步长，为常数；
Figure PCTCN2015098506-appb-000036
表示配置为重构第n+L-1时刻、第k次迭代无噪信号的输入向量；
信号生成模块，配置为利用所述解调硬比特和所述反馈信道信号进行迭代信道估计，获得迭代输出信号。
此外，为了进一步优化系统性能，所述参数获取模块，还配置为根据所述检测信号的有效长度，对所述第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000037
按照如下方式做时间维度扩展，获得扩展后的第k+1次的信道脉冲响应
Figure PCTCN2015098506-appb-000038
Figure PCTCN2015098506-appb-000039
Figure PCTCN2015098506-appb-000040
其中，r表示从L-1时刻到147时刻接收的检测信号向量；Dk表示第k次迭代，从L-1时刻到147时刻的重构信号矩阵；L表示信道弥散长度，为常数。
此外，如图6所示，所述装置还包括：
解码单元56，配置为在根据比较结果确定不需要进行信道迭代时，利 用所述解调软比特进行解码。
或者，所述获取单元53，还配置为分别获取下一次和再下一次信道迭代时的第二解调输出信噪比参数和第三解调输出信噪比参数；所述处理单元55还配置为将所述解调输出信噪比参数、所述第二解调输出信噪比参数和所述第三解调输出信噪比参数两两之间进行比较。此时，所述解码单元56配置为在所述解调输出信噪比参数、所述第二解调输出信噪比参数和所述第三解调输出信噪比参数两两之间的差值小于预设值时，则利用所述解调软比特进行解码。
本发明实施例还提供一种计算机存储介质，其中存储有计算机可执行指令，该计算机可执行指令用于执行上述迭代信道估计方法。
本发明实施例所述装置的工作原理可参照前述方法实施例的描述。
由此可以看出，利用本发明实施例的方案，在获取了检测信号的解调硬比特和解调软比特后，即可根据解调软比特获取解调输出信噪比参数，并将解调输出信噪比参数和获取的判决门限值进行比较，进而在根据比较结果确定需要进行信道迭代时，获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号，从而利用本发明实施例的方案避免了现有迭代方案中的繁琐处理。因而，利用本发明实施例的方案算法简单，网络时延小。
以上所述是本发明的优选实施方式，应当指出，对于本技术领域的普通技术人员来说，在不脱离本发明所述原理的前提下，还可以作出若干改进和润饰，这些改进和润饰也应视为本发明的保护范围。
工业实用性
在本发明实施例中，接收发送端发送的检测信号，并对该信号进行检测获取解调硬比特和解调软比特。然后，根据所述解调软比特获取解调输出信噪比参数，继而获取迭代判决门限值，并将所述解调输出信噪比参数 与所述判决门限值进行比较。若根据比较结果确定需要进行信道迭代，获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号。由此可以看出，利用本发明实施例的方案，在获取了检测信号的解调硬比特和解调软比特后，即可根据解调软比特获取解调输出信噪比参数，并将解调输出信噪比参数和获取的判决门限值进行比较，进而在根据比较结果确定需要进行信道迭代时，获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号，从而利用本发明实施例的方案避免了现有迭代方案中的繁琐处理。因而，利用本发明实施例的方案算法简单，网络时延小。

Claims (17)

  1. 一种迭代信道估计方法，包括：
    接收发送端发送的检测信号；
    对所述检测信号进行检测，获取解调硬比特和解调软比特；
    根据所述解调软比特获取解调输出信噪比参数；
    获取迭代判决门限值，并将所述解调输出信噪比参数与所述判决门限值进行比较；
    若根据比较结果确定需要进行信道迭代，则获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号。
  2. 根据权利要求1所述的方法，其中，所述解调输出信噪比参数为解调输出信噪比；所述根据所述解调软比特获取解调输出信噪比参数包括：
    根据所述解调软比特计算所述解调软比特的软解调统计特性；
    对所述软解调统计特性进行估计，获取解调输出信噪比。
  3. 根据权利要求1所述的方法，其中，所述解调输出信噪比参数为解调输出信噪比度量；所述根据所述解调软比特获取解调输出信噪比参数包括：
    根据所述解调软比特查找映射关系，根据对所述映射关系的查找结果获取解调输出信噪比度量，其中所述映射关系中存储有解调软比特和解调输出信噪比度量的对应关系。
  4. 根据权利要求1所述的方法，其中，所述获取迭代判决门限值包括：
    在多种测试环境下测试链路性能，获取各测试环境下删帧率为预设值时的测试信噪比；
    获取各测试环境下的测试信噪比对应的解调输出信噪比参数，并获得各测试环境下的解调输出信噪比参数概率密度分布曲线；
    获取各解调输出信噪比参数概率密度分布曲线的交点对应的数值，并 将所述数值中的最小值作为所述迭代判决门限值。
  5. 根据权利要求1所述的方法，其中，所述反馈信道信号为信道脉冲响应，所述若根据比较结果确定需要进行信道迭代，获取反馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号包括：
    若所述解调输出信噪比参数小于所述判决门限值，所述获取反馈信道信号，包括：
    获取所述解调硬比特与所述检测信号的训练序列码图案、尾比特的联合信息
    Figure PCTCN2015098506-appb-100001
    其中，
    Figure PCTCN2015098506-appb-100002
    k表示信道迭代的次数，为整数；
    获取第k次信道迭代后的信道脉冲响应
    Figure PCTCN2015098506-appb-100003
    其中，
    Figure PCTCN2015098506-appb-100004
    获取在n+L-1时刻、第k次信道迭代时的误差信号ek(n+L-1)，其中，148-L；
    Figure PCTCN2015098506-appb-100005
    利用所述误差信号获取第k+1次的信道脉冲响应
    Figure PCTCN2015098506-appb-100006
    Figure PCTCN2015098506-appb-100007
    其中，l表示多径信道抽头系数；L表示信道弥散长度，为常数；l取值为[0～L-1]，r(n+L-1)表示在第n+L-1时刻接收到的检测信号，其中n＝(0，1，2…155)，μ为跟踪步长，为常数；
    Figure PCTCN2015098506-appb-100008
    表示用于重构第n+L-1时刻、第k次迭代无噪信号的输入向量；
    利用所述解调硬比特和所述反馈信道信号进行迭代信道估计，获得迭代输出信号。
  6. 根据权利要求5所述的方法，其中，所述获取反馈信道信号还包括：根据所述检测信号的有效长度，对所述第k+1次的信道脉冲响应
    Figure PCTCN2015098506-appb-100009
    按照如下方式做时间维度扩展，获得扩展后的第k+1次的信道脉冲响应
    Figure PCTCN2015098506-appb-100010
    Figure PCTCN2015098506-appb-100011
    r＝[r(L-1)r(L).....r(147)]T；
    Figure PCTCN2015098506-appb-100012
    其中，r表示从L-1时刻到147时刻接收的检测信号向量；Dk表示第k次迭代，从L-1时刻到147时刻的重构信号矩阵；L表示信道弥散长度，为常数。
  7. 根据权利要求1至6任一项所述的方法，其中，所述方法还包括：
    若根据比较结果确定不需要进行信道迭代，则利用所述解调软比特进行解码。
  8. 根据权利要求1至6任一项所述的方法，其中，所述方法还包括：
    分别获取下一次和再下一次信道迭代时的第二解调输出信噪比参数和第三解调输出信噪比参数；
    若所述解调输出信噪比参数、所述第二解调输出信噪比参数和所述第三解调输出信噪比参数两两之间的差值小于预设值，则利用所述解调软比特进行解码。
  9. 一种迭代信道估计装置，包括：
    接收单元，配置为接收发送端发送的检测信号；
    检测单元，配置为对所述检测信号进行检测，获取解调硬比特和解调软比特；
    获取单元，配置为根据所述解调软比特获取解调输出信噪比参数；
    比较单元，配置为获取迭代判决门限值，并将所述解调输出信噪比参数与所述判决门限值进行比较；
    处理单元，配置为在根据比较结果确定需要进行信道迭代时，获取反 馈信道信号，并利用所述解调硬比特和所述反馈信道信号获取迭代输出信号。
  10. 根据权利要求9所述的装置，其中，所述解调输出信噪比参数为解调输出信噪比；所述获取单元包括：
    计算模块，配置为根据所述解调软比特计算所述解调软比特的软解调统计特性；
    获取模块，配置为对所述软解调统计特性进行估计，获取解调输出信噪比。
  11. 根据权利要求9所述的装置，其中，所述解调输出信噪比参数为解调输出信噪比度量；所述获取单元配置为：根据所述解调软比特查找映射关系，根据对所述映射关系的查找结果获取解调输出信噪比度量，其中所述映射关系中存储有解调软比特和解调输出信噪比度量的对应关系。
  12. 根据权利要求9所述的装置，其中，所述比较单元包括：
    第一获取模块，配置为在多种测试环境下测试链路性能，获取各测试环境下删帧率为预设值时的测试信噪比；
    第二获取模块，配置为获取各测试环境下的测试信噪比对应的解调输出信噪比参数，并获得各测试环境下的解调输出信噪比参数概率密度分布曲线；
    第三获取模块，配置为获取各解调输出信噪比参数概率密度分布曲线的交点对应的数值，并将所述数值中的最小值作为所述迭代判决门限值；
    比较模块，配置为所述解调输出信噪比参数与所述判决门限值进行比较。
  13. 根据权利要求9所述的装置，其中，所述处理单元包括：
    参数获取模块，配置为在若所述解调输出信噪比参数小于所述判决门限值时，获取反馈信道信号，包括：
    获取第k次信道迭代后的信道脉冲响应
    Figure PCTCN2015098506-appb-100013
    其中，
    Figure PCTCN2015098506-appb-100014
    获取在n+L-1时刻、第k次信道迭代时的误差信号ek(n+L-1)，其中，148-L；
    Figure PCTCN2015098506-appb-100015
    利用所述误差信号获取第k+1次的信道脉冲响应
    Figure PCTCN2015098506-appb-100016
    Figure PCTCN2015098506-appb-100017
    其中，l表示多径信道抽头系数；L表示信道弥散长度，为常数；l取值为[0～L-1]；r(n+L-1)表示在第n+L-1时刻接收到的检测信号，其中n＝(0，1，2…155)，μ为跟踪步长，为常数；
    Figure PCTCN2015098506-appb-100018
    表示用于重构第n+L-1时刻、第k次迭代无噪信号的输入向量；
    信号生成模块，配置为利用所述解调硬比特和所述反馈信道信号进行迭代信道估计，获得迭代输出信号。
  14. 根据权利要求13所述的装置，其中，
    所述参数获取模块，还配置为根据所述检测信号的有效长度，对所述第k+1次的信道脉冲响应
    Figure PCTCN2015098506-appb-100019
    按照如下方式做时间维度扩展，获得扩展后的第k+1次的信道脉冲响应
    Figure PCTCN2015098506-appb-100020
    Figure PCTCN2015098506-appb-100021
    r＝[r(L-1)r(L).....r(147)]T；
    Figure PCTCN2015098506-appb-100022
    其中，r表示从L-1时刻到147时刻接收的检测信号向量；Dk表示第 k次迭代，从L-1时刻到147时刻的重构信号矩阵；L表示信道弥散长度，为常数。
  15. 根据权利要求9至13任一项所述的装置，其中，所述装置还包括：
    解码单元，配置为在根据比较结果确定不需要进行信道迭代时，利用所述解调软比特进行解码。
  16. 根据权利要求9至13任一项所述的装置，其中，
    所述获取单元，还配置为：分别获取下一次和再下一次信道迭代时的第二解调输出信噪比参数和第三解调输出信噪比参数；
    所述处理单元，还配置为：将所述解调输出信噪比参数、所述第二解调输出信噪比参数和所述第三解调输出信噪比参数两两之间进行比较；
    所述装置还包括：
    解码单元，配置为在所述解调输出信噪比参数、所述第二解调输出信噪比参数和所述第三解调输出信噪比参数两两之间的差值小于预设值时，则利用所述解调软比特进行解码。
  17. 一种计算机存储介质，其中存储有计算机可执行指令，该计算机可执行指令用于执行所述权利要求1至8任一项所述的方法。
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CN112564881A (zh) * 2020-12-01 2021-03-26 国网安徽省电力有限公司 基于长短时多门限信道状态预测的5g通信自适应传输方法
CN114785434A (zh) * 2022-03-23 2022-07-22 北京睿信丰科技有限公司 S波段频道可用性检测方法、装置、设备、系统及介质

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CN101057469A (zh) * 2004-09-17 2007-10-17 诺基亚公司 用于扩频下行链路信道均衡的基于迭代和Turbo的方法和设备
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CN112564881A (zh) * 2020-12-01 2021-03-26 国网安徽省电力有限公司 基于长短时多门限信道状态预测的5g通信自适应传输方法
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CN114785434B (zh) * 2022-03-23 2022-12-02 北京睿信丰科技有限公司 S波段频道可用性检测方法、装置、设备、系统及介质

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