WO2016019657A1 - 一种频偏估计的方法和装置、存储介质 - Google Patents

一种频偏估计的方法和装置、存储介质 Download PDF

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WO2016019657A1
WO2016019657A1 PCT/CN2014/092359 CN2014092359W WO2016019657A1 WO 2016019657 A1 WO2016019657 A1 WO 2016019657A1 CN 2014092359 W CN2014092359 W CN 2014092359W WO 2016019657 A1 WO2016019657 A1 WO 2016019657A1
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frequency offset
value
estimation value
offset estimation
current subframe
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PCT/CN2014/092359
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English (en)
French (fr)
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魏继东
李斌
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中兴通讯股份有限公司
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Priority to US15/329,065 priority Critical patent/US9900184B2/en
Priority to EP14899441.1A priority patent/EP3179682A4/en
Publication of WO2016019657A1 publication Critical patent/WO2016019657A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2657—Carrier synchronisation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2669—Details of algorithms characterised by the domain of operation
    • H04L27/2671—Time domain
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2673—Details of algorithms characterised by synchronisation parameters
    • H04L27/2675—Pilot or known symbols
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2681—Details of algorithms characterised by constraints
    • H04L27/2682—Precision
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2681—Details of algorithms characterised by constraints
    • H04L27/2686—Range of frequencies or delays tested
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2689—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation
    • H04L27/2695—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation with channel estimation, e.g. determination of delay spread, derivative or peak tracking

Definitions

  • the present invention relates to communication signal processing technologies, and in particular, to a method and apparatus for frequency offset estimation, and a storage medium.
  • Orthogonal Frequency Division Multiplexing is a multi-carrier transmission technology in which subcarriers are orthogonal to each other. This technique requires that subcarriers are orthogonal to each other and are very sensitive to carrier frequency offset. The carrier frequency offset problem has become one of the core issues of current OFDM technology.
  • embodiments of the present invention are expected to provide a method and apparatus for frequency offset estimation, and a storage medium. For the problem of large frequency offset, both frequency offset estimation accuracy and complexity of large frequency offset estimation are reduced. degree.
  • an embodiment of the present invention provides a method for estimating a frequency offset, and the method may include:
  • the initial channel estimation by using the received SRS or Preamble code to obtain the first frequency offset estimation value of the current subframe includes:
  • Acquiring channel estimation value H u and Y u receive data by receiving a current sub-frame of SRS code or the current sub-frame Preamble;
  • n represents a sampling point sequence number
  • u represents a user equipment UE corresponding to the current subframe
  • k represents a subcarrier index corresponding to the UE
  • Ka Rx represents the receiving antenna index
  • * indicates a conjugate operation
  • IDFT indicates an inverse Fourier transform
  • Get current subframe ka Rx antenna receives the phase information of the time-domain sample values w u (n, ka Rx) of said receive antenna ka Rx current frame of the first sub frequency offset estimate f 0 u (ka Rx) .
  • the value f 0 u (ka Rx ) including:
  • the method further includes:
  • the pilot sequence included in the received current subframe determines a phase difference of adjacent pilot positions, and is within a range defined by an initial frequency offset value corresponding to the first frequency offset estimation value, Obtaining a dual pilot frequency offset estimation value according to the phase difference, including:
  • the double pilot frequency offset estimation value ⁇ f 2 (ka Rx ) of the receiving antenna ka Rx is obtained according to the dual pilot frequency offset estimation result ⁇ f 2 (u) (ka Rx ) and the following equation:
  • T is the maximum range value of the dual pilot frequency offset estimation value
  • l is a preset integer used to limit the dual pilot frequency offset estimation value to a predetermined range.
  • the initial frequency offset value corresponding to the first frequency offset estimation value is After the dual pilot frequency offset estimation value obtains the frequency offset estimation value of the current subframe, the method further includes:
  • the frequency offset estimation value f u (ka Rx ) of the current subframe is smoothed by filtering to obtain a frequency offset estimation value f (u) (ka Rx ) of the smoothed current subframe.
  • an embodiment of the present invention provides a device for estimating a frequency offset, where the device includes: a first acquiring unit, a second acquiring unit, a third obtaining unit, and a fourth acquiring unit, where
  • the first acquiring unit is configured to perform initial channel estimation by using the received SRS or Preamble code, and obtain a first frequency offset estimation value of the current subframe;
  • the second acquiring unit is configured to determine a frequency offset interval in which the first frequency offset estimation value is located, and acquire the first frequency according to a correspondence between a preset frequency offset interval and an initial frequency offset value.
  • the initial frequency offset value corresponding to the partial estimated value
  • the third acquiring unit is configured to determine a phase difference of the adjacent pilot positions based on the received pilot sequence included in the current subframe, and is defined by an initial frequency offset value corresponding to the first frequency offset estimation value. Within the range, obtaining a dual pilot frequency offset estimation value according to the phase difference;
  • the fourth acquiring unit is configured to acquire a frequency offset estimation value of the current subframe according to the initial frequency offset value corresponding to the first frequency offset estimation value and the dual pilot frequency offset estimation value.
  • the first acquiring unit is configured to:
  • Acquiring channel estimation value H u and Y u receive data by receiving a current sub-frame of SRS code or the current sub-frame Preamble;
  • n represents a sampling point sequence number
  • u represents a user equipment UE corresponding to the current subframe
  • k represents a subcarrier index corresponding to the UE
  • Ka Rx represents the receiving antenna index
  • * indicates a conjugate operation
  • IDFT indicates an inverse Fourier transform
  • the first acquiring unit is configured to:
  • the first acquiring unit is further configured to perform smoothing processing on the first frequency offset estimation value f 0 u (ka Rx ) of the current subframe of the receiving antenna ka Rx to obtain a smooth current current
  • the first frequency offset estimate of the subframe is f 1 (u) (ka Rx ).
  • the third acquiring unit is configured to:
  • the double pilot frequency offset estimation value ⁇ f 2 (ka Rx ) of the receiving antenna ka Rx is obtained from the double pilot frequency offset estimation result ⁇ f 1 (u) (ka Rx ) and the following equation:
  • T is the maximum range value of the dual pilot frequency offset estimation value
  • l is a preset integer used to limit the dual pilot frequency offset estimation value to a predetermined range.
  • the fourth acquiring unit is further configured to perform smoothing processing on the frequency offset estimation value f u (ka Rx ) of the current subframe by using a filtering manner to obtain a frequency offset estimation of the smoothed current subframe.
  • a storage medium having stored therein a computer program configured to perform the aforementioned method of frequency offset estimation.
  • an initial frequency offset value is obtained according to the first frequency offset estimation value determined by the SRS or Preamble code sent by the UE, and the frequency of the current subframe is obtained by combining the dual pilot frequency offset estimation value in the range of the initial frequency offset value.
  • the partial estimation value not only ensures the accuracy of the frequency offset estimation, but also reduces the complexity of the estimation of the large frequency offset.
  • FIG. 1 is a schematic flowchart of a method for estimating frequency offset according to an embodiment of the present invention
  • FIG. 2 is a schematic structural diagram of an apparatus for frequency offset estimation according to an embodiment of the present invention.
  • FIG. 1 is a flowchart of a method for estimating a frequency offset according to an embodiment of the present invention.
  • a UE is used.
  • This method can include:
  • S101 Perform initial channel estimation by using an SRS or Preamble code sent by a user equipment (UE, User Equipment), and obtain a first frequency offset estimation value of a current subframe of the UE.
  • UE User Equipment
  • step S101 may specifically include:
  • the UE acquires the channel estimation value H u and Y u receives data by receiving the current subframe SRS sent by the UE or the current sub-frame Preamble code; specific acquisition process are conventional means of achieving skilled in the art , will not repeat them here;
  • the time domain sample value w u of the current subframe of the receiving antenna ka Rx of the UE is acquired ( n,ka Rx ):
  • Ka Rx represents the receiving antenna index, Indicates the size of a resource block (RB, Resource Block) occupied by the UE, * indicates a conjugate operation, and IDFT indicates an inverse Fourier transform;
  • phase information acquired according to the time-domain sample values w u (n, ka Rx) of said receive antenna ka Rx UE in the current sub-frame the UE in a first frequency offset estimated ka Rx antenna receiving a current sub-frame The value f 0 u (ka Rx ); in detail, in the embodiment, the phase values of the first half and the second half of the time domain sample value w u (n, ka Rx ) of the current subframe may be separately performed.
  • phase difference between the front and back parts The phase difference between adjacent sampling points in the time domain sample value w u (n, ka Rx ) of the current subframe may also be averaged to obtain Then, according to Equation 2, the first frequency offset estimation value f 0 u (ka Rx ) of the current subframe of the UE in the receiving antenna ka Rx is obtained:
  • the f 0 u (ka Rx ) obtained by the formula 2 may be smoothed to obtain a first frequency offset estimation value f 0 (u) (ka Rx ) of the smoothed current subframe; specifically, The first frequency offset estimation value corresponding to the previous subframe of the current subframe may be weighted and summed with f 0 u (ka Rx ); it may be understood that the closer the time is to the current subframe, the greater the weight; the farther away from the current time Subframes have smaller weights.
  • the corresponding first frequency offset estimation value of the previous subframe of the current subframe may be used.
  • f 0 u (ka Rx ) is subjected to weighted summation according to Equation 3 to smooth out f 0 u (ka Rx ) to obtain a first frequency offset estimated value f 0 (u) of the smoothed current subframe (ka Rx ):
  • f 1 (u) (ka Rx ) is only smoother than f 0 u (ka Rx ), but f 0 u (ka Rx ) can also be used for subsequent processing, and f 1 (u) (ka Rx ) for subsequent processing is only a more preferable scheme of the embodiment, so the first frequency offset estimation value used in the subsequent processing may select f 0 u (ka Rx ) or The f 1 (u) (ka Rx ) is selected in the embodiment of the present invention.
  • S102 Determine a frequency offset interval range in which the first frequency offset estimation value is located, and obtain an initial frequency offset value corresponding to the first frequency offset estimation value according to a correspondence between the preset frequency offset interval range and the initial frequency offset value. ;
  • the preset correspondence between the preset frequency offset interval range and the initial frequency offset value may be a mapping table of upper and lower limits and initial frequency offset values of a specific frequency offset range interval, as shown in Table 1. Show,
  • the first frequency offset estimation value can be compared with the upper and lower limits of each frequency offset range section in Table 1, and the frequency offset range interval in which the first frequency offset estimation value is located can be determined, and then Correspondingly, an initial frequency offset value corresponding to the first frequency offset estimation value is obtained.
  • the initial frequency offset value corresponding to the first frequency offset estimation value of the receiving antenna ka Rx of the UE may be used. Said.
  • S103 Determine a phase difference of adjacent pilot positions based on a pilot sequence included in the received current subframe, and obtain, according to the phase difference, within a range defined by an initial frequency offset value corresponding to the first frequency offset estimation value. Dual pilot frequency offset estimate.
  • S103 may specifically include:
  • the double pilot frequency offset estimation value ⁇ f 2 (ka Rx ) of the UE at the receiving antenna ka Rx is obtained according to the dual pilot frequency offset estimation result ⁇ f 2 (u) (ka Rx ) and Equation 5:
  • T is the maximum range value of the dual pilot frequency offset estimation value
  • l is a preset integer used to limit the dual pilot frequency offset estimation value to a predetermined range.
  • S104 Obtain a frequency offset estimation value of the current subframe according to the initial frequency offset value corresponding to the first frequency offset estimation value and the dual pilot frequency offset estimation value.
  • the initial frequency offset value may be Guiding the double frequency bias estimate ⁇ f 2 (ka Rx) adding UE acquires the estimation value f u (ka Rx) offset in the current subframe of the receiving antenna ka Rx.
  • the UE may perform smoothing processing on the f u (ka Rx ) by filtering, Obtaining a frequency offset estimation value f (u) (ka Rx ) of the smoothed current subframe;
  • the frequency offset estimation value of the previous subframe of the receiving antenna ka Rx may be adopted by the UE.
  • f u (ka Rx) according to a weighted sum of the embodiment of formula 6 to obtain the current sub-frame, the smoothed frequency offset estimate f (u) (ka Rx) :
  • the foregoing solution is a method for estimating a frequency offset according to an embodiment of the present invention, where an initial frequency offset value is obtained according to a first frequency offset estimation value determined according to an SRS or a Preamble code sent by a UE, and is within a range of an initial frequency offset value.
  • Combining the dual pilot frequency offset estimation value to obtain the frequency offset estimation value of the current subframe not only ensures the frequency offset estimation accuracy, but also reduces the complexity of the large frequency offset estimation.
  • the apparatus 20 may include: a first acquiring unit 201, and a second acquiring.
  • the first acquiring unit 201 is configured to perform initial channel estimation by receiving an SRS or a Preamble code sent by the UE, and acquire a first frequency offset estimation value of the current subframe of the UE;
  • the second obtaining unit 202 is configured to determine a frequency range in which the first frequency offset estimation value is located, and according to the frequency range and a preset correspondence between the frequency range and an initial frequency offset value, Obtaining an initial frequency offset value corresponding to the first frequency offset estimation value;
  • the third acquiring unit 203 is configured to calculate a phase difference between two pilot positions based on the received two pilot sequences included in the current subframe of the UE, and within a range defined by the initial frequency offset value, according to The phase difference acquires a dual pilot frequency offset estimation value;
  • the fourth obtaining unit 204 is configured to acquire a frequency offset estimation value of the current subframe according to the initial frequency offset value and the dual pilot frequency offset estimation value.
  • the first obtaining unit 201 is configured to:
  • the UE acquires by receiving a current sub-frame SRS sent by the UE or the current subframe Preamble code channel estimation value H u and receiving data Y u;
  • n represents a sampling point sequence number
  • u represents a user equipment UE corresponding to the current subframe
  • k represents a subcarrier index corresponding to the UE
  • Ka Rx represents the receiving antenna index
  • * indicates a conjugate operation
  • IDFT indicates an inverse Fourier transform
  • the first acquiring unit 201 is configured to:
  • the first acquiring unit 201 is further configured to perform smoothing processing on the first frequency offset estimation value f 0 u (ka Rx ) of the current subframe of the receiving antenna ka Rx by the UE, to obtain smoothing.
  • the first frequency offset estimation value f 1 (u) (ka Rx ) of the current current subframe specifically, the first acquiring unit 201 may estimate the first frequency offset corresponding to the previous subframe of the current subframe f 0 u (ka Rx ) performs weighted summation; it can be understood that the closer the time is to the current subframe, the larger the weight; the farther away from the current subframe, the smaller the weight.
  • the first acquiring unit 201 may be configured according to a corresponding first frequency offset estimation value of a previous subframe of the current subframe. And f 0 u (ka Rx ) is subjected to weighted summation according to the following equation to smooth out f 0 u (ka Rx ) to obtain a first frequency offset estimated value f 1 (u) of the smoothed current subframe (ka Rx ) ):
  • f 1 (u) (ka Rx ) is only smoother than f 0 u (ka Rx ), but f 0 u (ka Rx ) can also be used for subsequent module processing, and f 1 (u ) (ka Rx) module for subsequent processing is merely a more preferred embodiment according to the present embodiment, therefore, a first frequency offset estimation value in the subsequent process modules may be used to select f 0 u (ka Rx) For example, f 1 (u) (ka Rx ) may be selected, which is not specifically limited in the embodiment of the present invention.
  • the correspondence between the preset frequency range and the initial frequency offset value may be a mapping table of upper and lower limits and initial frequency offset values of a specific frequency range interval, as shown in Table 1.
  • the second obtaining unit 202 may be configured to compare the first frequency offset estimation value with the upper and lower limits of each frequency range interval in Table 1, and determine the first frequency offset estimation.
  • the frequency range interval in which the value is located, and then the initial frequency offset value corresponding to the first frequency offset estimation value may also be acquired accordingly.
  • the initial frequency offset value corresponding to the first frequency offset estimation value of the receiving antenna ka Rx of the UE may be used. Said.
  • the third obtaining unit 203 is configured to:
  • T is the maximum range value of the dual pilot frequency offset estimation value
  • l is a preset integer used to limit the dual pilot frequency offset estimation value to a predetermined range.
  • the fourth obtaining unit 204 may pass the initial frequency offset value. Guiding the double frequency bias estimate ⁇ f 2 (ka Rx) acquired by adding the offset current subframe UE receiving antenna ka Rx estimate f u (ka Rx).
  • the fourth acquiring unit 204 is further configured to use the frequency of the current subframe.
  • the partial estimated value f u (ka Rx ) is smoothed by filtering to obtain a frequency offset estimated value f (u) (ka Rx ) of the smoothed current subframe.
  • the fourth acquiring unit 204 may receive the frequency offset estimation value of the previous subframe of the antenna ka Rx by using the UE.
  • the frequency offset estimation value f (u) (ka Rx ) of the smoothed current subframe is obtained by performing weighted summation with f u (ka Rx ) according to the following equation:
  • the embodiment provides a frequency offset estimation apparatus 20, which obtains an initial frequency offset value by using a first frequency offset estimation value determined according to an SRS or a Preamble code sent by the UE, and combines the double pilot in a range of the initial frequency offset value.
  • the frequency offset estimation value obtains the frequency offset estimation value of the current subframe, which not only ensures the accuracy of the frequency offset estimation, but also reduces the complexity of the estimation of the large frequency offset.
  • Embodiments of the present invention also describe a storage medium in which a computer program is stored, the computer program being configured to perform the method of frequency offset estimation of the foregoing embodiments.
  • embodiments of the present invention can be provided as a method, system, or computer program product. Accordingly, the present invention can take the form of a hardware embodiment, a software embodiment, or a combination of software and hardware. Moreover, the invention can take the form of a computer program product embodied on one or more computer-usable storage media (including but not limited to disk storage and optical storage, etc.) including computer usable program code.
  • the computer program instructions can also be stored in a computer readable memory that can direct a computer or other programmable data processing device to operate in a particular manner, such that the instructions stored in the computer readable memory produce an article of manufacture comprising the instruction device.
  • the apparatus implements the functions specified in one or more blocks of a flow or a flow and/or block diagram of the flowchart.
  • These computer program instructions can also be loaded onto a computer or other programmable data processing device such that a series of operational steps are performed on a computer or other programmable device to produce computer-implemented processing for execution on a computer or other programmable device.
  • the instructions provide steps for implementing the functions specified in one or more of the flow or in a block or blocks of a flow diagram.
  • the present invention obtains an initial frequency offset value by using a first frequency offset estimation value determined according to an SRS or a Preamble code sent by the UE, and obtains a frequency offset estimation of the current subframe by combining the dual pilot frequency offset estimation value in a range of the initial frequency offset value.
  • the value not only ensures the accuracy of the frequency offset estimation, but also reduces the complexity of the estimation of the large frequency offset.

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Abstract

本发明提供了一种频偏估计的方法、装置以及存储介质，所述频偏估计的方法包括：通过接收用户设备（UE）发送的探测参考信号（SRS）或Preamble码进行初始信道估计，获取UE当前子帧的第一频偏估计值（S101）；确定第一频偏估计值所处的频偏区间范围，并根据预设的频偏区间范围与初始频偏值之间的对应关系，获取第一频偏估计值对应的初始频偏值（S102）；基于接收的当前子帧包含的导频序列确定相邻导频位置的相位差，并在第一频偏估计值对应的初始频偏值限定的范围内，根据相位差获取双导频频偏估计值（S103）；根据所述第一频偏估计值对应的初始频偏值和所述双导频频偏估计值得到当前子帧的频偏估计值（S104）。

Description

一种频偏估计的方法和装置、存储介质 技术领域
本发明涉及通信信号处理技术，尤其涉及一种频偏估计的方法和装置、存储介质。
背景技术
正交频分复用(OFDM，Orthogonal Frequency Division Multiplexing)技术是一种子载波相互正交的多载波传输技术，这种技术要求子载波之间相互正交，并且对载波频率偏移非常敏感；所以，载波频率偏移问题成为当前OFDM技术的核心问题之一。
目前对于解决频偏较小的问题，已有很多精度高并且实现简单的方法；但是对于大频偏的问题，解决方案的精度都相对比较低，即使有些方法提高了频偏估计的精度，但同时也增加了实现的复杂度。
发明内容
为解决上述技术问题，本发明实施例期望提供一种频偏估计的方法和装置、存储介质，针对大频偏的问题，既保证频偏估计精度，而且还降低了对于大频偏估计的复杂度。
本发明实施例的技术方案是这样实现的：
第一方面，本发明实施例提供了一种频偏估计的方法，该方法可以包括：
通过接收的探测参考信号(SRS，Sounding Reference Signal)或Preamble码进行初始信道估计，获取当前子帧的第一频偏估计值；
确定所述第一频偏估计值所处的频偏区间，并根据预设的频偏区间与 初始频偏值之间的对应关系，获取所述第一频偏估计值对应的初始频偏值；
基于接收的当前子帧包含的导频序列确定相邻导频位置的相位差，并在所述第一频偏估计值对应的初始频偏值限定的范围内，根据所述相位差获取双导频频偏估计值；
根据所述第一频偏估计值对应的初始频偏值和所述双导频频偏估计值获取当前子帧的频偏估计值。
作为一种实施方式，所述通过接收的SRS或Preamble码进行初始信道估计，获取当前子帧的第一频偏估计值，包括：
通过接收当前子帧的SRS或者当前子帧的Preamble码来获取信道估计值Hu和接收数据Yu；
根据所述信道估计值Hu和所述接收数据Yu，并结合本地导频序列Pu和下式获取接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)：
Figure PCTCN2014092359-appb-000001
其中，n表示采样点序号，u表示所述当前子帧对应的用户设备UE，k表示所述UE对应的子载波索引，
Figure PCTCN2014092359-appb-000002
kaRx表示接收天线索引，
Figure PCTCN2014092359-appb-000003
表示所述UE所占用的资源块(RB，Resource Block)的大小，*表示共轭运算，IDFT表示傅里叶逆变换；
根据所述接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)的相位信息获取接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)。
作为一种实施方式，所述根据所述接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)的相位信息获取接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)，包括：
将所述当前子帧的时域采样值wu(n,kaRx)的前半部分和后半部分的相位值分别进行平均后，获取前、后两个部分之间的相位差
Figure PCTCN2014092359-appb-000004
根据下式获取所述接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)：
Figure PCTCN2014092359-appb-000005
作为一种实施方式，所述方法还包括：
对所述接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)进行平滑处理，得到平滑后的当前子帧的第一频偏估计值f1 (u)(kaRx)。
作为一种实施方式，所述基于接收的当前子帧包含的导频序列确定相邻导频位置的相位差，并在所述第一频偏估计值对应的初始频偏值限定的范围内，根据所述相位差获取双导频频偏估计值，包括：
根据所述接收天线kaRx的当前子帧包含的两个导频序列所得到的两个导频信道估计值
Figure PCTCN2014092359-appb-000006
和
Figure PCTCN2014092359-appb-000007
并按照下式获取接收天线kaRx的两个导频位置的相位差
Figure PCTCN2014092359-appb-000008
Figure PCTCN2014092359-appb-000009
其中，*表示共轭运算符，angle()表示求角度运算符；
通过所述两个导频序列的时间间隔Δt以及所述两个导频序列的相位差
Figure PCTCN2014092359-appb-000010
按照下式获取接收天线kaRx的双导频频偏估计结果Δf2 (u)(kaRx)：
Figure PCTCN2014092359-appb-000011
在所述初始频偏值
Figure PCTCN2014092359-appb-000012
限定的范围内，根据双导频频偏估计结果Δf2 (u)(kaRx)以及下式获取所述接收天线kaRx的双导频频偏估计值ΔΔf2(kaRx)：
Figure PCTCN2014092359-appb-000013
其中，T为所述双导频频偏估计值的最大范围值；l为预设整数，用于将所述双导频频偏估计值限定在预定的范围内。
作为一种实施方式，在根据所述第一频偏估计值对应的初始频偏值和 所述双导频频偏估计值获取当前子帧的频偏估计值之后，所述方法还包括：
对当前子帧的频偏估计值fu(kaRx)通过滤波的方式进行平滑处理，得到平滑后的当前子帧的频偏估计值f(u)(kaRx)。
第二方面，本发明实施例提供了一种频偏估计的装置，所述装置包括：第一获取单元、第二获取单元、第三获取单元和第四获取单元，其中，
所述第一获取单元，配置为通过接收的SRS或Preamble码进行初始信道估计，获取当前子帧的第一频偏估计值；
所述第二获取单元，配置为确定所述第一频偏估计值所处的频偏区间，并根据预设的频偏区间与初始频偏值之间的对应关系，获取所述第一频偏估计值对应的初始频偏值；
所述第三获取单元，配置为基于接收的所述当前子帧包含的导频序列确定相邻导频位置的相位差，并在所述第一频偏估计值对应的初始频偏值限定的范围内，根据所述相位差获取双导频频偏估计值；
所述第四获取单元，配置为根据所述第一频偏估计值对应的初始频偏值和所述双导频频偏估计值获取当前子帧的频偏估计值。
作为一种实施方式，所述第一获取单元，配置为：
通过接收当前子帧的SRS或者当前子帧的Preamble码来获取信道估计值Hu和接收数据Yu；
以及，根据所述信道估计值Hu和所述接收数据Yu，并结合本地导频序列Pu和下式获取接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)：
Figure PCTCN2014092359-appb-000014
其中，n表示采样点序号，u表示所述当前子帧对应的用户设备UE，k表示所述UE对应的子载波索引，
Figure PCTCN2014092359-appb-000015
kaRx表示接收天线索引，
Figure PCTCN2014092359-appb-000016
表示所述UE所占用的RB的大小，*表示共轭运算，IDFT表示傅里叶逆变换；
以及，根据所述接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)的相位信息获取接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)。
作为一种实施方式，所述第一获取单元，配置为：
将所述当前子帧的时域采样值wu(n,kaRx)的前半部分和后半部分的相位值分别进行平均后，获取前、后两个部分之间的相位差
Figure PCTCN2014092359-appb-000017
根据下式获取所述接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)：
Figure PCTCN2014092359-appb-000018
作为一种实施方式，所述第一获取单元，还配置为对所述接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)进行平滑处理，得到平滑后的当前子帧的第一频偏估计值f1 (u)(kaRx)。
作为一种实施方式，所述第三获取单元，配置为：
根据所述接收天线kaRx的当前子帧包含的两个导频序列所得到的两个导频信道估计值
Figure PCTCN2014092359-appb-000019
和
Figure PCTCN2014092359-appb-000020
并按照下式获取接收天线kaRx的两个导频位置的相位差
Figure PCTCN2014092359-appb-000021
Figure PCTCN2014092359-appb-000022
其中，*表示共轭运算符，angle()表示求角度运算符；
以及，通过所述两个导频序列的时间间隔Δt以及所述两个导频序列的相位差
Figure PCTCN2014092359-appb-000023
按照下式获取接收天线kaRx的双导频频偏估计结果Δf2 (u)(kaRx)：
Figure PCTCN2014092359-appb-000024
以及，在所述初始频偏值
Figure PCTCN2014092359-appb-000025
限定的范围内，根据双导频频偏 估计结果Δf1 (u)(kaRx)以及下式获取所述接收天线kaRx的双导频频偏估计值ΔΔf2(kaRx)：
Figure PCTCN2014092359-appb-000026
其中，T为所述双导频频偏估计值的最大范围值；l为预设整数，用于将所述双导频频偏估计值限定在预定的范围内。
作为一种实施方式，所述第四获取单元，还配置为对当前子帧的频偏估计值fu(kaRx)通过滤波的方式进行平滑处理，得到平滑后的当前子帧的频偏估计值f(u)(kaRx)。
一种存储介质，所述存储介质中存储有计算机程序，所述计算机程序配置为执行前述的频偏估计的方法。
本发明实施例通过根据UE发送的SRS或Preamble码所确定的第一频偏估计值得到初始频偏值，并且在初始频偏值的范围内结合双导频频偏估计值获取当前子帧的频偏估计值，既保证频偏估计精度，而且还降低了对于大频偏估计的复杂度。
附图说明
图1为本发明实施例提供的一种频偏估计的方法流程示意图；
图2为本发明实施例提供的一种频偏估计的装置结构示意图。
具体实施方式
下面将结合本发明实施例中的附图，对本发明实施例中的技术方案进行清楚、完整地描述。
参见图1，其示出了本发明实施例提供的一种频偏估计的方法流程，需要说明的是，为了能够清楚的对本发明实施例的技术方案进行说明，本实施例中以一个UE为例进行说明，可以理解的，本领域技术人员可以无需创造性劳动将一个UE为例的实施例应用于多个UE的实施例中。该方法可以 包括：
S101：通过接收用户设备(UE，User Equipment)发送的SRS或Preamble码进行初始信道估计，获取所述UE当前子帧的第一频偏估计值；
示例性地，步骤S101具体可以包括：
首先，通过接收由UE发送的当前子帧的SRS或者当前子帧的Preamble码来获取所述UE的信道估计值Hu和接收数据Yu；具体的获取过程为本领域技术人员的常规实现手段，在此不再赘述；
然后，根据所述UE的信道估计值Hu和接收数据Yu，并结合本地导频序列Pu和式1获取所述UE在接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)：
Figure PCTCN2014092359-appb-000027
其中，n表示采样点序号，u表示所述UE，k表示所述UE对应的子载波索引，
Figure PCTCN2014092359-appb-000028
kaRx表示接收天线索引，
Figure PCTCN2014092359-appb-000029
表示所述UE所占用的资源块(RB，Resource Block)的大小，*表示共轭运算，IDFT表示傅里叶逆变换；
接着，根据所述UE在接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)的相位信息获取所述UE在接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)；详细地，在本实施例中，可以将所述当前子帧的时域采样值wu(n,kaRx)的前半部分和后半部分的相位值分别进行平均后，获取前、后两个部分之间的相位差
Figure PCTCN2014092359-appb-000030
也可以对所述当前子帧的时域采样值wu(n,kaRx)中相邻采样点之间的相位差进行平均来得到
Figure PCTCN2014092359-appb-000031
随后根据式2获取所述UE在接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)：
Figure PCTCN2014092359-appb-000032
作为一种实施方式，可以对式2得到的f0 u(kaRx)进行平滑处理，得到平 滑后的当前子帧的第一频偏估计值f0 (u)(kaRx)；具体地，可以将当前子帧以前的子帧对应的第一频偏估计值与f0 u(kaRx)进行加权求和；可以理解的，时间上越接近当前子帧则权值越大；时间上越远离当前子帧则权值越小。
在本实施例中，可以根据当前子帧的前一个子帧的对应的第一频偏估计值
Figure PCTCN2014092359-appb-000033
与f0 u(kaRx)按照式3进行加权求和来对f0 u(kaRx)进行平滑处理，得到平滑后的当前子帧的第一频偏估计值f0 (u)(kaRx)：
Figure PCTCN2014092359-appb-000034
其中，p1为滤波因子，且0≤p1≤1。
可以理解的，f1 (u)(kaRx)仅较f0 u(kaRx)更加的平滑，但是f0 u(kaRx)也同样可以用于后续的处理，而将f1 (u)(kaRx)用于后续的处理仅是本实施例的一个更为优选的方案，所以，后续处理过程中所使用的第一频偏估计值既可以选择f0 u(kaRx)，也可以选择f1 (u)(kaRx)，本发明实施例对此不作具体的限定。
S102：确定第一频偏估计值所处的频偏区间范围，并根据预设的频偏区间范围与初始频偏值之间的对应关系，获取第一频偏估计值对应的初始频偏值；
示例性地，预设的所述频偏区间范围与初始频偏值之间的对应关系可以是一张具体的频偏范围区间的上、下限与初始频偏值的映射表，如表1所示，
表1
Figure PCTCN2014092359-appb-000035
Figure PCTCN2014092359-appb-000036
由表1可知，可以将所述第一频偏估计值与表1中的各频偏范围区间的上、下限进行比较，确定第一频偏估计值所处的频偏范围区间，然后还可以相应地获取到所述第一频偏估计值对应的初始频偏值。在本实施例中，与所述UE在接收天线kaRx的第一频偏估计值所对应的初始频偏值可以用
Figure PCTCN2014092359-appb-000037
表示。
S103：基于接收的当前子帧包含的导频序列确定相邻导频位置的相位差，并在所述第一频偏估计值对应的初始频偏值限定的范围内，根据所述相位差获取双导频频偏估计值。
作为一种实施方式，在本实施例中，S103具体可以包括：
首先，根据所述UE在接收天线kaRx的当前子帧包含的两个导频序列所得到的两个导频信道估计值
Figure PCTCN2014092359-appb-000038
和
Figure PCTCN2014092359-appb-000039
按照式3获取所述UE在接收天线kaRx的两个导频位置的相位差
Figure PCTCN2014092359-appb-000040
Figure PCTCN2014092359-appb-000041
其中，*表示共轭运算符，angle()表示求角度运算符。
然后，通过两个导频序列的时间间隔Δt以及所述两个导频序列的相位差
Figure PCTCN2014092359-appb-000042
按照式4获取所述UE在接收天线kaRx的双导频频偏估计结果Δf1 (u)(kaRx)：
Figure PCTCN2014092359-appb-000043
接着，在初始频偏值
Figure PCTCN2014092359-appb-000044
限定的范围内，根据双导频频偏估计结果Δf2 (u)(kaRx)以及式5获取所述UE在接收天线kaRx的双导频频偏估计值ΔΔf2(kaRx)：
Figure PCTCN2014092359-appb-000045
其中，T为双导频频偏估计值的最大范围值；l为预设整数，用于将双导频频偏估计值限定在预定的范围内。
S104：根据所述第一频偏估计值对应的初始频偏值和所述双导频频偏估计值得到当前子帧的频偏估计值。
示例性地，在本实施例中，可以通过将所述初始频偏值
Figure PCTCN2014092359-appb-000046
与所述双导频频偏估计值ΔΔf2(kaRx)相加获取所述UE在接收天线kaRx的当前子帧的频偏估计值fu(kaRx)。
作为一种实施方式，在获取到所述UE在接收天线kaRx的当前子帧的频偏估计值fu(kaRx)之后，可以对fu(kaRx)通过滤波的方式进行平滑处理，得到平滑后的当前子帧的频偏估计值f(u)(kaRx)；
作为一种实施方式，本实施例中，可以通过所述UE在接收天线kaRx的前一子帧的频偏估计值
Figure PCTCN2014092359-appb-000047
与fu(kaRx)按照式6进行加权求和的方式来得到平滑后的当前子帧的频偏估计值f(u)(kaRx)：
Figure PCTCN2014092359-appb-000048
其中，p2是滤波因子，且0≤p2≤1。
上述方案为本发明实施例提供的一种频偏估计的方法，通过根据UE发送的SRS或Preamble码所确定的第一频偏估计值得到初始频偏值，并且在初始频偏值的范围内结合双导频频偏估计值获取当前子帧的频偏估计值，既保证频偏估计精度，而且还降低了对于大频偏估计的复杂度。
基于图1所示实施例相同的技术构思，参见图2，其示出了本发明实施例提供的一种频偏估计的装置20，该装置20可以包括：第一获取单元201、第二获取单元202、第三获取单元203和第四获取单元204，其中，
所述第一获取单元201，配置为通过接收UE发送的SRS或Preamble码进行初始信道估计，获取所述UE当前子帧的第一频偏估计值；
所述第二获取单元202，配置为确定所述第一频偏估计值所处的频率范围，并根据所述频率范围以及预设的所述频率范围与初始频偏值之间的对应关系，获取所述第一频偏估计值对应的初始频偏值；
所述第三获取单元203，配置为基于接收的所述UE当前子帧包含的两个导频序列计算两个导频位置的相位差，并在所述初始频偏值限定的范围内，根据所述相位差获取双导频频偏估计值；
所述第四获取单元204，配置为根据所述初始频偏值和所述双导频频偏估计值获取当前子帧的频偏估计值。
示例性地，所述第一获取单元201，配置为：
通过接收由UE发送的当前子帧的SRS或者当前子帧的Preamble码来获取所述UE的信道估计值Hu和接收数据Yu；
以及，根据所述UE的信道估计值Hu和接收数据Yu，并结合本地导频序列Pu和下式获取所述UE在接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)：
Figure PCTCN2014092359-appb-000049
其中，n表示采样点序号，u表示所述当前子帧对应的用户设备UE，k表示所述UE对应的子载波索引，
Figure PCTCN2014092359-appb-000050
kaRx表示接收天线索引，
Figure PCTCN2014092359-appb-000051
表示所述UE所占用的RB的大小，*表示共轭运算，IDFT表示傅里叶逆变换；
以及，根据所述UE在接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)的相位信息获取所述UE接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)。
作为一种实施方式，所述第一获取单元201，配置为：
将所述当前子帧的时域采样值wu(n,kaRx)的前半部分和后半部分的相位值分别进行平均后，获取前、后两个部分之间的相位差
Figure PCTCN2014092359-appb-000052
根据下式获取所述UE在接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)：
Figure PCTCN2014092359-appb-000053
作为一种实施方式，所述第一获取单元201，还配置为对所述UE在接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)进行平滑处理，得到平滑后的当前子帧的第一频偏估计值f1 (u)(kaRx)；具体地，所述第一获取单元201可以将当前子帧以前的子帧对应的第一频偏估计值与f0 u(kaRx)进行加权求和；可以理解的，时间上越接近当前子帧则权值越大；时间上越远离当前子帧则权值越小。
在本实施例中，所述第一获取单元201可以根据当前子帧的前一个子帧的对应的第一频偏估计值
Figure PCTCN2014092359-appb-000054
与f0 u(kaRx)按照下式进行加权求和来对f0 u(kaRx)进行平滑处理，得到平滑后的当前子帧的第一频偏估计值f1 (u)(kaRx)：
Figure PCTCN2014092359-appb-000055
其中，p1为滤波因子，且0≤p1≤1。
可以理解的，f1 (u)(kaRx)仅较f0 u(kaRx)更加的平滑，但是f0 u(kaRx)也同样可以用于后续模块进行处理，而将f1 (u)(kaRx)用于后续模块的处理仅是本实施例的一个更为优选的方案，所以，后续模块处理过程中所使用的第一频偏估计值既可以选择f0 u(kaRx)，也可以选择f1 (u)(kaRx)，本发明实施例对此不作具体的限定。
示例性地，预设的所述频率范围与初始频偏值之间的对应关系可以是一张具体的频率范围区间的上、下限与初始频偏值的映射表，如表1所示，
作为一种实施方式，由表1可知，第二获取单元202可以配置为将所述第一频偏估计值与表1中的各频率范围区间的上、下限进行比较，确定 第一频偏估计值所处的频率范围区间，然后还可以相应地获取到所述第一频偏估计值对应的初始频偏值。在本实施例中，与所述UE在接收天线kaRx的第一频偏估计值所对应的初始频偏值可以用
Figure PCTCN2014092359-appb-000056
表示。
示例性地，所述第三获取单元203，配置为：
根据所述UE在接收天线kaRx的当前子帧包含的两个导频序列所得到的两个导频信道估计值
Figure PCTCN2014092359-appb-000057
和
Figure PCTCN2014092359-appb-000058
按照下式获取所述UE在接收天线kaRx的两个导频位置的相位差
Figure PCTCN2014092359-appb-000059
Figure PCTCN2014092359-appb-000060
其中，*表示共轭运算符，angle()表示求角度运算符；
以及，通过所述两个导频序列的时间间隔Δt以及所述两个导频序列的相位差
Figure PCTCN2014092359-appb-000061
按照下式获取所述UE在接收天线kaRx的双导频频偏估计结果Δf2 (u)(kaRx)：
Figure PCTCN2014092359-appb-000062
以及，在所述初始频偏值限定的范围内，根据双导频频偏估计结果Δf2 (u)(kaRx)以及下式获取所述UE在接收天线kaRx的双导频频偏估计值ΔΔf2(kaRx)：
Figure PCTCN2014092359-appb-000063
其中，T为所述双导频频偏估计值的最大范围值；l为预设整数，用于将所述双导频频偏估计值限定在预定的范围内。
作为一种实施方式，在本实施例中，第四获取单元204可以通过将所述初始频偏值
Figure PCTCN2014092359-appb-000064
与所述双导频频偏估计值ΔΔf2(kaRx)相加获取所述UE接收天线kaRx的当前子帧的频偏估计值fu(kaRx)。
作为一种实施方式，在获取到所述UE接收天线kaRx的当前子帧的频偏 估计值fu(kaRx)之后，所述第四获取单元204，还配置为对当前子帧的频偏估计值fu(kaRx)通过滤波的方式进行平滑处理，得到平滑后的当前子帧的频偏估计值f(u)(kaRx)。
作为一种实施方式，本实施例中，第四获取单元204可以通过所述UE接收天线kaRx的前一子帧的频偏估计值
Figure PCTCN2014092359-appb-000065
与fu(kaRx)按照下式进行加权求和的方式来得到平滑后的当前子帧的频偏估计值f(u)(kaRx)：
Figure PCTCN2014092359-appb-000066
其中，p2是滤波因子，且0≤p2≤1。
本实施例提供了一种频偏估计的装置20，通过根据UE发送的SRS或Preamble码所确定的第一频偏估计值得到初始频偏值，并且在初始频偏值的范围内结合双导频频偏估计值获取当前子帧的频偏估计值，既保证频偏估计精度，而且还降低了对于大频偏估计的复杂度。
本发明实施例还记载了一种存储介质，所述存储介质中存储有计算机程序，所述计算机程序配置为执行前述各实施例的频偏估计的方法。
本领域内的技术人员应明白，本发明的实施例可提供为方法、系统、或计算机程序产品。因此，本发明可采用硬件实施例、软件实施例、或结合软件和硬件方面的实施例的形式。而且，本发明可采用在一个或多个其中包含有计算机可用程序代码的计算机可用存储介质(包括但不限于磁盘存储器和光学存储器等)上实施的计算机程序产品的形式。
本发明是参照根据本发明实施例的方法、设备(系统)、和计算机程序产品的流程图和/或方框图来描述的。应理解可由计算机程序指令实现流程图和/或方框图中的每一流程和/或方框、以及流程图和/或方框图中的流程和/或方框的结合。可提供这些计算机程序指令到通用计算机、专用计算机、嵌入式处理机或其他可编程数据处理设备的处理器以产生一个机器，使得通过计算机或其他可编程数据处理设备的处理器执行的指令产生用于实现 在流程图一个流程或多个流程和/或方框图一个方框或多个方框中指定的功能的装置。
这些计算机程序指令也可存储在能引导计算机或其他可编程数据处理设备以特定方式工作的计算机可读存储器中，使得存储在该计算机可读存储器中的指令产生包括指令装置的制造品，该指令装置实现在流程图一个流程或多个流程和/或方框图一个方框或多个方框中指定的功能。
这些计算机程序指令也可装载到计算机或其他可编程数据处理设备上，使得在计算机或其他可编程设备上执行一系列操作步骤以产生计算机实现的处理，从而在计算机或其他可编程设备上执行的指令提供用于实现在流程图一个流程或多个流程和/或方框图一个方框或多个方框中指定的功能的步骤。
以上所述，仅为本发明的较佳实施例而已，并非用于限定本发明的保护范围。
工业实用性
本发明通过根据UE发送的SRS或Preamble码所确定的第一频偏估计值得到初始频偏值，并且在初始频偏值的范围内结合双导频频偏估计值获取当前子帧的频偏估计值，既保证频偏估计精度，而且还降低了对于大频偏估计的复杂度。

Claims (13)

  1. 一种频偏估计的方法，包括：
    通过接收的探测参考信号SRS或Preamble码进行初始信道估计，获取当前子帧的第一频偏估计值；
    确定所述第一频偏估计值所处的频偏区间，并根据预设的频偏区间与初始频偏值之间的对应关系，获取所述第一频偏估计值对应的初始频偏值；
    基于接收的当前子帧包含的导频序列确定相邻导频位置的相位差，并在所述第一频偏估计值对应的初始频偏值限定的范围内，根据所述相位差获取双导频频偏估计值；
    根据所述第一频偏估计值对应的初始频偏值和所述双导频频偏估计值获取当前子帧的频偏估计值。
  2. 根据权利要求1所述的方法，其中，所述通过接收的SRS或Preamble码进行初始信道估计，获取当前子帧的第一频偏估计值，包括：
    通过接收当前子帧的SRS或者当前子帧的Preamble码来获取信道估计值Hu和接收数据Yu；
    根据所述信道估计值Hu和所述接收数据Yu，并结合本地导频序列Pu和下式获取接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)：
    wu(n,kaRx)＝IDFT(Yu(k,kaRx)×Hu*(k,kaRx))×(IDFT(Pu(k)))*
    其中，n表示采样点序号，u表示所述当前子帧对应的用户设备UE，k表示所述UE对应的子载波索引，
    Figure PCTCN2014092359-appb-100001
    kaRx表示接收天线索引，
    Figure PCTCN2014092359-appb-100002
    表示所述UE所占用的资源块RB的大小，*表示共轭运算，IDFT表示傅里叶逆变换；
    根据所述接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)的相位信息获取接收天线kaRx的当前子帧的第一频偏估计值
    Figure PCTCN2014092359-appb-100003
  3. 根据权利要求2所述的方法，其中，所述根据所述接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)的相位信息获取接收天线kaRx的当前子帧的第一频偏估计值
    Figure PCTCN2014092359-appb-100004
    包括：
    将所述当前子帧的时域采样值wu(n,kaRx)的前半部分和后半部分的相位值分别进行平均后，获取前、后两个部分之间的相位差
    Figure PCTCN2014092359-appb-100005
    根据下式获取所述接收天线kaRx的当前子帧的第一频偏估计值
    Figure PCTCN2014092359-appb-100006
    Figure PCTCN2014092359-appb-100007
  4. 根据权利要求2所述的方法，其中，所述方法还包括：
    对所述接收天线kaRx的当前子帧的第一频偏估计值
    Figure PCTCN2014092359-appb-100008
    进行平滑处理，得到平滑后的当前子帧的第一频偏估计值
    Figure PCTCN2014092359-appb-100009
  5. 根据权利要求1所述的方法，其中，所述基于接收的当前子帧包含的导频序列确定相邻导频位置的相位差，并在所述第一频偏估计值对应的初始频偏值限定的范围内，根据所述相位差获取双导频频偏估计值，包括：
    根据所述接收天线kaRx的当前子帧包含的两个导频序列所得到的两个导频信道估计值
    Figure PCTCN2014092359-appb-100010
    和
    Figure PCTCN2014092359-appb-100011
    并按照下式获取接收天线kaRx的两个导频位置的相位差
    Figure PCTCN2014092359-appb-100012
    Figure PCTCN2014092359-appb-100013
    其中，*表示共轭运算符，angle()表示求角度运算符；
    通过所述两个导频序列的时间间隔Δt以及所述两个导频序列的相位差
    Figure PCTCN2014092359-appb-100014
    按照下式获取接收天线kaRx的双导频频偏估计结果
    Figure PCTCN2014092359-appb-100015
    Figure PCTCN2014092359-appb-100016
    在所述初始频偏值
    Figure PCTCN2014092359-appb-100017
    限定的范围内，根据双导频频偏估计结 果
    Figure PCTCN2014092359-appb-100018
    以及下式获取所述接收天线kaRx的双导频频偏估计值ΔΔf2(kaRx)：
    Figure PCTCN2014092359-appb-100019
    其中，T为所述双导频频偏估计值的最大范围值；l为预设整数，用于将所述双导频频偏估计值限定在预定的范围内。
  6. 根据权利要求1所述的方法，其中，在根据所述第一频偏估计值对应的初始频偏值和所述双导频频偏估计值获取当前子帧的频偏估计值之后，所述方法还包括：
    对当前子帧的频偏估计值fu(kaRx)通过滤波的方式进行平滑处理，得到平滑后的当前子帧的频偏估计值f(u)(kaRx)。
  7. 一种频偏估计的装置，包括：第一获取单元、第二获取单元、第三获取单元和第四获取单元，其中，
    所述第一获取单元，配置为通过接收的探测参考信号SRS或Preamble码进行初始信道估计，获取当前子帧的第一频偏估计值；
    所述第二获取单元，配置为确定所述第一频偏估计值所处的频偏区间，并根据预设的频偏区间与初始频偏值之间的对应关系，获取所述第一频偏估计值对应的初始频偏值；
    所述第三获取单元，配置为基于接收的所述当前子帧包含的导频序列确定相邻导频位置的相位差，并在所述第一频偏估计值对应的初始频偏值限定的范围内，根据所述相位差获取双导频频偏估计值；
    所述第四获取单元，配置为根据所述第一频偏估计值对应的初始频偏值和所述双导频频偏估计值获取当前子帧的频偏估计值。
  8. 根据权利要求7所述的装置，其中，所述第一获取单元，配置为：
    通过接收当前子帧的SRS或者当前子帧的Preamble码来获取信道估计值Hu和接收数据Yu；
    以及，根据所述信道估计值Hu和所述接收数据Yu，并结合本地导频 序列Pu和下式获取接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)：
    wu(n,kaRx)＝IDFT(Yu(k,kaRx)×Hu*(k,kaRx))×(IDFT(Pu(k)))*
    其中，n表示采样点序号，u表示所述当前子帧对应的用户设备UE，k表示所述UE对应的子载波索引，
    Figure PCTCN2014092359-appb-100020
    kaRx表示接收天线索引，
    Figure PCTCN2014092359-appb-100021
    表示所述UE所占用的资源块RB的大小，*表示共轭运算，IDFT表示傅里叶逆变换；
    以及，根据所述接收天线kaRx的当前子帧的时域采样值wu(n,kaRx)的相位信息获取接收天线kaRx的当前子帧的第一频偏估计值f0 u(kaRx)。
  9. 根据权利要求8所述的装置，其中，所述第一获取单元，配置为：
    将所述当前子帧的时域采样值wu(n,kaRx)的前半部分和后半部分的相位值分别进行平均后，获取前、后两个部分之间的相位差
    Figure PCTCN2014092359-appb-100022
    根据下式获取所述接收天线kaRx的当前子帧的第一频偏估计值
    Figure PCTCN2014092359-appb-100023
    Figure PCTCN2014092359-appb-100024
  10. 根据权利要求8所述的装置，其中，所述第一获取单元，还配置为对所述接收天线kaRx的当前子帧的第一频偏估计值
    Figure PCTCN2014092359-appb-100025
    进行平滑处理，得到平滑后的当前子帧的第一频偏估计值f1 (u)(kaRx)。
  11. 根据权利要求7所述的装置，其中，所述第三获取单元，配置为：
    根据所述接收天线kaRx的当前子帧包含的两个导频序列所得到的两个导频信道估计值
    Figure PCTCN2014092359-appb-100026
    和
    Figure PCTCN2014092359-appb-100027
    并按照下式获取接收天线kaRx的两个导频位置的相位差
    Figure PCTCN2014092359-appb-100028
    Figure PCTCN2014092359-appb-100029
    其中，*表示共轭运算符，angle()表示求角度运算符；
    以及，通过所述两个导频序列的时间间隔Δt以及所述两个导频序列的相位差
    Figure PCTCN2014092359-appb-100030
    按照下式获取接收天线kaRx的双导频频偏估计结果
    Figure PCTCN2014092359-appb-100031
    Figure PCTCN2014092359-appb-100032
    以及，在所述初始频偏值
    Figure PCTCN2014092359-appb-100033
    限定的范围内，根据双导频频偏估计结果
    Figure PCTCN2014092359-appb-100034
    以及下式获取所述接收天线kaRx的双导频频偏估计值ΔΔf2(kaRx)：
    Figure PCTCN2014092359-appb-100035
    其中，T为所述双导频频偏估计值的最大范围值；l为预设整数，用于将所述双导频频偏估计值限定在预定的范围内。
  12. 根据权利要求7所述的装置，其中，所述第四获取单元，还配置为对当前子帧的频偏估计值fu(kaRx)通过滤波的方式进行平滑处理，得到平滑后的当前子帧的频偏估计值f(u)(kaRx)。
  13. 一种存储介质，所述存储介质中存储有计算机程序，所述计算机程序配置为执行权利要求1至6任一项所述的频偏估计的方法。
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