WO2015139474A1 - 一种校准射频收发机的系统、方法和计算机存储介质 - Google Patents

一种校准射频收发机的系统、方法和计算机存储介质 Download PDF

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Publication number
WO2015139474A1
WO2015139474A1 PCT/CN2014/092055 CN2014092055W WO2015139474A1 WO 2015139474 A1 WO2015139474 A1 WO 2015139474A1 CN 2014092055 W CN2014092055 W CN 2014092055W WO 2015139474 A1 WO2015139474 A1 WO 2015139474A1
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Prior art keywords
signal
transmit
compensated
radio frequency
parameter
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PCT/CN2014/092055
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English (en)
French (fr)
Inventor
王勇涛
谢豪律
王倬遥
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深圳市中兴微电子技术有限公司
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Priority to EP14886299.8A priority Critical patent/EP2966822B1/en
Priority to US14/778,865 priority patent/US9413473B2/en
Publication of WO2015139474A1 publication Critical patent/WO2015139474A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/10—Monitoring; Testing of transmitters
    • H04B17/11—Monitoring; Testing of transmitters for calibration
    • H04B17/14—Monitoring; Testing of transmitters for calibration of the whole transmission and reception path, e.g. self-test loop-back
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/50—Circuits using different frequencies for the two directions of communication
    • H04B1/52—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/50—Circuits using different frequencies for the two directions of communication
    • H04B1/52—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa
    • H04B1/525—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa with means for reducing leakage of transmitter signal into the receiver
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/06—Dc level restoring means; Bias distortion correction ; Decision circuits providing symbol by symbol detection
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/20—Arrangements for detecting or preventing errors in the information received using signal quality detector
    • H04L1/206—Arrangements for detecting or preventing errors in the information received using signal quality detector for modulated signals

Definitions

  • the present invention relates to the field of radio frequency calibration, and more particularly to a system, method and computer storage medium for calibrating a radio frequency transceiver.
  • radio frequency transceivers which are widely used in wireless communication systems, typically have two signal paths in the transmit channel and the receive channel: an I-in-phase path and a quadrature (Q, Quadrature) path.
  • the local oscillator (LO, Local Oscillator) in the RF transceiver cannot achieve the ideal amplitude and signal amplitude of the two paths and the phase and orthogonal path signals. Fully orthogonal, therefore, IQ mismatch occurs in the transmit channel and the receive channel; in addition, due to the DC offset of the transmit channel and the coupling effect of the integrated circuit, the RF transceiver is at the local oscillator frequency of the local oscillator. Carrier leakage occurs in the transmit channel.
  • embodiments of the present invention are directed to a system, method, and computer storage medium for calibrating a radio frequency transceiver capable of simultaneously correcting a carrier leakage phenomenon of a transmission channel and an IQ mismatch phenomenon of a transmission and reception channel.
  • a system for calibrating a radio frequency transceiver is provided in a radio frequency transceiver system, where the system includes: a transmit channel compensator, a receive channel compensator, an estimator, a memory, and a pan mixer, where
  • the memory is configured to save a compensation parameter
  • the transmit channel compensator is configured to receive the received in-phase baseband transmit signal I_tx and positive
  • the baseband transmit signal Q_tx is amplified and superimposed to obtain a compensated in-phase baseband transmit signal I_atx and a quadrature baseband transmit signal Q_atx; and the compensated in-phase baseband transmit signal I_atx and quadrature baseband transmit signal Q_atx are transmitted through the radio frequency transceiver system After the digital-to-analog converter and the transmission channel are processed, the output RF signal Tx_out is formed;
  • the panning mixer is configured to compensate the difference between the transmitted local oscillator frequency and the received local oscillator frequency for the received transmit radio frequency signal Tx_out, and then transmit the compensated Tx_out as the received radio frequency signal Rx_in to the radio frequency transceiver.
  • the receiving channel of the system respectively forms an in-phase baseband received signal I_rx receiving the I branch and an orthogonal baseband received signal Q_rx receiving the Q branch;
  • the receiving channel compensator is configured to amplify and superimpose the received in-phase baseband received signal I_rx and the quadrature baseband received signal Q_rx to obtain a compensated in-phase baseband received signal I_arx and a quadrature baseband received signal Q_arx;
  • the in-phase baseband received signal I_arx and the orthogonal baseband received signal Q_arx are transmitted to the estimator;
  • the estimator is configured to estimate a compensation parameter of the compensated in-phase baseband received signal I_arx and the orthogonal baseband received signal Q_arx, and update the compensation parameter of the memory with the estimated compensation parameter.
  • the transmit channel compensator is configured to obtain the first signal by the in-phase baseband transmit signal I_tx through the first amplifier, and obtain the second signal by using the orthogonal baseband transmit signal Q_tx through the second amplifier, and then the first The signal and the second signal are superimposed by the first adder to obtain a third signal; then the third signal is superimposed with the first DC compensation parameter DCi by using a second adder to obtain the compensated in-phase baseband transmission.
  • the quadrature baseband transmit signal Q_tx is obtained by the third amplifier to obtain a fourth signal
  • the in-phase baseband transmit signal I_tx is obtained by the fourth amplifier to obtain a fifth signal
  • the fourth signal and the fifth signal are superimposed by the third adder.
  • the translation mixer is configured to generate a compensation signal S tm by translating the mixing local oscillator; and then mixing the compensation signal S tm with the transmitting RF signal Tx_out by a mixer to obtain The signal is transmitted to the receiving channel of the radio frequency transceiver system as the received radio frequency signal Rx_in.
  • the receiving channel compensator is configured to obtain the seventh signal by the in-phase baseband received signal I_rx through the fifth amplifier, and obtain the eighth signal by the quadrature baseband received signal Q_rx through the sixth amplifier, and then the seventh signal The signal and the eighth signal are superimposed by using a fifth adder to obtain the compensated in-phase baseband received signal I_arx;
  • the quadrature baseband received signal Q_rx is obtained by the seventh amplifier to obtain a ninth signal
  • the in-phase baseband received signal I_rx is obtained by the eighth amplifier to obtain a tenth signal
  • the ninth signal and the tenth signal are superimposed by the sixth adder.
  • the compensated orthogonal baseband received signal Q_arx is obtained.
  • the estimator includes: a single-point discrete Fourier transform DFT calculation module and a compensation parameter calculation module; wherein
  • the single-point DFT calculation module is configured to receive the compensated in-phase baseband received signal I_arx and the compensated orthogonal baseband received signal Q_arx transmitted by the receive channel compensator;
  • an image signal generated by a mismatch of a transmission channel IQ of the radio frequency transceiver system an image signal generated by carrier leakage of the radio frequency transceiver system, and the image signal according to the compensated in-phase baseband received signal I_arx and the compensated quadrature baseband received signal Q_arx
  • the receiving channel IQ of the radio frequency transceiver system mismatches the power of the image signal generated by the image, and transmits the power of the three image signals to the compensation parameter calculation module;
  • the compensation parameter calculation module is configured to search for power of the three image signals by a binary search method, estimate a compensation parameter that minimizes power of the three image signals, and transmit the compensation parameters obtained after the estimation Up to the memory, the memory is caused to update the existing compensation parameter to a compensation parameter obtained by the compensation parameter calculation module.
  • the compensation parameter calculation module is further configured to pass the binary search method. Before estimating the power of the three image signals, an initial search interval corresponding to the power of the three image signals is determined.
  • a method for calibrating a radio frequency transceiver is provided in a system for calibrating a radio frequency transceiver, wherein the system for calibrating the radio frequency transceiver is applied to a radio frequency transceiver; the system for calibrating the radio frequency transceiver includes: transmitting Channel compensator, receive channel compensator, estimator, memory and translation mixer;
  • the method includes:
  • the transmit channel compensator receives an in-phase baseband transmit signal I_tx and a quadrature baseband transmit signal Q_tx generated by a single frequency signal generator of the radio frequency transceiver;
  • the transmit channel compensator compensates the in-phase baseband transmit signal I_tx and the orthogonal baseband transmit signal Q_tx by amplification and superposition to obtain a compensated in-phase baseband transmit signal I_atx and a compensated orthogonal baseband transmit signal Q_atx;
  • the compensated in-phase baseband transmit signal I_atx and the quadrature baseband transmit signal Q_atx are processed by the digital-to-analog converter and the transmit channel of the radio frequency transceiver to form a transmit RF signal Tx_out output;
  • the panning mixer compensates the received transmit radio frequency signal Tx_out with a difference between the transmit local oscillator frequency and the received local oscillator frequency; and transmits the compensated Tx_out as the received radio frequency signal Rx_in to the radio frequency transceiver system.
  • Receiving channels respectively forming an in-phase baseband receive signal I_rx receiving the I branch and a quadrature baseband receive signal Q_rx receiving the Q branch;
  • the receiving channel compensator amplifies and superimposes the received in-phase baseband received signal I_rx and the orthogonal baseband received signal Q_rx to obtain a compensated in-phase baseband received signal I_arx and a compensated orthogonal baseband received signal Q_arx; And transmitting the compensated in-phase baseband received signal I_arx and the compensated orthogonal baseband received signal Q_arx to an estimator;
  • the estimator estimates the compensated parameters of the compensated in-phase baseband received signal I_arx and the orthogonal baseband received signal Q_arx, and updates the compensation parameter of the memory with the estimated compensation parameter; the compensation parameter includes: transmitting related compensation parameters and Receive relevant compensation parameters.
  • the transmit channel compensator transmits the in-phase baseband transmit signal I_tx and the The orthogonal baseband transmit signal Q_tx is compensated by amplification and superposition, and the compensated in-phase baseband transmit signal I_atx and the compensated orthogonal baseband transmit signal Q_atx are obtained, including:
  • the transmit channel compensator superimposes the in-phase baseband transmit signal I_tx by a first predetermined multiple and then superimposes the second baseband transmit signal Q_tx amplified by a second predetermined multiple, and superimposes the superposed signal with the first DC
  • the compensation parameter DCi is superimposed to obtain the compensated in-phase baseband transmission signal
  • the transmit channel compensator superimposes the orthogonal baseband transmit signal Q_tx by a third predetermined multiple and then superimposes the second phase multiple of the in-phase baseband transmit signal I_tx, and superimposes the superimposed signal with the second DC offset
  • the parameter DCq is superimposed to obtain a compensated orthogonal baseband transmit signal
  • the translation mixer compensates the difference between the transmitted local oscillator frequency and the received local oscillator frequency for the received transmit RF signal Tx_out, including:
  • the translating mixer generates a compensation signal S tm having a frequency of f tm , where f tm is a difference between a transmitting local oscillator frequency and a receiving local oscillator frequency;
  • the translating mixer mixes the compensation signal S tm with the transmitted radio frequency signal Tx_out.
  • the receiving channel compensator amplifies and superimposes the received in-phase baseband received signal I_rx and the orthogonal baseband received signal Q_rx to obtain a compensated in-phase baseband received signal and compensated orthogonal baseband receive.
  • Signals including:
  • the receiving channel compensator superimposes the in-phase baseband received signal I_rx by a fourth predetermined multiple and is superimposed with the quadrature baseband received signal Q_rx amplified by a fifth predetermined multiple to obtain a compensated in-phase baseband received signal I_arx;
  • the receiving channel compensator superimposes the quadrature baseband received signal Q_rx by a sixth predetermined multiple and then superimposes the in-phase baseband received signal I_rx amplified by a fifth predetermined multiple to obtain a compensated orthogonal baseband received signal Q_arx.
  • the estimator estimates the compensation parameters of the compensated in-phase baseband received signal I_arx and the orthogonal baseband received signal Q_arx, including:
  • the estimator receives the compensated in-phase baseband received signal I_arx and the compensated orthogonal baseband received signal Q_arx transmitted by the receive channel compensator;
  • the estimator searches the power of the three image signals by a binary search method to estimate a compensation parameter that minimizes the power of the three image signals.
  • the estimator obtains an image signal generated by the transmitter channel IQ mismatch of the radio frequency transceiver system according to the compensated in-phase baseband received signal I_arx and the compensated orthogonal baseband received signal Q_arx,
  • the power of the image signal generated by the carrier leakage of the RF transceiver system and the image signal generated by the receiving channel IQ mismatch of the RF transceiver system includes:
  • the estimator performs a single-point DFT calculation on the complex signal of the baseband received signal obtained according to the compensated in-phase baseband received signal I_arx and the compensated orthogonal baseband received signal Q_arx, respectively obtained by the transmit channel IQ mismatch , carrier leakage and the frequency of the image signal generated by the receiving channel IQ mismatch f tximage , f cl and f rximage ;
  • the estimator multiplies the complex signals of the baseband received signals by with 3 sequences, and reduce the influence of other signals on the respective powers through a low-pass filter, and the filtered signals are I tximage +jQ tximage , I cl +jQ cl and I rximage +jQ rximage , where f s An analog-to-digital converter for receiving the I branch of the radio frequency transceiver system and an analog-to-digital converter sampling frequency of the receiving Q branch of the radio frequency transceiver system, where N is a sequence length;
  • the estimator searches the power of the three image signals by a binary search method, and estimates compensation parameters that minimize the power of the three image signals, including:
  • the estimator uses the first transmit channel compensation parameter g 1 and the second transmit channel compensation parameter ⁇ 1 of the transmission-related compensation parameters as a first parameter group, and the image signal generated by the mismatch with the transmit channel IQ Corresponding to: a first receiving channel compensation parameter g 2 and a second receiving channel compensation parameter ⁇ 2 of the receiving related compensation parameters as a second parameter group, and an image signal generated by mismatching with the receiving channel IQ Corresponding to the power; the first DC compensation parameter DCi and the second DC compensation parameter DCq of the transmission-related compensation parameters are used as a third parameter group, corresponding to the power of the image signal generated by the carrier leakage;
  • the estimator calculates the first parameter group, the second parameter group, and the third parameter group, respectively, including:
  • Step 1A The estimator selects any parameter group of the first parameter group, the second parameter group, and the third parameter group, and a two-dimensional search interval corresponding to any one of the parameter groups;
  • Step 2A The estimator divides each dimension interval of the search interval into four sub-intervals equally, so that a total of five endpoints of four sub-intervals of each dimension interval can be obtained;
  • Step 3A The estimator performs the calculation of the power of the image signal corresponding to the parameter group of the parameter group by substituting the five endpoints of the each dimension interval, and acquiring any parameter group in the each dimension interval. The lowest power end of the corresponding image signal;
  • Step 4A The estimator sets an endpoint that minimizes the power of the image signal corresponding to any one of the parameter groups in each dimension interval as a midpoint, and uses two endpoints of the midpoint as a boundary point. , thereby obtaining a new search interval;
  • Step 5A The estimator takes, as the any parameter group, an endpoint that minimizes the power of the image signal corresponding to any one of the parameter groups in each dimension interval, so that the single-point DFT meter
  • the calculation module calculates the power of the image signal corresponding to the new one of the parameter groups
  • Step 6A Step 2A is repeatedly performed in the new search interval of the estimator until a preset number of times is performed, thereby obtaining any one of the parameter groups that minimizes the power of the image signal corresponding to any one of the parameter groups.
  • the method further includes: the estimator determining the first An initial search interval corresponding to the parameter group, the second parameter group, and the third parameter group respectively;
  • the estimator determines the first parameter group, the second parameter group, and the third parameter group by performing a process of steps 1A to 6A three to five times or by a particle filtering algorithm or a sequence importance sampling SIS method. Corresponding initial search intervals.
  • An embodiment of the present invention further provides a computer storage medium, the storage medium comprising a set of computer executable instructions for performing a method of calibrating a radio frequency transceiver according to an embodiment of the present invention.
  • Embodiments of the present invention provide a system, method, and computer storage medium for calibrating a radio frequency transceiver, and performing parameter search on an image signal caused by an IQ mismatch of a transmitting channel and a receiving channel and a carrier leakage of a transmitting channel in a baseband received signal.
  • a radio frequency transceiver performing parameter search on an image signal caused by an IQ mismatch of a transmitting channel and a receiving channel and a carrier leakage of a transmitting channel in a baseband received signal.
  • FIG. 1 is a schematic structural diagram of a commonly used radio frequency transceiver system
  • FIG. 2 is a schematic structural diagram of a system for calibrating a radio frequency transceiver according to an embodiment of the present invention
  • 3a is a schematic diagram of a circuit implementation of a transmit channel compensator according to an embodiment of the present invention.
  • FIG. 3b is a schematic diagram of a circuit implementation of a pan mixer according to an embodiment of the present invention.
  • 3c is a schematic diagram of a circuit implementation of a receiving channel compensator according to an embodiment of the present invention.
  • FIG. 4 is a schematic structural diagram of an estimator according to an embodiment of the present invention.
  • FIG. 5 is a schematic diagram of amplitude-frequency characteristics of a complex signal of a baseband received signal according to an embodiment of the present invention
  • FIG. 6 is a schematic diagram of a process for calculating a parameter group according to an embodiment of the present invention.
  • the system for calibrating the radio frequency transceiver provided by the embodiment of the present invention can be applied to the commonly used radio frequency transceiver system, thereby enabling the present invention.
  • the specific technical solutions of the embodiments are explained in detail.
  • FIG. 1 shows a commonly used radio frequency transceiver system 10 for IQ modulation and demodulation of various wireless communication systems.
  • the radio frequency transceiver system 10 may include a transmitting channel 101 and a receiving channel 102.
  • a transmitting channel 101 is above the dotted line, and a receiving channel 102 is below the dotted line.
  • the transmitting channel 101 can generate two baseband signals I_tx and Q_tx whose frequencies are f sig and whose phases are mutually orthogonal, by the single frequency signal generator 1011, Can be called the in-phase baseband transmit signal, Can be called orthogonal baseband transmit signal, Is the phase of the baseband signal; then transmitting the in-phase baseband transmit signal to the transmit co-directional I branch 101a, and transmitting the orthogonal baseband transmit signal to the transmit orthogonal Q branch 101b;
  • the in-phase baseband transmit signal is first converted from a digital signal to an analog signal by a digital to analog converter (DAC) 1012a and a low pass filter (LF, Lowpass Filter) 1013a; After passing through the digital-to-analog converter 1012a and the low-pass filter 1013a, the in-phase baseband transmit signal only changes its own representation type, and the in-phase baseband transmit signal expression remains Accordingly, in the transmit Q branch 101b, the orthogonal baseband transmit signal is also converted from the digital signal to the analog signal by the digital to analog converter 1012b and the low pass filter 1013b; it is understood that the digital to analog converter 1012b and low are After the pass filter 1013b, the orthogonal baseband transmit signal only changes its own representation type, and the orthogonal baseband transmit signal expression remains
  • the transmitting local oscillator 1014 can generate the local oscillator signal generated by itself.
  • the transmitting local oscillator signal can be transmitted through the phase shifter 1015 to obtain a phase 0° signal to obtain a transmitting in-phase local oscillator signal.
  • the mixer 1016a performs upmixing of the LOI_tx0 and the I_tx to obtain an in-phase mixed transmit signal of the I branch, where f txlo is the local oscillator frequency of the local oscillator 1014.
  • the transmitted local oscillator signal is shifted by 90° through the phase shifter 1015 to obtain a transmitted orthogonal local oscillator signal.
  • the mixer 1016b upmixes the LOQ_tx0 and the Q_tx to obtain an orthogonal mix of the Q branches.
  • Frequency-transmitted signal similarly, f txlo is the local oscillator frequency of the local oscillator 1014.
  • the transmitter local oscillator mismatch occurs when the local oscillator is transmitted.
  • the in-phase local oscillator signal mixed with the in-phase baseband transmit signal is The transmitting local oscillator signal generated by the transmitting local oscillator 1014 is shifted by the phase shifter 1015.
  • the in-phase local oscillator signal mixed with the in-phase baseband transmit signal is:
  • the transmitted orthogonal local oscillator signal mixed with the orthogonal baseband transmit signal is the transmit local oscillator signal generated by the transmit local oscillator 1014, and the phase is shifted by the phase shifter 1015.
  • the orthogonal to local oscillator signal that is mixed with the orthogonal baseband transmit signal is:
  • the in-phase mixing signal and the quadrature mixing signal may be superimposed by the adder 1018, and then the superimposed mixing signal is transmitted to the external space as the transmitting RF signal Tx_out through the transmitting antenna 1019. ;
  • the RF transceiver has a carrier leakage phenomenon in the transmitting channel 101 at the local oscillator frequency of the local oscillator. Therefore, in an ideal state, The superimposed mixing signal also needs to be superimposed with the leaked transmitting carrier Acos (2 ⁇ f lo t+ ⁇ cl ) simulated by the carrier leakage simulator 10110 through the adder 10111 to obtain the transmitted radio frequency signal Tx_out under actual conditions.
  • the transmitting radio frequency signal Tx_out can also be transmitted to the receiving channel 102 as the receiving radio frequency signal Rx_in through the radio frequency loop 103.
  • the receiving channel 102 can separate the received radio frequency signal Rx_in into an in-phase radio frequency receiving signal I_rxin and a quadrature radio frequency receiving signal Q_rxin having the same frequency and mutually orthogonal phases; and transmitting the in-phase radio frequency receiving signal I_rxin to the receiving co-directional I branch 102a, the orthogonal radio frequency received signal Q_rxin is transmitted to the receiving orthogonal Q branch 102b;
  • the receiving local oscillator 1021 can generate the local oscillator signal generated by itself.
  • the receiving local oscillator signal can be phase-shifted by phase shifter 1022 to obtain a received in-phase local oscillator signal.
  • the LOI_rx0 is mixed with the in-phase radio frequency receiving signal I_rxin transmitted from the receiving I branch 102a.
  • the mixer 1023a downmixes the LOI_rx0 and the I_rxin to obtain the in-phase baseband receiving signal I_rx of the receiving I branch 102a, wherein , f rxlo is the local oscillator frequency of receiving the local oscillator 1021.
  • the received local oscillator signal can be phase-shifted by the phase shifter 1022 to obtain a received quadrature local oscillator signal.
  • the LOQ_rx0 is mixed with the orthogonal radio frequency receiving signal Q_rxin transmitted from the receiving Q branch 102b.
  • the mixer 1023b downmixes the LOQ_rx0 and the Q_rxin to obtain the quadrature baseband receiving signal Q_rx of the receiving Q branch.
  • f rxlo local oscillation frequency of the reception local oscillator 1021 To receive the local oscillator phase of the local oscillator 1021.
  • the receive local oscillator may also have a receive channel IQ mismatch.
  • the in-phase local oscillator signal is mixed with the in-phase RF receive signal I_rxin.
  • the received local oscillator signal generated by the receiving local oscillator 1021 is shifted by the phase shifter 1022.
  • the received in-phase local oscillator signal mixed with the signal I_rxin is:
  • the received quadrature local oscillator signal mixed with the received quadrature radio frequency signal Q_rxin is moved by the phase oscillator 1022 by the receiving local oscillator signal generated by the receiving local oscillator 1021.
  • zoom in through amplifier 1024b Doubled therefore, in practical applications, the received quadrature local oscillator signal mixed with the signal Q_rxin is:
  • the in-phase baseband received signal I_rx obtained by mixing is sequentially passed through the low pass filter 1025a, the variable gain amplifier 1026a, and the analog to digital converter (ADC) 1027a.
  • the in-phase baseband in the form of a digital signal receives the signal I_rx.
  • the in-phase baseband received signal I_rx in the form of a digital signal and the in-phase baseband received signal I_rx obtained by mixing are only different in representation type, and the expression of the signal is still the same; correspondingly, in the receiving Q branch 102b, Mixed quadrature baseband received signal Q_rx After passing through the low pass filter 1025b, the variable gain amplifier 1026b, and the ADC 1027b in sequence, a quadrature baseband received signal Q_rx in the form of a digital signal can be obtained.
  • the obtained quadrature baseband received signal Q_rx is also only the representation type difference, and the expression of the signal is still the same; it can be understood that the I_rx in the form of a digital signal and the Q_rx in the form of a digital signal are the received baseband signals.
  • the IQ mismatch of the transmit channel, the carrier leakage, and the IQ mismatch of the receive channel will respectively cause the in-phase baseband receive signal I_rx and the quadrature baseband receive signal Q_rx to be additionally included by the transmit.
  • the interference can be reduced by means of compensation, for example, after the single-frequency signal generator 1011 of the transmission channel 101 generates the in-phase baseband transmission signal and the orthogonal baseband transmission signal, the in-phase baseband transmission signal and the orthogonality
  • the baseband transmit signal separately compensates for the transmit IQ mismatch and the carrier leakage; correspondingly, in the receive channel 102, the I_rx in the form of the digital signal obtained by the ADC 1027a and the ADC 1027b and the Q_rx in the form of the digital signal are respectively subjected to the receive IQ mismatch. make up.
  • FIG. 2 a system for calibrating a radio frequency transceiver is proposed. 20, can be applied to the radio frequency transceiver system 10 shown in FIG. 1 .
  • the radio frequency transceiver system shown in FIG. 1 is only used to describe the technical solution of the embodiment of the present invention in detail, and is not limited to FIG. 1 .
  • the system 20 is applied to the radio frequency transceiver system shown in FIG. 1, and in combination with the foregoing description of the radio frequency transceiver system shown in FIG. 1, it can be understood that FIG. 2 retains the radio frequency.
  • Portions and devices of the transceiver system 10 associated with the system 20, the other portions are identical to the RF transceiver system 10 shown in FIG. 1, and are therefore replaced with ellipses in FIG.
  • the system 20 can include: a transmit channel compensator 201, a receive channel compensator 203, an estimator 204, a memory 205, and a translating mixer 202;
  • the memory 205 is configured to save the compensation parameter
  • the saved compensation parameters include a transmission-related compensation parameter and a reception-related compensation parameter, which are respectively provided to the transmission channel compensator 201 and the reception channel compensator 203 to complete signal compensation;
  • the transmission related compensation parameters include: a first transmit channel compensation parameter g 1 , a second transmit channel compensation parameter ⁇ 1 , a first DC compensation parameter DCi, and a second DC compensation parameter DCq;
  • the receiving related compensation parameters include: a first receiving channel compensation parameter g 2 and a second receiving channel compensation parameter ⁇ 2 .
  • the transmit channel compensator 201 is configured to receive the in-phase baseband transmit signal I_tx and the quadrature baseband transmit signal Q_tx, and the in-phase baseband transmit signal I_tx and the quadrature baseband transmit signal Q_tx are amplified and superimposed to obtain a compensated in-phase baseband transmit signal I_atx and compensated
  • the subsequent orthogonal baseband transmits a signal Q_atx, and transmits the compensated in-phase baseband transmit signal I_atx to the digital-to-analog converter 1012a of the transmit I branch 101a, and the compensated orthogonal baseband transmit signal Q_atx is transmitted to the transmit Q branch 101b.
  • the digital-to-analog converter 1012b so that the transmitting channel 101 of the radio frequency transceiver system 10 can obtain the transmitting radio frequency signal Tx_out according to the compensated in-phase baseband transmit signal I_atx and the compensated quadrature baseband transmit signal Q_atx;
  • the in-phase baseband transmit signal I_tx and the quadrature baseband transmit signal Q_tx received by the transmit channel compensator 201 are generated by the single-frequency signal generator 1011 in the radio frequency transceiver system 10;
  • the transmit channel compensator 201 superimposes the in-phase baseband transmit signal I_tx (1-g 1 ) times and then superimposes the orthogonal baseband transmit signal Q_tx that is amplified by ⁇ 1 times, and superimposes the superposed signal with the first DC compensation.
  • the parameter DCi is superimposed so that the compensated in-phase baseband transmit signal can be obtained
  • the transmit channel compensator 201 superimposes the orthogonal baseband transmit signal Q_tx by (1+g 1 ) times and then superimposes the in-phase baseband transmit signal I_tx amplified by ⁇ 1 times, and performs the superimposed signal and the second DC compensation parameter DCq. Superimposed, so that the compensated orthogonal baseband transmit signal can be obtained
  • circuit implementation of the transmit channel compensator 201 can be as shown in Figure 3a:
  • the quadrature baseband transmit signal Q_tx is superimposed by a third adder of the fourth signal of the (1+g 1 ) third amplifier and the fifth signal of the fourth amplifier that passes the in-phase baseband transmit signal I_tx by ⁇ 1 times. a sixth signal; and using a fourth adder to superimpose the sixth signal and the second DC compensation parameter DCq, thereby obtaining a compensated orthogonal baseband transmission signal
  • the translational mixer (TM) is configured to compensate the received radio frequency signal Tx_out transmitted by the radio frequency transceiver system 10 to compensate the difference between the transmitting local oscillator frequency and the receiving local oscillator frequency, and the compensated transmitting radio frequency.
  • the signal Tx_out is transmitted as the received radio frequency signal Rx_in to the receiving channel 102 of the radio frequency transceiver system 10, so that the radio frequency transceiver system 10 receives the shot according to the radio frequency receiving system 10
  • the frequency signal Rx_in obtains the in-phase baseband received signal I_rx of the receiving I branch 102a of the radio frequency transceiver system 10 and the orthogonal baseband received signal Q_rx of the receiving Q branch 102b of the radio frequency transceiver system 10;
  • the signal obtained by mixing the signal Tx_out is transmitted as the received radio frequency signal Rx_in to the receiving channel 102 of the radio frequency transceiver system 10; wherein f tm is the difference between the transmitting local oscillator frequency and the receiving local oscillator frequency, and ⁇ tm is the compensation signal.
  • the signal Rx_in is transmitted to the receiving channel 102;
  • the receive channel compensator 203 is configured to receive the in-phase baseband receive signal I_rx and the quadrature baseband receive signal Q_rx transmitted by the receive I branch 102a of the radio frequency transceiver system 10 and the receive Q branch 102b of the radio frequency transceiver system 10;
  • the in-phase baseband received signal I_rx and the orthogonal baseband received signal Q_rx are amplified and superimposed to obtain a compensated in-phase baseband received signal I_arx and a quadrature baseband received signal Q_arx, and the compensated in-phase baseband received signal I_arx and the compensated positive
  • the baseband received signal Q_arx is transmitted to the estimator 204;
  • the receiving channel compensator 203 superimposes the in-phase baseband received signal I_rx (1-g 2 ) times and then the quadrature baseband received signal Q_rx which is amplified by ⁇ 2 times, thereby obtaining the compensated in-phase baseband received signal I_arx;
  • the receiving channel compensator 203 superimposes the orthogonal baseband received signal Q_rx by (1+g 2 ) times and then superimposes the in-phase baseband received signal I_rx amplified by ⁇ 2 times, thereby obtaining the compensated orthogonal baseband received signal Q_arx;
  • circuit implementation of receive channel compensator 203 can be as shown in Figure 3c:
  • the quadrature baseband received signal Q_rx is superimposed by a ninth signal of the (1+g 2 ) times seventh amplifier and a tenth signal of the eighth amplifier that passes the in-phase baseband received signal I_rx by ⁇ 2 times by using a sixth adder, thereby The compensated quadrature baseband received signal Q_arx is obtained.
  • the multiple of the above amplifiers may be preset by the transmit channel compensator 201 and the receive channel compensator 203 in the amplifier after receiving the corresponding transmit related compensation parameters from the memory 205 and receiving the associated compensation parameters.
  • the estimator 204 is configured to estimate the compensation parameter according to the compensated in-phase baseband received signal I_arx and the compensated orthogonal baseband received signal Q_arx, and transmit the estimated compensation parameter to the a memory such that the memory replaces the existing compensation parameter with the estimated compensation parameter.
  • the estimator 204 may include a single point discrete Fourier transform (DFT) calculation module 2041 and a compensation parameter calculation module 2042; as shown in FIG.
  • DFT discrete Fourier transform
  • the single-point DFT calculation module 2041 is configured to receive the compensated in-phase baseband received signal I_arx and the compensated orthogonal baseband received signal Q_arx transmitted by the receive channel compensator 203;
  • f tximage f txlo -f sig -f rxlo +f tm
  • f cl f txlo -f rxlo +f tm
  • f rximage -(f txlo +f sig -f rxlo +f tm )
  • f sig is The frequency of the in-phase baseband transmit signal and the quadrature baseband transmit signal generated by the single-frequency signal generator of the radio frequency transceiver system
  • f txlo is the local oscillator frequency of the local oscillator of the radio frequency transceiver system
  • f rxlo is the radio frequency
  • f tm is a frequency at which the translation mixing local oscillator generates a compensation signal
  • the translation mixer 202 transmits the signal obtained by mixing the compensation signal S tm having the frequency f tm and the transmission radio frequency signal Tx_out to the receiving channel 102 as the received radio frequency signal Rx_in.
  • the complex signals of the baseband received signals can be multiplied by with Three sequences, and through the low-pass filter, reduce the influence of other signals on their respective powers, so that the filtered signals are I tximage +jQ tximage , I cl +jQ cl and I rximage +jQ rximage ;
  • f Sampling the frequency for analog to digital converter 1027a and analog to digital converter 1027b, N is the sequence length;
  • the power of the image signal generated by the transmit channel IQ mismatch of the radio frequency transceiver system 10 is obtained by calculating
  • , and the radio frequency transceiver system 10 is obtained by calculating
  • the power of the image signal generated by the carrier leakage is obtained by calculating
  • the compensation parameter calculation module 2042 is configured to estimate a compensation parameter that minimizes the power of the three image signals according to the power of the three image signals and a new binary search method proposed by the embodiment of the present invention; and the estimated compensation parameter Transfer to the memory 205, so that the memory 205 updates the existing compensation parameters to the estimated compensation parameters transmitted by the compensation parameter calculation module 2042;
  • the first transmitting channel compensation parameter g 1 and the second transmitting channel compensation parameter ⁇ 1 , the first receiving channel compensation parameter g 2 and the second receiving channel compensation parameter ⁇ 2 , and the first DC compensation The parameter DCi and the second DC compensation parameter DCq are independent of each other; therefore, the three sets of parameters can be calculated in parallel to shorten the calculation time of the compensation parameter;
  • the new binary search method proposed by the embodiment of the present invention can be performed on the three sets of parameters in parallel.
  • the first transmission channel compensation parameter g 1 and the second transmission channel compensation parameter ⁇ 1 may be used as the first parameter group, and the The power of the image signal generated by the transmission channel IQ mismatch corresponds to; the first receiving channel compensation parameter g 2 and the second receiving channel compensation parameter ⁇ 2 are used as the second parameter group, and the image signal generated by the mismatch with the receiving channel IQ
  • the first DC compensation parameter DCi and the second DC compensation parameter DCq are used as the third parameter group, corresponding to the power of the image signal generated by the carrier leakage; specifically, the new binary search method proposed by the embodiment of the present invention
  • the calculation process of the three parameter groups is similar, and the embodiment of the present invention takes one parameter group from the above three parameter groups
  • S601 Select a search interval corresponding to any selected parameter group
  • the initial search interval corresponding to the first parameter group may be a two-dimensional interval. Therefore, the first transmission channel compensation parameter g 1 may be Set to the first dimension parameter; correspondingly, set the second transmit channel compensation parameter ⁇ 1 to the second dimension parameter; it can be understood that the first dimension parameter may also be the second transmit channel compensation parameter ⁇ 1 and corresponding to the second
  • the dimension parameter is the first transmission channel compensation parameter g 1 , which is not limited in this embodiment of the present invention
  • S602 Averagely divide each dimension interval of the search interval into four sub-intervals, so that a total of five endpoints of four sub-intervals of each dimension interval can be obtained. It can be understood that five endpoints of each dimension interval are Arranged in order of size;
  • the five endpoints of each dimension interval can be substituted into the corresponding
  • S604 Set, in each dimension interval, an endpoint that minimizes the power of the image signal corresponding to any one of the parameter groups as a midpoint, and use the two endpoints of the midpoint as a boundary point, thereby obtaining a new search interval. ;
  • in each dimension interval may be set as a midpoint, and the two endpoints of the midpoint are used as boundary points, thereby obtaining New search interval;
  • S605 use, as the any parameter group, an endpoint that minimizes the power of the image signal corresponding to any one of the parameter groups in each dimension interval, so that the single-point DFT calculation module calculates a new one.
  • in each dimension interval can be used as the first transmit channel compensation parameter g 1 and the second transmit channel compensation parameter ⁇ 1 , and the memory
  • the corresponding compensation parameters saved in 205 are updated, such that system 20 calculates a new
  • Step S602 is repeatedly performed in the new search interval until a preset number of times is performed, thereby obtaining any one of the parameter groups that minimizes the power of the image signal corresponding to any one of the parameter groups.
  • step S602 may be repeatedly performed in the new search interval until a preset number of times is performed, thereby obtaining a first transmit channel compensation parameter g 1 that minimizes
  • steps S601 to S606 can also be applied in the process of estimating the second parameter group and the third parameter group, which is similar to the first parameter group, but only changes the corresponding parameter group and the corresponding image signal power. It can be realized, and will not be described in detail.
  • the global optimum value of the first transmit channel compensation parameter g 1 and the second transmit channel compensation parameter ⁇ 1 can be obtained after performing step S601 to step S606;
  • the obtained error of the first transmit channel compensation parameter g 1 and the second transmit channel compensation parameter ⁇ 1 is not greater than L/2 N+1 , where L represents the length of the initial search interval, and N represents the preset number of executions;
  • the time is equal to T ⁇ (2N + 1), where T represents the calculation time of a single point;
  • the distance ⁇ 1 between the first transmit channel compensation parameter g 1 and the second transmit channel compensation parameter ⁇ 1 can only be obtained within the search interval.
  • the parameters g 1 and ⁇ 1 is a constant between the correlation, based on this correlation, the initial search point when any of the parameters g 1 and ⁇ 1 is a parameter most far away from the own advantages, the search for another parameter obtained results It will also be far from the most advantageous of the other parameter itself, resulting in an excessively large error in the search result, and finally only the local optimum value;
  • the process of determining the initial search interval corresponding to the first parameter group may also be included, and the process may also be regarded as a process of roughly calculating the parameters g 1 and ⁇ 1 to make a rough
  • the estimated range of parameters g 1 and ⁇ 1 can contain ⁇ 1 and Moreover, the range of this rough estimation can be taken as the initially selected search interval of steps S601 to S606.
  • the process of determining the initial search interval corresponding to the first parameter group may be performed three to five times from the steps S601 to S606, or may be obtained by other estimation algorithm processes applied to the discrete values to obtain ⁇ 1 and
  • the high probability interval is used as the initial search interval corresponding to the first parameter group, such as a particle filter algorithm and a Sequence Importance Sampling (SIS) method.
  • SIS Sequence Importance Sampling
  • the process of determining the initial search interval corresponding to the second parameter group and the third parameter group before step S601 may also be included, and the process may also be regarded as a parameter.
  • the second parameter group and the third parameter group perform a rough calculation process, so that the range of the second parameter group and the third parameter group obtained by the rough estimation can respectively include ⁇ 2 and And the carrier leakage signal, and this rough estimated range can be used as the initial selected search interval for steps S601 to S606 for the second parameter group and the third parameter group, respectively.
  • the process of determining the initial search interval corresponding to the second parameter group and the third parameter group may also be a process of performing steps S601 to S606 three to five times, or may be performed by other estimation algorithm processes applied to discrete values, such as particle filtering. Algorithm and SIS method.
  • the system 20 can directly obtain the three parameter sets according to the power of the three image signals by the estimator 204.
  • the calculation process of the first parameter group, the second parameter group, and the third parameter group can be processed in parallel, and the space is replaced by time to save the compensation.
  • the estimated time of the parameter thus, after N iterations, the first transmit channel compensation parameter g 1 and the second transmit channel compensation parameter ⁇ 1 , the first receive channel compensation parameter g 2 and the second receive channel compensation parameter ⁇ can be directly derived. 2.
  • Embodiments of the present invention provide a system for calibrating a radio frequency transceiver and a method for calibrating the radio frequency transceiver by the system, which are caused by an IQ mismatch of a transmitting channel and a receiving channel and a carrier leakage of a transmitting channel in a baseband received signal.
  • the image signal is searched for parameters to obtain corresponding compensation parameters, thereby eliminating the IQ mismatch of the transmitting channel and the receiving channel and the carrier leakage of the transmitting channel, correcting the carrier leakage phenomenon of the transmitting channel and the IQ mismatch of the transmitting channel and the receiving channel. phenomenon.
  • An embodiment of the present invention further provides a computer storage medium, the storage medium comprising a set of computer executable instructions for performing a method of calibrating a radio frequency transceiver according to an embodiment of the present invention.
  • embodiments of the present invention can be provided as a method, system, Or a computer program product. Accordingly, the present invention can take the form of a hardware embodiment, a software embodiment, or a combination of software and hardware. Moreover, the invention can take the form of a computer program product embodied on one or more computer-usable storage media (including but not limited to disk storage and optical storage, etc.) including computer usable program code.
  • the computer program instructions can also be stored in a computer readable memory that can direct a computer or other programmable data processing device to operate in a particular manner, such that the instructions stored in the computer readable memory produce an article of manufacture comprising the instruction device.
  • the apparatus implements the functions specified in one or more blocks of a flow or a flow and/or block diagram of the flowchart.
  • These computer program instructions can also be loaded onto a computer or other programmable data processing device such that a series of operational steps are performed on a computer or other programmable device to produce computer-implemented processing for execution on a computer or other programmable device.
  • the instructions provide steps for implementing the functions specified in one or more of the flow or in a block or blocks of a flow diagram.

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Abstract

本发明实施例公开了一种校准射频收发机的系统、方法和计算机存储介质，该系统可以包括：发射通道补偿器，接收通道补偿器，估计器、存储器和平移混频器。

Description

一种校准射频收发机的系统、方法和计算机存储介质 技术领域
本发明涉及射频校准领域，尤其涉及一种校准射频收发机的系统、方法和计算机存储介质。
背景技术
目前，被广泛应用于无线通信系统的射频收发机通常在发射通道以及接收通道都分别具有两条信号路径：同向(I，In-phase)路径和正交(Q，Quadrature)路径。而由于制造成本、工艺及功耗等原因，射频收发机中的本地振荡器(LO，Local Oscillator)无法做到理想的实现幅度与两条路径的信号幅度相等、以及相位与正交路径的信号完全正交，因此，在发射通道以及接收通道会发生IQ失配现象；另外，由于发射通道的直流失调及集成电路的耦合效应等原因，在本地振荡器的本振频率上，射频收发机会在发射通道发生载波泄漏现象。
发明内容
有鉴于此，本发明实施例期望提供一种校准射频收发机的系统、方法和计算机存储介质，能够同时校正发射通道的载波泄漏现象、以及发射和接收通道的IQ失配现象。
为达到上述目的，本发明实施例的技术方案是这样实现的：
本发明实施例提供的一种校准射频收发机的系统，应用于射频收发系统，所述系统包括：发射通道补偿器，接收通道补偿器，估计器、存储器和平移混频器，其中，
所述存储器，配置为保存补偿参数；
所述发射通道补偿器，配置为将接收到的同相基带发射信号I_tx和正 交基带发射信号Q_tx进行放大叠加，得到补偿后的同相基带发射信号I_atx和正交基带发射信号Q_atx；并将补偿后的同相基带发射信号I_atx和正交基带发射信号Q_atx经所述射频收发系统的数模转换器和发射通道处理后，形成发射射频信号Tx_out输出；
所述平移混频器，配置为对接收到的发射射频信号Tx_out补偿发射本振频率与接收本振频率之间的差值，再将补偿后的Tx_out作为接收射频信号Rx_in传输至所述射频收发系统的接收通道，分别形成接收I支路的同相基带接收信号I_rx和接收Q支路的正交基带接收信号Q_rx；
所述接收通道补偿器，配置为对接收到的同相基带接收信号I_rx和正交基带接收信号Q_rx进行放大叠加，得到补偿后的同相基带接收信号I_arx和正交基带接收信号Q_arx；并将补偿后的同相基带接收信号I_arx和正交基带接收信号Q_arx传输至估计器；
所述估计器，配置为对补偿后的同相基带接收信号I_arx和正交基带接收信号Q_arx的补偿参数进行估计，并用估计得到的补偿参数更新存储器的补偿参数。
上述方案中，所述发射通道补偿器，配置为将同相基带发射信号I_tx通过第一放大器得到第一信号，将正交基带发射信号Q_tx通过第二放大器得到第二信号，再将所述第一信号和第二信号利用第一加法器进行叠加，得到第三信号；之后利用第二加法器将所述第三信号与第一直流补偿参数DCi进行叠加，得到所述补偿后的同相基带发射信号I_atx；
将正交基带发射信号Q_tx通过第三放大器得到第四信号，将同相基带发射信号I_tx通过第四放大器得到第五信号，再将所述第四信号和第五信号利用第三加法器进行叠加，得到第六信号；之后利用第四加法器将所述第六信号与第二直流补偿参数DCq进行叠加，得到所述补偿后的正交基带发射信号Q_atx。
上述方案中，所述平移混频器，配置为通过平移混频本地振荡器产生 补偿信号Stm；再通过混频器将所述补偿信号Stm与所述发射射频信号Tx_out进行混频后得到的信号，作为所述接收射频信号Rx_in传输至所述射频收发系统的接收通道。
上述方案中，所述接收通道补偿器，配置为将同相基带接收信号I_rx通过第五放大器得到第七信号，将正交基带接收信号Q_rx通过第六放大器得到第八信号，再将所述第七信号和第八信号利用第五加法器进行叠加，得到所述补偿后的同相基带接收信号I_arx；
将正交基带接收信号Q_rx通过第七放大器得到第九信号，将同相基带接收信号I_rx通过第八放大器得到第十信号，再将所述第九信号和第十信号利用第六加法器进行叠加，得到所述补偿后的正交基带接收信号Q_arx。
上述方案中，所述估计器包括：单点离散傅里叶变换DFT计算模块和补偿参数计算模块；其中，
所述单点DFT计算模块，配置为接收由所述接收通道补偿器传输的所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx；
根据补偿后的同相基带接收信号I_arx和补偿后的正交基带接收信号Q_arx得到所述射频收发系统的发射通道IQ失配产生的镜像信号、所述射频收发系统载波泄漏产生的镜像信号及所述射频收发系统的接收通道IQ失配所产生的镜像信号的功率，并将所述三个镜像信号的功率传输至所述补偿参数计算模块；
所述补偿参数计算模块，配置为通过二进制搜索法对所述三个镜像信号的功率进行搜索，估计使所述三个镜像信号功率最小的补偿参数；并将所述估计后得到的补偿参数传输至所述存储器，使所述存储器将所述已有的补偿参数更新为所述补偿参数计算模块估计后得到的补偿参数。
上述方案中，所述补偿参数计算模块，还配置为在通过二进制搜索法 估计所述三个镜像信号的功率之前，确定所述三个镜像信号功率对应的初始搜索区间。
本发明实施例提供的一种校准射频收发机的方法，应用于校准射频收发机的系统中，所述校准射频收发机的系统应用于射频收发机；所述校准射频收发机的系统包括：发射通道补偿器，接收通道补偿器，估计器、存储器和平移混频器；
所述方法包括：
所述发射通道补偿器接收所述射频收发机的单频信号发生器所产生的同相基带发射信号I_tx和正交基带发射信号Q_tx；
所述发射通道补偿器将所述同相基带发射信号I_tx和所述正交基带发射信号Q_tx通过放大叠加进行补偿，得到补偿后的同相基带发射信号I_atx和补偿后的正交基带发射信号Q_atx；并将补偿后的同相基带发射信号I_atx和正交基带发射信号Q_atx经所述射频收发机的数模转换器和发射通道处理后，形成发射射频信号Tx_out输出；
所述平移混频器对接收到的发射射频信号Tx_out补偿发射本振频率与接收本振频率之间的差值；再将所述补偿后的Tx_out作为接收射频信号Rx_in传输至所述射频收发系统的接收通道，分别形成接收I支路的同相基带接收信号I_rx和接收Q支路的正交基带接收信号Q_rx；
所述接收通道补偿器对接收到的所述同相基带接收信号I_rx和所述正交基带接收信号Q_rx进行放大叠加，得到补偿后的同相基带接收信号I_arx和补偿后的正交基带接收信号Q_arx；并将所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx传输至估计器；
所述估计器对补偿后的同相基带接收信号I_arx和正交基带接收信号Q_arx的补偿参数进行估计，并用估计得到的补偿参数更新存储器的补偿参数；所述补偿参数包括：发送相关的补偿参数和接收相关的补偿参数。
上述方案中，所述发射通道补偿器将所述同相基带发射信号I_tx和所 述正交基带发射信号Q_tx通过放大叠加进行补偿，得到补偿后的同相基带发射信号I_atx和补偿后的正交基带发射信号Q_atx，包括：
所述发射通道补偿器将所述同相基带发射信号I_tx放大第一预设倍数之后与放大了第二预设倍数的正交基带发射信号Q_tx进行叠加，并将叠加后的信号与第一直流补偿参数DCi进行叠加，从而得到补偿后的同相基带发射信号；
所述发射通道补偿器将所述正交基带发射信号Q_tx放大第三预设倍数之后与放大了第二预设倍数的同相基带发射信号I_tx进行叠加，并将叠加后的信号与第二直流补偿参数DCq进行叠加，从而得到补偿后的正交基带发射信号；
上述方案中，所述平移混频器对接收到的发射射频信号Tx_out补偿发射本振频率与接收本振频率之间的差值，包括：
所述平移混频器生成频率为ftm的补偿信号Stm，其中，ftm为发射本振频率与接收本振频率之间的差值；
所述平移混频器将所述补偿信号Stm与所述发射射频信号Tx_out进行混频。
上述方案中，所述接收通道补偿器对接收到的所述同相基带接收信号I_rx和所述正交基带接收信号Q_rx进行放大叠加，得到补偿后的同相基带接收信号和补偿后的正交基带接收信号，包括：
所述接收通道补偿器将所述同相基带接收信号I_rx放大第四预设倍数之后与放大了第五预设倍数的正交基带接收信号Q_rx进行叠加，得到补偿后的同相基带接收信号I_arx；
所述接收通道补偿器将所述正交基带接收信号Q_rx放大第六预设倍数之后与放大了第五预设倍数的同相基带接收信号I_rx进行叠加，得到补偿后的正交基带接收信号Q_arx。
上述方案中，所述估计器对补偿后的同相基带接收信号I_arx和正交基带接收信号Q_arx的补偿参数进行估计，包括：
所述估计器接收由所述接收通道补偿器传输的所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx；
根据所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx得到所述射频收发系统的发射通道IQ失配产生的镜像信号、所述射频收发系统载波泄漏产生的镜像信号及所述射频收发系统的接收通道IQ失配所产生的镜像信号的功率；
所述估计器通过二进制搜索法对所述三个镜像信号的功率进行搜索，估计使所述三个镜像信号功率最小的补偿参数。
上述方案中，所述估计器根据所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx得到所述射频收发系统的发射通道IQ失配产生的镜像信号、所述射频收发系统载波泄漏产生的镜像信号及所述射频收发系统的接收通道IQ失配所产生的镜像信号的功率，包括：
所述估计器对根据所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx所得到基带接收信号的复信号进行单点DFT计算，分别得到由发射通道IQ失配、载波泄漏及接收通道IQ失配所产生的镜像信号所在频率ftximage、fcl和frximage；
所述估计器将所述基带接收信号的复信号分别乘以
Figure PCTCN2014092055-appb-000001
Figure PCTCN2014092055-appb-000002
和
Figure PCTCN2014092055-appb-000003
3个序列，并通过低通滤波器减少其它信号对各自功率的影响，得到所述滤波后的信号分别为Itximage+jQtximage、Icl+jQcl和Irximage+jQrximage，其中，fs为所述射频收发系统的接收I支路的模数转换器和所述射频收发系统的接收Q支路的模数转换器采样频率，N为序列长度；
通过计算|Itximage|+|Qtximage|得到所述发射通道IQ失配产生的镜像信号的功率，通过计算|Icl|+|Qcl|得到所述载波泄漏产生的镜像信号的功率，通过计算 |Irximage|+|Qrximage|得到所述接收通道IQ失配所产生的镜像信号的功率，其中，|●|表示对●进行取模计算。
上述方案中，所述估计器通过二进制搜索法对所述三个镜像信号的功率进行搜索，估计使所述三个镜像信号功率最小的补偿参数，包括：
所述估计器将所述发送相关的补偿参数中的第一发射通道补偿参数g1和第二发射通道补偿参数θ1作为第一参数组，与所述发射通道IQ失配产生的镜像信号的功率对应；将所述接收相关的补偿参数中的第一接收通道补偿参数g2和第二接收通道补偿参数θ2作为第二参数组，与所述接收通道IQ失配所产生的镜像信号的功率对应；将所述发射相关的补偿参数中的第一直流补偿参数DCi和第二直流补偿参数DCq作为第三参数组，与所述载波泄漏产生的镜像信号的功率对应；
所述估计器分别对所述第一参数组、所述第二参数组、所述第三参数组进行计算，包括：
步骤1A、所述估计器选取所述第一参数组、所述第二参数组、所述第三参数组中任一参数组，以及所述任一参数组对应的二维搜索区间；
步骤2A、所述估计器将所述搜索区间的每一维区间都平均划分为4个子区间，从而可以得到所述每一维区间的4个子区间的共5个端点；
步骤3A、所述估计器将所述每一维区间的5个端点代入到所述任一参数组对应的镜像信号的功率进行计算，获取所述每一维区间中令所述任一参数组对应的镜像信号的功率最小的端点；
步骤4A、所述估计器将所述每一维区间中令所述任一参数组对应的镜像信号的功率最小的端点设置为中点，并将所述中点的前后两个端点作为边界点，从而得到新的搜索区间；
步骤5A、所述估计器将所述每一维区间中令所述任一参数组对应的镜像信号的功率最小的端点作为所述任一参数组，从而使得所述单点DFT计 算模块计算出新的所述任一参数组对应的镜像信号的功率；
步骤6A、所述估计器所述新的搜索区间中重复执行步骤2A，直至执行预设的次数，从而得到令所述任一参数组对应的镜像信号的功率最小的所述任一参数组。
上述方案中，在所述估计器分别对所述第一参数组、所述第二参数组、所述第三参数组进行计算之前，所述方法还包括：所述估计器确定所述第一参数组、所述第二参数组和所述第三参数组分别对应的初始搜索区间；包括：
所述估计器通过执行三到五次步骤1A至步骤6A的过程或者通过粒子滤波算法或序列重要性采样SIS方法确定所述第一参数组、所述第二参数组和所述第三参数组分别对应的初始搜索区间。
本发明实施例还提供了一种计算机存储介质，所述存储介质包括一组计算机可执行指令，所述指令用于执行本发明实施例所述校准射频收发机的方法。
本发明实施例提供了一种校准射频收发机的系统、方法和计算机存储介质，通过对基带接收信号中由于发射通道和接收通道的IQ失配及发射通道的载波泄露造成的镜像信号进行参数搜索，以得到相应的补偿参数，从而消除发射通道和接收通道的IQ失配及发射通道的载波泄露的影响，校正发射通道的载波泄漏现象以及发射通道和接收通道的IQ失配现象。
附图说明
图1为一种当前常用的射频收发系统结构示意图；
图2为本发明实施例提出的一种校准射频收发机的系统结构示意图；
图3a为本发明实施例提出的一种发射通道补偿器的电路实现示意图；
图3b为本发明实施例提供的一种平移混频器的电路实现示意图；
图3c为本发明实施例提供的一种接收通道补偿器的电路实现示意图；
图4为本发明实施例提供的一种估计器的结构示意图；
图5为本发明实施例提供的基带接收信号的复信号的幅频特性示意图；
图6为本发明实施例提供的一种对参数组进行计算过程的示意图。
具体实施方式
下面将结合本发明实施例中的附图，对本发明实施例中的技术方案进行清楚、完整地描述。
为了能够同时校正发射通道的载波泄漏现象以及发射和接收通道的IQ失配现象，可以将本发明实施例所提出的校准射频收发机的系统应用在目前常用的射频收发系统中，从而能够对本发明实施例的具体技术方案进行详细的阐述。
图1为当前常用的一种射频收发系统10，用于各种无线通信系统的IQ调制及解调。如图1所示，射频收发系统10可以包括发射通道101和接收通道102，图1中，点划线上方的为发射通道101，点划线下方的为接收通道102。
其中，发射通道101可以由单频信号发生器1011产生两路频率均为fsig、且相位相互正交的基带信号I_tx和Q_tx，
Figure PCTCN2014092055-appb-000004
可以称为同相基带发射信号，
Figure PCTCN2014092055-appb-000005
可以称为正交基带发射信号，
Figure PCTCN2014092055-appb-000006
为基带信号的相位；然后将同相基带发射信号传输至发射同向I支路101a，将正交基带发射信号传输至发射正交Q支路101b；
在发射I支路101a中，首先通过数模转换器(DAC，Digital to Analog Converter)1012a和低通滤波器(LF，Lowpass Filter)1013a将同相基带发射信号从数字信号转换为模拟信号；可以理解的，经过数模转换器1012a和低通滤波器1013a后，同相基带发射信号仅仅只改变了自身的表示类型，同相基带发射信号表达式依旧为
Figure PCTCN2014092055-appb-000007
相应的，在发射Q 支路101b中，同样通过数模转换器1012b和低通滤波器1013b将正交基带发射信号从数字信号转换为模拟信号；可以理解的，经过数模转换器1012b和低通滤波器1013b后，正交基带发射信号也仅仅只改变了自身的表示类型，而正交基带发射信号表达式依旧为
Figure PCTCN2014092055-appb-000008
然后，发射本地振荡器1014可以将自身所产生的发射本振信号
Figure PCTCN2014092055-appb-000009
作为发射载波，在理想状态下，发射本振信号可以通过移相器1015移动相位0°来得到发射同相本振信号
Figure PCTCN2014092055-appb-000010
并将LOI_tx0与发射I支路中的LF1013a传出的同相基带发射信号进行混频，具体可以由混频器1016a将LOI_tx0和I_tx进行上混频得到I支路的同相混频发射信号，其中，ftxlo为发射本地振荡器1014的本振频率，
Figure PCTCN2014092055-appb-000011
为发射本地振荡器1014的本振相位；相应的，在理想状态下，发射本振信号通过移相器1015移动相位90°来得到发射正交本振信号
Figure PCTCN2014092055-appb-000012
并将LOQ_tx0与发射Q支路中的低通滤波器1013b传出的正交基带发射信号进行混频，具体可以由混频器1016b将LOQ_tx0和Q_tx进行上混频得到Q支路的正交混频发射信号，类似的，ftxlo为发射本地振荡器1014的本振频率，
Figure PCTCN2014092055-appb-000013
为发射本地振荡器1014的本振相位；
然而，在实际应用中，由于制造成本、工艺及功耗等原因，发射本地振荡器会发生发射通道IQ失配现象，此时，与同相基带发射信号进行混频的发射同相本振信号是由发射本地振荡器1014所产生的发射本振信号经过移相器1015移动相位
Figure PCTCN2014092055-appb-000014
之后，通过放大器1017a放大
Figure PCTCN2014092055-appb-000015
倍得到的，因此，在实际应用中，与同相基带发射信号进行混频的发射同相本振信号为：
Figure PCTCN2014092055-appb-000016
相应的，与正交基带发射信号进行混频的发射正交本振信号是由发射本地振荡器1014所产生的发射本振信号，经 过移相器1015移动相位
Figure PCTCN2014092055-appb-000017
之后，通过放大器1017b放大
Figure PCTCN2014092055-appb-000018
倍得到的，因此，在实际应用中，与正交基带发射信号进行混频的发射正交本振信号为：
Figure PCTCN2014092055-appb-000019
最后，在理想状态下，可以由加法器1018将同相混频发射信号和正交混频发射信号进行叠加之后，通过发射天线1019将叠加后的混频信号作为发射射频信号Tx_out向外部空间发射出去；
然而，在实际应用过程中，由于发射通道的直流失调及集成电路的耦合效应等原因，在本地振荡器的本振频率上，射频收发机会在发射通道101发生载波泄漏现象，因此，理想状态中叠加后的混频信号还需要与载波泄露模拟器10110所模拟的泄露的发射载波Acos(2πflot+φcl)再通过叠加器10111进行一次叠加才能得到实际情况下的发射射频信号Tx_out。
为了说明本发明实施例的技术方案，还可以将发射射频信号Tx_out通过射频环路103后作为接收射频信号Rx_in传输至接收通道102。
其中，接收通道102可以将接收射频信号Rx_in分离为频率相同，且相位相互正交的同相射频接收信号I_rxin和正交射频接收信号Q_rxin；并将同相射频接收信号I_rxin传输至接收同向I支路102a，将正交射频接收信号Q_rxin传输至接收正交Q支路102b；
首先，接收本地振荡器1021可以将自身所产生的接收本振信号
Figure PCTCN2014092055-appb-000020
作为接收载波，在理想状态下，接收本振信号可以通过移相器1022移动相位0°来得到接收同相本振信号
Figure PCTCN2014092055-appb-000021
并将LOI_rx0与接收I支路102a传输过来的同相射频接收信号I_rxin进行混频，具体可以由混频器1023a将LOI_rx0和I_rxin进行下混频得到接收I支路102a的同相基带接收信号I_rx，其中，frxlo为接收本地振荡器1021的本振频率，
Figure PCTCN2014092055-appb-000022
为接收本地振荡器1021的本振相位； 相应的，接收本振信号可以通过移相器1022移动相位90°来得到接收正交本振信号
Figure PCTCN2014092055-appb-000023
并将LOQ_rx0与接收Q支路102b传输过来的正交射频接收信号Q_rxin进行混频，具体可以由混频器1023b将LOQ_rx0和Q_rxin进行下混频得到接收Q支路的正交基带接收信号Q_rx，类似的，frxlo为接收本地振荡器1021的本振频率，
Figure PCTCN2014092055-appb-000024
为接收本地振荡器1021的本振相位；
然而，在实际应用中，由于制造成本、工艺及功耗等原因，接收本地振荡器也会发生接收通道IQ失配现象，此时，与同相射频接收信号I_rxin进行混频的接收同相本振信号是由接收本地振荡器1021所产生的接收本振信号经过移相器1022移动相位
Figure PCTCN2014092055-appb-000025
之后，通过放大器1024a放大
Figure PCTCN2014092055-appb-000026
倍得到的，因此，在实际应用中，与信号I_rxin进行混频的接收同相本振信号为：
Figure PCTCN2014092055-appb-000027
相应的，与接收正交射频信号Q_rxin进行混频的接收正交本振信号是由接收本地振荡器1021所产生的接收本振信号经过移相器1022移动相位
Figure PCTCN2014092055-appb-000028
之后，通过放大器1024b放大
Figure PCTCN2014092055-appb-000029
倍得到的，因此，在实际应用中，与信号Q_rxin进行混频的接收正交本振信号为：
Figure PCTCN2014092055-appb-000030
然后，接收I支路102a中，将混频得到的同相基带接收信号I_rx依次通过低通滤波器1025a、可变增益放大器1026a以及模数转换器(ADC，Analog to Digital Converter)1027a之后，可以得到数字信号形式的同相基带接收信号I_rx。
需要说明的是，数字信号形式的同相基带接收信号I_rx与混频得到的同相基带接收信号I_rx仅仅只是表示类型的不同，而信号的表达式仍然相同；相应的，接收Q支路102b中，将混频得到的正交基带接收信号Q_rx 依次通过低通滤波器1025b、可变增益放大器1026b以及ADC 1027b之后，可以得到数字信号形式的正交基带接收信号Q_rx，同样需要说明的是，数字信号形式的正交基带接收信号Q_rx与混频得到的正交基带接收信号Q_rx也仅仅只是表示类型的不同，而信号的表达式仍然相同；可以理解的，数字信号形式的I_rx和数字信号形式的Q_rx就是接收基带信号。
还有需要注意的是，在实际应用中，发射通道的IQ失配、载波泄露以及接收通道的IQ失配均分别会使得同相基带接收信号I_rx和正交基带接收信号Q_rx中额外的包括由发射通道IQ失配、载波泄漏及接收通道IQ失配产生的镜像信号，这三种镜像信号会成为同相基带接收信号I_rx和正交基带接收信号Q_rx的干扰，这是因为在理想状态下，同相基带接收信号I_rx和正交基带接收信号Q_rx的能量只存在于频率frxsig＝ftxlo+fsig-frxlo处；而实际应用中，由于三种镜像信号的存在，同相基带接收信号I_rx和正交基带接收信号Q_rx的能量会分散在频率为ftximage＝ftxlo-fsig-frxlo、fcl＝ftxlo-frxlo以及frximage＝-(ftxlo+fsig-frxlo)处，其中，ftximage表示由发射通道IQ失配产生的镜像信号所在频率；fcl表示由载波泄露产生的镜像信号所在频率；frximage表示由接收通道IQ失配产生的镜像信号所在频率；
根据能量守恒定律，这三种镜像信号会导致同相基带接收信号I_rx和正交基带接收信号Q_rx中处于频率frxsig＝ftxlo+fsig-frxlo处能量的削弱。
综上所述，可以通过补偿的方式来降低这种干扰，例如，在发射通道101的单频信号发生器1011产生同相基带发射信号和正交基带发射信号之后，对同相基带发射信号和正交基带发射信号分别进行发射IQ失配以及载波泄露的补偿；相应的，在接收通道102，也会对ADC 1027a和ADC 1027b得到的数字信号形式的I_rx和数字信号形式的Q_rx分别进行接收IQ失配补偿。
在本发明实施例中，如图2所示，提出了一种校准射频收发机的系统 20，可以应用在如图1所示的射频收发系统10中，可以理解的，图1所示的射频收发系统仅用于对本发明实施例的技术方案进行详细说明，并不仅限定于图1所示的射频收发系统；在本实施例中，将系统20应用于图1所示的射频收发系统，并结合前述对图1所示的射频收发系统的说明，可以理解的，图2保留了射频收发系统10中与系统20相关的部分和器件，其他部分与图1所示的射频收发系统10一致，因此在图2中用省略号代替。
该系统20可以包括：发射通道补偿器201，接收通道补偿器203，估计器204、存储器205和平移混频器202；其中，
存储器205，配置为保存补偿参数；
这里，所保存的补偿参数包括发送相关的补偿参数和接收相关的补偿参数，分别用于提供给发射通道补偿器201、接收通道补偿器203完成信号补偿；
这里，发送相关的补偿参数包括：第一发射通道补偿参数g1、第二发射通道补偿参数θ1、第一直流补偿参数DCi、第二直流补偿参数DCq；
接收相关的补偿参数包括：第一接收通道补偿参数g2和第二接收通道补偿参数θ2。
发射通道补偿器201，配置为接收同相基带发射信号I_tx和正交基带发射信号Q_tx，将同相基带发射信号I_tx和正交基带发射信号Q_tx经放大叠加后得到补偿后的同相基带发射信号I_atx和补偿后的正交基带发射信号Q_atx，并将补偿后的同相基带发射信号I_atx传输至发射I支路101a的数模转换器1012a，补偿后的正交基带发射信号Q_atx传输至发射Q支路101b的数模转换器1012b；从而可使射频收发系统10的发射通道101根据补偿后的同相基带发射信号I_atx和补偿后的正交基带发射信号Q_atx得到发射射频信号Tx_out；
可以理解的，射频收发系统10得到发射射频信号Tx_out的具体过程可由上述对图1的说明进行实现，在此不再赘述。
这里，发射通道补偿器201所接收的同相基带发射信号I_tx和正交基带发射信号Q_tx由射频收发系统10中的单频信号发生器1011产生；
其中，发射通道补偿器201将同相基带发射信号I_tx放大(1-g1)倍之后与放大了θ1倍的正交基带发射信号Q_tx进行叠加，并将叠加后的信号与第一直流补偿参数DCi进行叠加，从而可以得到补偿后的同相基带发射信号
Figure PCTCN2014092055-appb-000031
发射通道补偿器201将正交基带发射信号Q_tx放大(1+g1)倍之后与放大了θ1倍的同相基带发射信号I_tx进行叠加，并将叠加后的信号与第二直流补偿参数DCq进行叠加，从而可以得到补偿后的正交基带发射信号
Figure PCTCN2014092055-appb-000032
示例性的，发射通道补偿器201的电路实现形式可以如图3a所示：
将同相基带发射信号I_tx通过(1-g1)倍的第一放大器的第一信号与将正交基带发射信号Q_tx通过θ1倍的第二放大器的第二信号利用第一加法器进行叠加，得到第三信号；并利用第二加法器将第三信号与第一直流补偿参数DCi进行叠加，从而得到补偿后的同相基带发射信号
Figure PCTCN2014092055-appb-000033
将正交基带发射信号Q_tx通过(1+g1)倍第三放大器的第四信号与将同相基带发射信号I_tx通过θ1倍的第四放大器的第五信号利用第三加法器进行叠加，得到第六信号；并利用第四加法器将第六信号与第二直流补偿参数DCq进行叠加，从而得到补偿后的正交基带发射信号
Figure PCTCN2014092055-appb-000034
平移混频器(TM，Translational Mixer)202，配置为对接收的由射频收发系统10传输的发射射频信号Tx_out补偿发射本振频率与接收本振频率之间的差值，将补偿后的发射射频信号Tx_out作为接收射频信号Rx_in传输至射频收发系统10的接收通道102，以使得射频收发系统10根据接收射 频信号Rx_in得到射频收发系统10的接收I支路102a的同相基带接收信号I_rx和射频收发系统10的接收Q支路102b的正交基带接收信号Q_rx；
其中，平移混频器202可以替换图1中的射频环路103；平移混频器202可以通过生成补偿信号Stm＝cos(2πftmt+φtm)，并将补偿信号Stm与发射射频信号Tx_out进行混频后得到的信号作为接收射频信号Rx_in传输至射频收发系统10的接收通道102；其中，ftm为发射本振频率与接收本振频率之间的差值，φtm为补偿信号的相位；
示例性的，平移混频器202的电路实现形式可以如图3b所示，通过平移混频本地振荡器(LO TM)产生补偿信号Stm＝cos(2πftmt+φtm)，其中，ftm为发射本振频率与接收本振频率之间的差值，φtm为补偿信号的相位；然后通过混频器将补偿信号Stm与发射射频信号Tx_out进行混频之后得到的信号作为接收射频信号Rx_in传输至接收通道102；
接收通道补偿器203，配置为接收由射频收发系统10的接收I支路102a和射频收发系统10的接收Q支路102b传输来的同相基带接收信号I_rx和正交基带接收信号Q_rx；将所述同相基带接收信号I_rx和所述正交基带接收信号Q_rx进行放大叠加后得到补偿后的同相基带接收信号I_arx和正交基带接收信号Q_arx，并将补偿后的同相基带接收信号I_arx和补偿后的正交基带接收信号Q_arx传输至估计器204；
其中，接收通道补偿器203将同相基带接收信号I_rx放大(1-g2)倍之后与放大了θ2倍的正交基带接收信号Q_rx进行叠加，从而得到补偿后的同相基带接收信号I_arx；
接收通道补偿器203将正交基带接收信号Q_rx放大(1+g2)倍之后与放大了θ2倍的同相基带接收信号I_rx进行叠加，从而得到补偿后的正交基带接收信号Q_arx；
示例性的，接收通道补偿器203的电路实现形式可以如图3c所示：
将同相基带接收信号I_rx通过(1-g2)倍第五放大器的第七信号与将正交基带接收信号Q_rx通过θ2倍的第六放大器的第八信号利用第五加法器进行叠加，从而得到补偿后的同相基带接收信号I_arx；
将正交基带接收信号Q_rx通过(1+g2)倍第七放大器的第九信号与将同相基带接收信号I_rx通过θ2倍的第八放大器的第十信号利用第六加法器进行叠加，从而得到补偿后的正交基带接收信号Q_arx。
可以理解的，上述放大器的倍数可以是发射通道补偿器201和接收通道补偿器203通过从存储器205接收相应的发送相关的补偿参数和接收相关的补偿参数之后，在放大器中预先设置的。
估计器204，配置为根据所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx对所述补偿参数进行估计，并将所述估计后的补偿参数传输至所述存储器，以使得所述存储器将所述已有的补偿参数替换为所述估计后的补偿参数。
这里，估计器204可以包括单点离散傅里叶变换(DFT，Discrete Fourier Transform)计算模块2041和补偿参数计算模块2042；如图4所示，其中，
单点DFT计算模块2041，配置为接收由接收通道补偿器203传输的补偿后的同相基带接收信号I_arx和补偿后的正交基带接收信号Q_arx；
根据补偿后的同相基带接收信号I_arx和补偿后的正交基带接收信号Q_arx得到基带接收信号的复信号(I_arx+j×Q_arx)，其中，j表示复数单位，可以由-1开根号得到；
对基带接收信号的复信号(I_arx+j×Q_arx)进行单点DFT计算，分别得到由发射通道IQ失配、载波泄漏及接收通道IQ失配所产生的镜像信号所在频率ftximage、fcl和frximage，
其中，ftximage＝ftxlo-fsig-frxlo+ftm、fcl＝ftxlo-frxlo+ftm以及frximage＝-(ftxlo+fsig-frxlo+ftm)，fsig为所述射频收发系统的单频信号发生器产 生的同相基带发射信号和正交基带发射信号的频率，ftxlo为所述射频收发系统的发射本地振荡器的本振频率，frxlo为所述射频收发系统的接收本地振荡器的本振频率，ftm为所述平移混频本地振荡器产生补偿信号的频率；
其中，由于本实施例中，平移混频器202通过将频率为ftm的补偿信号Stm与发射射频信号Tx_out进行混频之后得到的信号作为接收射频信号Rx_in传输至接收通道102，因此，本实施例中，由发射通道IQ失配、载波泄漏及接收通道IQ失配产生的三个镜像信号所在频率分别是ftximage＝ftxlo-fsig-frxlo+ftm、fcl＝ftxlo-frxlo+ftm以及frximage＝-(ftxlo+fsig-frxlo+ftm)处；相应的，补偿后的同相基带接收信号I_arx和补偿后的正交基带接收信号Q_arx所在频率为frxsig＝(ftxlo+fsig-frxlo+ftm)；在如图5所示的幅频特性示意图中，横坐标表示频率，纵坐标表示信号的幅度，从图5可知，对于横坐标来说，frxsig与ftximage关于fcl对称，frxsig与frximage关于f＝0对称，因此，单点DFT计算模块2041可以根据以上两种对称关系得到三个镜像信号所在频率；
通过基带接收信号的复信号以及三个镜像信号所在频率ftximage、fcl和frximage分别求出所述发射通道IQ失配产生的镜像信号、载波泄漏产生的镜像信号及接收通道IQ失配所产生的镜像信号的功率，并将所述三个镜像信号的功率传输至补偿参数计算模块2042；
其中，首先可以将基带接收信号的复信号分别乘以
Figure PCTCN2014092055-appb-000035
Figure PCTCN2014092055-appb-000036
和
Figure PCTCN2014092055-appb-000037
3个序列，并通过低通滤波器减少其它信号对各自功率的影响，从而可以得到滤波后的信号分别为Itximage+jQtximage、Icl+jQcl和Irximage+jQrximage；其中，fs为模数转换器1027a和模数转换器1027b采样频率，N为序列长度；
然后通过计算|Itximage|+|Qtximage|得到所述射频收发系统10的发射通道IQ 失配产生的镜像信号的功率，通过计算|Icl|+|Qcl|得到所述射频收发系统10载波泄漏产生的镜像信号的功率，通过计算|Irximage|+|Qrximage|得到所述射频收发系统10接收通道IQ失配所产生的镜像信号的功率，其中，|●|表示对●进行取模计算；
补偿参数计算模块2042，配置为根据上述三个镜像信号的功率以及本发明实施例所提出的一种新的二进制搜索法估计使三个镜像信号功率最小的补偿参数；并将估计后的补偿参数传输至存储器205，使得存储器205将已有的补偿参数更新为补偿参数计算模块2042传输的估计后的补偿参数；
值得注意的是，根据关于发射通道IQ失配所导致的发射同相本振信号LOI_tx和发射正交本振信号LOQ_tx的表达式可知，由发射通道IQ失配产生的镜像信号仅与参数ε1和
Figure PCTCN2014092055-appb-000038
有关，因此，结合补偿后的同相基带发射信号I_atx与补偿后的正交基带发射信号Q_atx可以得知，当g1＝ε1且
Figure PCTCN2014092055-appb-000039
时，就可以使得由发射通道IQ失配导致的镜像信号功率最小；同理，由接收通道IQ失配产生的镜像信号仅与参数ε2和
Figure PCTCN2014092055-appb-000040
有关，因此，当g2＝ε2且
Figure PCTCN2014092055-appb-000041
时，就可以使得由接收通道IQ失配导致的镜像信号功率最小；此外，可以对由载波泄露导致的镜像信号功率进行搜索，得到使由载波泄露导致的镜像信号功率最小的第一直流补偿参数DCi和第二直流补偿参数DCq；
从上述的分析还可以得知，第一发射通道补偿参数g1和第二发射通道补偿参数θ1、第一接收通道补偿参数g2和第二接收通道补偿参数θ2、第一直流补偿参数DCi和第二直流补偿参数DCq，这三组参数之间是相互独立的关系；因此，可以并行地对这三组参数进行计算，以缩短补偿参数的计算时间；
示例性的，由于上述三组参数之间是相互独立的，且可以并行地对这三组参数进行计算，因此可以并行地对上述三组参数通过本发明实施例所提出的新的二进制搜索法来获取使得三个镜像信号功率最小的补偿参数， 为了简洁的对计算过程进行描述，可以将第一发射通道补偿参数g1和第二发射通道补偿参数θ1作为第一参数组，与所述发射通道IQ失配产生的镜像信号的功率对应；第一接收通道补偿参数g2和第二接收通道补偿参数θ2作为第二参数组，与所述接收通道IQ失配所产生的镜像信号的功率对应；第一直流补偿参数DCi和第二直流补偿参数DCq作为第三参数组，与所述载波泄漏产生的镜像信号的功率对应；具体通过本发明实施例所提出的新的二进制搜索法对三个参数组进行计算过程是类似的，本发明实施例从上述的三个参数组中任取一个参数组进行具体说明，其他两个参数组则可以根据与该具体说明相近的方法进行计算。
如图6所示，具体过程如下：
S601：选择与选取的任一参数组对应的搜索区间；
以第一参数组为例，由于第一参数组中包括两个参数，所以，与第一参数组对应的初始搜索区间可以是一个二维区间，因此，可以将第一发射通道补偿参数g1设置为第一维参数；对应的，将第二发射通道补偿参数θ1设置为第二维参数；可以理解的，第一维参数也可以是第二发射通道补偿参数θ1而对应的第二维参数则是第一发射通道补偿参数g1，本发明实施例对此不作任何限定；
S602：将所述搜索区间的每一维区间都平均划分为四个子区间，从而可以得到每一维区间的四个子区间的共五个端点，可以理解的，每一维区间的五个端点是按照大小顺序排列的；
S603：将每一维区间的五个端点代入到选取的任一参数组对应的镜像信号的功率进行计算，获取每一维区间中令选取的任一参数组对应的镜像信号的功率最小的端点；
以第一参数组为例，可以将每一维区间的五个端点代入到第一参数组对应的|Itximage|+|Qtximage|进行计算，获取每一维区间中令|Itximage|+|Qtximage|最小的端 点；
S604：将每一维区间中令所述任一参数组对应的镜像信号的功率最小的端点设置为中点，并将所述中点的前后两个端点作为边界点，从而得到新的搜索区间；
以第一参数组为例，可以将每一维区间中令|Itximage|+|Qtximage|最小的端点设置为中点，并将所述中点的前后两个端点作为边界点，从而得到新的搜索区间；
S605：将所述每一维区间中令所述任一参数组对应的镜像信号的功率最小的端点作为所述任一参数组，从而使得所述单点DFT计算模块计算出新的所述任一参数组对应的镜像信号的功率；
以第一参数组为例，可以将每一维区间中令|Itximage|+|Qtximage|最小的端点作为第一发射通道补偿参数g1和第二发射通道补偿参数θ1，并对存储器205中所保存的对应的补偿参数进行更新，从而使得系统20计算出新的|Itximage|+|Qtximage|；
S606：在所述新的搜索区间中重复执行步骤S602，直至执行预设的次数，从而得到令所述任一参数组对应的镜像信号的功率最小的所述任一参数组。
以第一参数组为例，可以所述新的搜索区间中重复执行步骤S602，直至执行预设的次数，从而得到令|Itximage|+|Qtximage|最小的第一发射通道补偿参数g1和第二发射通道补偿参数θ1。
可以理解的，步骤S601至S606也可以应用在对第二参数组和第三参数组进行估计的过程中，具体与第一参数组类似，只是将相应的参数组以及对应的镜像信号功率进行改变就可以实现，具体不再赘述。
需要说明的是，当初始选定的对第一参数组g1和θ1进行搜索的搜索区间中包括ε1和
Figure PCTCN2014092055-appb-000042
时，执行N(N→∞，∞为无穷大)次步骤S601至步骤S606 之后，可以获得第一发射通道补偿参数g1和第二发射通道补偿参数θ1的全局最优值；此时，最终得到的第一发射通道补偿参数g1和第二发射通道补偿参数θ1的误差不大于L/2N+1，其中L表示最初的搜索区间的长度，N表示预设的执行次数；而且搜索时间等于T×(2N+1)，其中T表示单点的计算时间；
需要进一步说明的是，一方面，当初始选定的对参数g1和θ1进行搜索的搜索区间中没有包括ε1和
Figure PCTCN2014092055-appb-000043
时，步骤S601至步骤S606只能在所述搜索区间内获得第一发射通道补偿参数g1和第二发射通道补偿参数θ1的距离ε1和
Figure PCTCN2014092055-appb-000044
最近的点，因此仅能够得到在所述搜索区间内的最优解，该最优解并不是全局的最优解，而是全局中的局部最优值；另一方面，参数g1和θ1之间是具有一定的相关性的，根据这个相关性，当参数g1和θ1中的任意一个参数的初始搜索点距离本身的最优点较远的时候，对另一个参数搜索得到的结果也会距离所述另一个参数本身的最优点较远，导致搜索的结果误差过大，最终也只能得到的局部最优值；
为了解决这个问题，可以在步骤S601之前，还可以包括确定第一参数组对应的初始搜索区间的过程，这个过程也可以看作是对参数g1和θ1进行粗略计算的过程，以使得粗略估计得到的参数g1和θ1的范围能够包含ε1和
Figure PCTCN2014092055-appb-000045
而且可以将这个粗略估计的范围作为步骤S601至步骤S606的初始选定的搜索区间。确定第一参数组对应的初始搜索区间的过程可以是执行三到五次步骤S601至步骤S606的过程，也可以是通过其他应用于离散值的估计算法过程，求得ε1和
Figure PCTCN2014092055-appb-000046
的高概率区间，从而将这个高概率区间作为第一参数组对应的初始搜索区间，例如粒子滤波算法以及序列重要性采样(SIS，Sequential Importance Sampling)方法。
对于第二参数组和第三参数组，同理可知，也可以包括在步骤S601之前包括确定第二参数组和第三参数组对应的初始搜索区间的过程，这个过 程也可以看作是对参数第二参数组和第三参数组进行粗略计算的过程，以使得粗略估计得到的第二参数组和第三参数组的范围能够分别包含ε2和
Figure PCTCN2014092055-appb-000047
以及载波泄露的信号，而且可以将这个粗略估计的范围作为对第二参数组和第三参数组分别执行步骤S601至步骤S606的初始选定的搜索区间。确定第二参数组和第三参数组对应的初始搜索区间的过程也可以是执行三到五次步骤S601至步骤S606的过程，也可以是通过其他应用于离散值的估计算法过程，例如粒子滤波算法以及SIS方法。
所以，本系统20可以通过估计器204根据所述三个镜像信号的功率直接得到所述的三个参数组。
需要说明的是，由于三个参数组之间的独立性，因此对第一参数组、第二参数组和第三参数组计算过程可以并行的进行处理，通过空间换时间的方式以节省对补偿参数的估计时间；从而经过N次迭代之后就能够直接得出第一发射通道补偿参数g1和第二发射通道补偿参数θ1、第一接收通道补偿参数g2和第二接收通道补偿参数θ2、第一直流补偿参数DCi和第二直流补偿参数DCq。
本发明实施例提供了一种校准射频收发机的系统以及该系统对射频收发机进行校准的方法，通过对基带接收信号中由发射通道和接收通道的IQ失配及发射通道的载波泄露造成的镜像信号进行参数搜索，以得到相应的补偿参数，从而消除发射通道和接收通道的IQ失配及发射通道的载波泄露的影响，校正发射通道的载波泄漏现象以及发射通道和接收通道的IQ失配现象。
本发明实施例还提供了一种计算机存储介质，所述存储介质包括一组计算机可执行指令，所述指令用于执行本发明实施例所述校准射频收发机的方法。
本领域内的技术人员应明白，本发明的实施例可提供为方法、系统、 或计算机程序产品。因此，本发明可采用硬件实施例、软件实施例、或结合软件和硬件方面的实施例的形式。而且，本发明可采用在一个或多个其中包含有计算机可用程序代码的计算机可用存储介质(包括但不限于磁盘存储器和光学存储器等)上实施的计算机程序产品的形式。
本发明是参照根据本发明实施例的方法、设备(系统)、和计算机程序产品的流程图和/或方框图来描述的。应理解可由计算机程序指令实现流程图和/或方框图中的每一流程和/或方框、以及流程图和/或方框图中的流程和/或方框的结合。可提供这些计算机程序指令到通用计算机、专用计算机、嵌入式处理机或其他可编程数据处理设备的处理器以产生一个机器，使得通过计算机或其他可编程数据处理设备的处理器执行的指令产生用于实现在流程图一个流程或多个流程和/或方框图一个方框或多个方框中指定的功能的装置。
这些计算机程序指令也可存储在能引导计算机或其他可编程数据处理设备以特定方式工作的计算机可读存储器中，使得存储在该计算机可读存储器中的指令产生包括指令装置的制造品，该指令装置实现在流程图一个流程或多个流程和/或方框图一个方框或多个方框中指定的功能。
这些计算机程序指令也可装载到计算机或其他可编程数据处理设备上，使得在计算机或其他可编程设备上执行一系列操作步骤以产生计算机实现的处理，从而在计算机或其他可编程设备上执行的指令提供用于实现在流程图一个流程或多个流程和/或方框图一个方框或多个方框中指定的功能的步骤。
以上所述，仅为本发明的较佳实施例而已，并非用于限定本发明的保护范围。

Claims (15)

  1. 一种校准射频收发机的系统，应用于射频收发系统，所述系统包括：发射通道补偿器，接收通道补偿器，估计器、存储器和平移混频器，其中，
    所述存储器，配置为保存补偿参数；
    所述发射通道补偿器，配置为将接收到的同相基带发射信号I_tx和正交基带发射信号Q_tx进行放大叠加，得到补偿后的同相基带发射信号I_atx和正交基带发射信号Q_atx；并将补偿后的同相基带发射信号I_atx和正交基带发射信号Q_atx经所述射频收发系统的数模转换器和发射通道处理后，形成发射射频信号Tx_out输出；
    所述平移混频器，配置为对接收到的发射射频信号Tx_out补偿发射本振频率与接收本振频率之间的差值，再将补偿后的Tx_out作为接收射频信号Rx_in传输至所述射频收发系统的接收通道，分别形成接收I支路的同相基带接收信号I_rx和接收Q支路的正交基带接收信号Q_rx；
    所述接收通道补偿器，配置为对接收到的同相基带接收信号I_rx和正交基带接收信号Q_rx进行放大叠加，得到补偿后的同相基带接收信号I_arx和正交基带接收信号Q_arx；并将补偿后的同相基带接收信号I_arx和正交基带接收信号Q_arx传输至估计器；
    所述估计器，配置为对补偿后的同相基带接收信号I_arx和正交基带接收信号Q_arx的补偿参数进行估计，并用估计得到的补偿参数更新存储器的补偿参数。
  2. 根据权利要求1所述的系统，其中，所述发射通道补偿器，配置为将同相基带发射信号I_tx通过第一放大器得到第一信号，将正交基带发射信号Q_tx通过第二放大器得到第二信号，再将所述第一信号和第二信号利用第一加法器进行叠加，得到第三信号；之后利用第二加法器将 所述第三信号与第一直流补偿参数DCi进行叠加，得到所述补偿后的同相基带发射信号I_atx；
    将正交基带发射信号Q_tx通过第三放大器得到第四信号，将同相基带发射信号I_tx通过第四放大器得到第五信号，再将所述第四信号和第五信号利用第三加法器进行叠加，得到第六信号；之后利用第四加法器将所述第六信号与第二直流补偿参数DCq进行叠加，得到所述补偿后的正交基带发射信号Q_atx。
  3. 根据权利要求1所述的系统，其中，所述平移混频器，配置为通过平移混频本地振荡器产生补偿信号Stm；再通过混频器将所述补偿信号Stm与所述发射射频信号Tx_out进行混频后得到的信号，作为所述接收射频信号Rx_in传输至所述射频收发系统的接收通道。
  4. 根据权利要求1所述的系统，其中，所述接收通道补偿器，配置为将同相基带接收信号I_rx通过第五放大器得到第七信号，将正交基带接收信号Q_rx通过第六放大器得到第八信号，再将所述第七信号和第八信号利用第五加法器进行叠加，得到所述补偿后的同相基带接收信号I_arx；
    将正交基带接收信号Q_rx通过第七放大器得到第九信号，将同相基带接收信号I_rx通过第八放大器得到第十信号，再将所述第九信号和第十信号利用第六加法器进行叠加，得到所述补偿后的正交基带接收信号Q_arx。
  5. 根据权利要求1所述的系统，其中，所述估计器包括：单点离散傅里叶变换DFT计算模块和补偿参数计算模块；其中，
    所述单点DFT计算模块，配置为接收由所述接收通道补偿器传输的所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx；
    根据补偿后的同相基带接收信号I_arx和补偿后的正交基带接收信号Q_arx得到所述射频收发系统的发射通道IQ失配产生的镜像信号、所述射频收发系统载波泄漏产生的镜像信号及所述射频收发系统的接收通道IQ失配所产生的镜像信号的功率，并将所述三个镜像信号的功率传输至所述补偿参数计算模块；
    所述补偿参数计算模块，配置为通过二进制搜索法对所述三个镜像信号的功率进行搜索，估计使所述三个镜像信号功率最小的补偿参数；并将所述估计后得到的补偿参数传输至所述存储器，使所述存储器将所述已有的补偿参数更新为所述补偿参数计算模块估计后得到的补偿参数。
  6. 根据权利要求5所述的系统，其中，所述补偿参数计算模块，还配置为在通过二进制搜索法估计所述三个镜像信号的功率之前，确定所述三个镜像信号功率对应的初始搜索区间。
  7. 一种校准射频收发机的方法，应用于校准射频收发机的系统中，所述校准射频收发机的系统应用于射频收发机；所述校准射频收发机的系统包括：发射通道补偿器，接收通道补偿器，估计器、存储器和平移混频器；
    所述方法包括：
    所述发射通道补偿器接收所述射频收发机的单频信号发生器所产生的同相基带发射信号I_tx和正交基带发射信号Q_tx；
    所述发射通道补偿器将所述同相基带发射信号I_tx和所述正交基带发射信号Q_tx通过放大叠加进行补偿，得到补偿后的同相基带发射信号I_atx和补偿后的正交基带发射信号Q_atx；并将补偿后的同相基带发射信号I_atx和正交基带发射信号Q_atx经所述射频收发机的数模转换器和发射通道处理后，形成发射射频信号Tx_out输出；
    所述平移混频器对接收到的发射射频信号Tx_out补偿发射本振频率与接收本振频率之间的差值；再将所述补偿后的Tx_out作为接收射频信 号Rx_in传输至所述射频收发系统的接收通道，分别形成接收I支路的同相基带接收信号I_rx和接收Q支路的正交基带接收信号Q_rx；
    所述接收通道补偿器对接收到的所述同相基带接收信号I_rx和所述正交基带接收信号Q_rx进行放大叠加，得到补偿后的同相基带接收信号I_arx和补偿后的正交基带接收信号Q_arx；并将所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx传输至估计器；
    所述估计器对补偿后的同相基带接收信号I_arx和正交基带接收信号Q_arx的补偿参数进行估计，并用估计得到的补偿参数更新存储器的补偿参数；所述补偿参数包括：发送相关的补偿参数和接收相关的补偿参数。
  8. 根据权利要求7所述的方法，其中，所述发射通道补偿器将所述同相基带发射信号I_tx和所述正交基带发射信号Q_tx通过放大叠加进行补偿，得到补偿后的同相基带发射信号I_atx和补偿后的正交基带发射信号Q_atx，包括：
    所述发射通道补偿器将所述同相基带发射信号I_tx放大第一预设倍数之后与放大了第二预设倍数的正交基带发射信号Q_tx进行叠加，并将叠加后的信号与第一直流补偿参数DCi进行叠加，从而得到补偿后的同相基带发射信号；
    所述发射通道补偿器将所述正交基带发射信号Q_tx放大第三预设倍数之后与放大了第二预设倍数的同相基带发射信号I_tx进行叠加，并将叠加后的信号与第二直流补偿参数DCq进行叠加，从而得到补偿后的正交基带发射信号；
  9. 根据权利要求10所述的方法，其中，所述平移混频器对接收到的发射射频信号Tx_out补偿发射本振频率与接收本振频率之间的差值，包括：
    所述平移混频器生成频率为ftm的补偿信号Stm，其中，ftm为发射本振 频率与接收本振频率之间的差值；
    所述平移混频器将所述补偿信号Stm与所述发射射频信号Tx_out进行混频。
  10. 根据权利要求7所述的方法，其中，所述接收通道补偿器对接收到的所述同相基带接收信号I_rx和所述正交基带接收信号Q_rx进行放大叠加，得到补偿后的同相基带接收信号和补偿后的正交基带接收信号，包括：
    所述接收通道补偿器将所述同相基带接收信号I_rx放大第四预设倍数之后与放大了第五预设倍数的正交基带接收信号Q_rx进行叠加，得到补偿后的同相基带接收信号I_arx；
    所述接收通道补偿器将所述正交基带接收信号Q_rx放大第六预设倍数之后与放大了第五预设倍数的同相基带接收信号I_rx进行叠加，得到补偿后的正交基带接收信号Q_arx。
  11. 根据权利要求7所述的方法，其中，所述估计器对补偿后的同相基带接收信号I_arx和正交基带接收信号Q_arx的补偿参数进行估计，包括：
    所述估计器接收由所述接收通道补偿器传输的所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx；
    根据所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx得到所述射频收发系统的发射通道IQ失配产生的镜像信号、所述射频收发系统载波泄漏产生的镜像信号及所述射频收发系统的接收通道IQ失配所产生的镜像信号的功率；
    所述估计器通过二进制搜索法对所述三个镜像信号的功率进行搜索，估计使所述三个镜像信号功率最小的补偿参数。
  12. 根据权利要求11所述的方法，其中，所述估计器根据所述补偿 后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx得到所述射频收发系统的发射通道IQ失配产生的镜像信号、所述射频收发系统载波泄漏产生的镜像信号及所述射频收发系统的接收通道IQ失配所产生的镜像信号的功率，包括：
    所述估计器对根据所述补偿后的同相基带接收信号I_arx和所述补偿后的正交基带接收信号Q_arx所得到基带接收信号的复信号进行单点DFT计算，分别得到由发射通道IQ失配、载波泄漏及接收通道IQ失配所产生的镜像信号所在频率ftximage、fcl和frximage；
    所述估计器将所述基带接收信号的复信号分别乘以
    Figure PCTCN2014092055-appb-100001
    Figure PCTCN2014092055-appb-100002
    和
    Figure PCTCN2014092055-appb-100003
    3个序列，并通过低通滤波器减少其它信号对各自功率的影响，得到所述滤波后的信号分别为Itximage+jQtximage、Icl+jQcl和Irximage+jQrximage，其中，fs为所述射频收发系统的接收I支路的模数转换器和所述射频收发系统的接收Q支路的模数转换器采样频率，N为序列长度；
    通过计算|Itximage|+|Qtximage|得到所述发射通道IQ失配产生的镜像信号的功率，通过计算|Icl|+|Qcl|得到所述载波泄漏产生的镜像信号的功率，通过计算|Irximage|+|Qrximage|得到所述接收通道IQ失配所产生的镜像信号的功率，其中，|●|表示对●进行取模计算。
  13. 根据权利要求12所述的方法，其中，所述估计器通过二进制搜索法对所述三个镜像信号的功率进行搜索，估计使所述三个镜像信号功率最小的补偿参数，包括：
    所述估计器将所述发送相关的补偿参数中的第一发射通道补偿参数g1和第二发射通道补偿参数θ1作为第一参数组，与所述发射通道IQ失配产生的镜像信号的功率对应；将所述接收相关的补偿参数中的第一接 收通道补偿参数g2和第二接收通道补偿参数θ2作为第二参数组，与所述接收通道IQ失配所产生的镜像信号的功率对应；将所述发射相关的补偿参数中的第一直流补偿参数DCi和第二直流补偿参数DCq作为第三参数组，与所述载波泄漏产生的镜像信号的功率对应；
    所述估计器分别对所述第一参数组、所述第二参数组、所述第三参数组进行计算，包括：
    步骤1A、所述估计器选取所述第一参数组、所述第二参数组、所述第三参数组中任一参数组，以及所述任一参数组对应的二维搜索区间；
    步骤2A、所述估计器将所述搜索区间的每一维区间都平均划分为4个子区间，从而可以得到所述每一维区间的4个子区间的共5个端点；
    步骤3A、所述估计器将所述每一维区间的5个端点代入到所述任一参数组对应的镜像信号的功率进行计算，获取所述每一维区间中令所述任一参数组对应的镜像信号的功率最小的端点；
    步骤4A、所述估计器将所述每一维区间中令所述任一参数组对应的镜像信号的功率最小的端点设置为中点，并将所述中点的前后两个端点作为边界点，从而得到新的搜索区间；
    步骤5A、所述估计器将所述每一维区间中令所述任一参数组对应的镜像信号的功率最小的端点作为所述任一参数组，从而使得所述单点DFT计算模块计算出新的所述任一参数组对应的镜像信号的功率；
    步骤6A、所述估计器所述新的搜索区间中重复执行步骤2A，直至执行预设的次数，从而得到令所述任一参数组对应的镜像信号的功率最小的所述任一参数组。
  14. 根据权利要求13所述的方法，其中，在所述估计器分别对所述第一参数组、所述第二参数组、所述第三参数组进行计算之前，所述方法还包括：所述估计器确定所述第一参数组、所述第二参数组和所述第三参数组分别对应的初始搜索区间；包括：
    所述估计器通过执行三到五次步骤1A至步骤6A的过程或者通过粒子滤波算法或序列重要性采样SIS方法确定所述第一参数组、所述第二参数组和所述第三参数组分别对应的初始搜索区间。
  15. 一种计算机存储介质，所述存储介质包括一组计算机可执行指令，所述指令用于执行权利要求7-14任一项所述的校准射频收发机的方法。
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