WO2015114780A1 - キャパシタインプット形平滑回路 - Google Patents
キャパシタインプット形平滑回路 Download PDFInfo
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- WO2015114780A1 WO2015114780A1 PCT/JP2014/052122 JP2014052122W WO2015114780A1 WO 2015114780 A1 WO2015114780 A1 WO 2015114780A1 JP 2014052122 W JP2014052122 W JP 2014052122W WO 2015114780 A1 WO2015114780 A1 WO 2015114780A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/2176—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only comprising a passive stage to generate a rectified sinusoidal voltage and a controlled switching element in series between such stage and the output
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
- H02M1/15—Arrangements for reducing ripples from dc input or output using active elements
Definitions
- the present invention relates to a capacitor input type smoothing circuit for shaping a pulsating current formed when converting an alternating current to a direct current.
- a simple smoothing method that has long been used is a method of using a large capacity electrolytic capacitor after rectification. By charging and discharging the capacitor, the valley portion of the pulsating flow is covered by the discharge from the capacitor.
- a power factor improving circuit to which switching technology is applied is used. This mainly controls the current flowing through the coil by switching.
- a smoothing circuit using a large capacity electrolytic capacitor so-called capacitor input type or capacitor input type, charging is performed until the voltage of the pulsating current reaches its peak, and then discharge is repeated when the pulsating voltage decreases.
- the capacitor input type is simple, the number of parts is small and the cost is low.
- the power factor can be improved by the PFC circuit, a complicated circuit configuration is required and the cost is high. Furthermore, a circuit for suppressing noise is also required.
- Japanese Patent Application Laid-Open No. 2005-19266 discloses an invention using a PFC circuit.
- the invention relates to a transformer having a power transformation function and to cause the transformer to transform DC power by on / off control of a switching element.
- the PFC control unit is provided to suppress the harmonic current, there is almost no relation with the present invention.
- the present invention has been made in view of the above-described circumstances, and an object thereof is to embody a capacitor input type smoothing circuit capable of suppressing the power factor as much as possible without reducing the power factor as much as possible. . Another object of the present invention is to reduce the number of parts and to simplify as much as possible, thereby achieving an overwhelming cost reduction.
- the present invention comprises a pulsating current circuit that supplies pulsating current voltage to a load when the capacitor is not discharged, and a control circuit that controls discharging of the capacitor, the control circuit including the pulsating current circuit A smoothing circuit connected in parallel and a voltage detection circuit for detecting its voltage;
- the voltage detection circuit determines a voltage range in which the capacitor is discharged, and detects that the capacitor is in the voltage range, the first switch being disconnected, the second switch being connected to the first switch, the second switch being energized when disconnected, the second switch A third switch connected to the switch and energized when energized is provided,
- the first switch is energized and the second switch and the third switch are disconnected so that capacitor power is not supplied to the load, and
- the discharge voltage of the capacitor is set to a region slightly higher than the lower limit of the voltage required by the load and not higher than the lower limit.
- the basic configuration of the present invention is a general capacitor input type smoothing circuit.
- the control circuit includes a control circuit for controlling the discharge of the capacitor, and the control circuit includes a smoothing circuit connected in parallel with the pulsating current circuit and a voltage detection circuit for detecting the voltage.
- the voltage detection circuit determines a voltage range in which the capacitor is discharged, and detects that the capacitor is in the voltage range, the first switch being disconnected, the second switch being connected to the first switch, the second switch being energized when disconnected, the second switch A third switch connected to the switch and energized when energized is provided.
- the first switch When the pulsating voltage is not in the discharge voltage range of the capacitor, the first switch is energized and the second switch and the third switch are disconnected so that the capacitor power is not supplied to the load, and the discharge voltage of the capacitor Set in the area slightly higher than the lower limit of the voltage required by
- the capacitor input type smoothing circuit of the present invention has a bridge circuit connected to an alternating current power supply and a power line connected to the output end of the bridge circuit, and the power line is a rectified power Branch to three lines that provide direct connection to the capacitor input circuit, voltage detection circuit and load,
- the first branch directly supplies power to the load when the capacitor is not discharged
- the second branch line charges and charges the capacitor when the supplied pulsating current voltage rises
- the third branch line divides the supplied pulsating current and supplies it to the voltage detection circuit
- a backflow prevention element is disposed in the first branch line leading to the load and the second branch line leading to the capacitor, and the remaining third branch line is provided with a voltage detection circuit that determines and detects a voltage range for discharging the capacitor.
- a voltage range for discharging the capacitor is determined, and a first switch to be disconnected upon detection of being in the above voltage range, a second switch connected to the first switch to be energized at the time of the disconnection, A third switch connected and energized at the time of conduction may be provided, and the discharge voltage of the capacitor may be set to match the pulsating voltage with the operation base voltage of the first switch.
- power is mainly supplied from a commercial AC power source, rectified by a bridge circuit, and divided into three: a pulsating current circuit flowing directly to a load, a circuit having a capacitor, and a voltage detection circuit thereof.
- the pulsating current circuit is connected to the first branch line, the circuit having the capacitor is connected to the second branch line, and the voltage detection circuit is connected to the third branch line.
- the first branch line directly supplies power to the load when the capacitor is not discharged
- the second branch line charges and charges the capacitor when the supplied pulsating current voltage rises
- the third branch line divides the supplied pulsating current and supplies it to the voltage detection circuit.
- the first branch to the load supplies power directly to the load when the capacitor of the circuit of the invention is not discharged.
- the capacitor is charged when the supplied pulsating voltage rises.
- a voltage detection circuit As a voltage detection circuit, a voltage range for discharging the capacitor is determined, and a first switch to be disconnected upon detection of being in the above voltage range, a second switch connected to the first switch to be energized at the time of the disconnection, It has a third switch connected and energized when conducting.
- the electronic switch 1 When the voltage detection circuit detects that the voltage is not supplied to the load from the capacitor while charging the capacitor, the electronic switch 1 is energized and the electronic switch 2 connected thereto is disconnected. It becomes. Furthermore, the electronic switch 3 connected to the electronic switch 2 is also disconnected, and the power from the capacitor is not supplied to the load.
- the voltage range for discharging the capacitor may be set to be a region slightly higher than the lower limit of the voltage required by the load and below the voltage.
- the pulsating current voltage can be adjusted to the operation base voltage of the transistor using a voltage dividing resistor or the like.
- the power of the falling time zone of the pulsating voltage is not supplied from the power line, and the falling time zone is also transferred from the capacitor to the load by the voltage detection circuit of the present invention and its control circuit.
- the power supply of the power supply is stopped, and power is supplied from the power line to the load through the bypassed third branch line, so that the problem of lowering the power factor is improved. That is, as soon as the voltage of the pulsating current starts to fall, which is a drawback in the simple capacitor input method, the capacitor starts to discharge, and power in the falling time zone is not supplied from the power line, and the power factor is lowered. Problem will be improved.
- the discharge time is minimized by setting the voltage detection circuit so that power is supplied to the load from the capacitor provided on the second branch line immediately before the voltage reaches the lower limit of the voltage required by the load. As a result, smaller capacitors can be adopted. As a result, the effect of suppressing the power at the time of charging also occurs.
- the discharge of the capacitor is powerful and useful since it starts from the voltage obtained by subtracting the loss from the highest voltage during charging.
- Switching between the power from the power line of the first branch line and the power from the capacitor of the second branch line is performed only twice during one cycle of the pulsating current, and the noise and loss associated with switching are minimized.
- the invention can be made very simple, has a low part count and does not require expensive parts. Therefore, overwhelming cost reduction can be realized as compared with the conventional power factor correction circuit.
- the discharge voltage of the capacitor in a region that is not more than the lower limit of the voltage required by the load, it becomes possible to bury valleys of pulsating current with a smaller amount of charge than a general capacitor. The smaller one is sufficient and the current is small, so the power factor is further improved.
- FIG. 1 is an example 1 in which rectified power is supplied from a commercial AC power line which is an AC power supply 11 through a bridge circuit 12 composed of a diode. Since this is not smooth, although it is direct current, it becomes a pulsating current in which the voltage goes up and down (see FIGS. 2 and 3).
- the pulsating current has a bridge circuit 12 connected to an AC power supply 11 and a power line 13 connected to the output end of the bridge circuit 12, and the power line 13 directly supplies rectified power to a load. It is branched into three lines to the flow circuit 14, the smoothing circuit (or capacitor input circuit) 15 and the voltage detection circuit 16.
- the smoothing circuit (or capacitor input circuit) 15 and the voltage detection circuit 16 constitute a control circuit A1 that controls the discharge of the capacitor. Further, on the upstream side of the capacitor connection point of the pulsating flow circuit 14 leading to the load B and the smoothing circuit 15, diodes are respectively inserted as the backflow prevention elements D1 and D2.
- the first branch line is connected to the pulsating circuit 14 flowing directly through the diode D1 to the load.
- the second branch line is connected to the smoothing circuit 15 flowing through the diode D2 to the capacitor C1.
- the third branch line is connected to the voltage detection circuit 16 which is divided through the resistors R1, R2 and R3 inserted in series in the same order.
- the capacitor C1 In the first branch line, power is directly supplied from the power line to the load B when the capacitor C1 is not discharged. In the second branch line, the capacitor C1 is charged when the voltage of the supplied pulsating current rises. In the third branch line, the voltage of the supplied pulsating current is divided by three resistances.
- the divided voltage of the combined resistance of the resistors R2 and R3 and the resistor R1 is used to drive the base of the transistor Tr2, which is the second switch 18.
- the divided voltage of the combined resistance of the resistors R1 and R2 and the resistor R3 reaches the base voltage of the first switch 17 Tr1, the discharge of the capacitor C1 is stopped.
- the resistors R5 and R6 generate an appropriate voltage for driving the third switch 19 FET1.
- the resistor R6 is inserted in the circuit connecting the second switch 18 and the third switch 19, and the resistor R5 is inserted between the capacitor C1 and the third switch of the smoothing circuit 15 and between the resistor R6 and the third switch 19.
- a field effect transistor is used as the third switch 19. Since the FET 1 is a Pch (P-channel type), current flows from the gate through the resistor R6 when conducting. Generally, since the FET can be driven by a small amount of current and does not want to burden the transistor Tr2, the resistor R6 should be set so that the current does not flow excessively.
- D1, D2 and D3 each indicate a backflow preventing diode.
- the diodes D1 and D2 are necessary in order to not detect an incorrect voltage due to the backflow power from the capacitor C1 at the time of voltage detection of the power from the power line by the resistors R1, R2 and R3.
- the diode D3 is inserted in order to prevent the power flowing through the diode D1 from flowing into the capacitor C1 through the damage preventing diode built in the FET1. In addition, it should be stored that a large current can not flow in the damage prevention diode.
- the voltage supplied from the commercial AC power line is AC 210 V, it is 296 V when converted to DC.
- the resistance R1 is 2.2 M ⁇
- the resistance R2 is 260 K ⁇
- the resistance R3 is 14 K ⁇
- the resistance R4 is 260 K ⁇
- the base voltage of the transistor Tr1 becomes about 0.56 V at around 180 V
- the transistor Tr1 is energized at the border Switch interruptions.
- the capacitor input type smoothing circuit 10 of the present invention having such a configuration, when the transistor Tr1 is energized, the collector voltage of the transistor Tr1 is lowered, the base voltage of the transistor Tr2 connected thereto is lowered, and the transistor Tr2 is It will be interrupted. When the transistor Tr2 is disconnected, the voltage of the gate of the Pch FET1 connected to the collector of the transistor Tr2 is not a negative potential, and the FET1 is disconnected. Therefore, the capacitor C1 is not discharged to the load B.
- the transistor Tr1 When the transistor Tr1 is disconnected, the collector voltage of the transistor Tr1 is increased, the base voltage of the transistor Tr2 connected thereto is also increased, and the transistor Tr2 is energized.
- the transistor Tr2 When the transistor Tr2 is energized, the voltage of the gate of the Pch FET1 connected to the collector of the transistor Tr2 becomes a negative potential, and the FET1 is energized. Thus, the capacitor C1 is discharged to the load.
- the transistor Tr2 should be disconnected at around 0 V of the pulsating current voltage, but in fact the transistor has a little capacitance at the base like an FET, so that the residual power of the transistor Tr2 is energized. Since the field effect transistor FET1 of the third switch can conduct even a weak current, no practical problem occurs even if the transistor Tr2 of the second switch is half open.
- the capacitor C2 of an appropriate capacity is additionally connected to the collector of the transistor Tr1 and the base of the transistor Tr2 to secure conduction. Thereby, the conduction of the transistor Tr2 can be maintained at around 0 V of the pulsating current voltage.
- the other configuration of the example 2 including the control circuit A2 may be the same as that of the example 1, and thus the detailed description will be omitted.
- FIG. 3 shows the input voltage from the power line, the voltage applied to the load, and the charge / discharge amount of the current of the capacitor C1 along with the time axis when smoothed by the conventional simple capacitor input method.
- the voltage is shown at the top and the current at the bottom.
- Vsen When the voltage of the pulsating current from the power line reaches Vsen, current flows into the capacitor C1 and is charged. Charging continues until the voltage of the pulsating current reaches the apex Vmax. At the same time, power to the load is supplied from the power line. Thereafter, when the voltage of the pulsating current starts to drop below Vmax, a current is discharged from the capacitor C1. At the same time, power to the load is supplied from the capacitor C1.
- the time supplied from the power line is between T1 and T2, and the other time periods are supplied from the capacitor C1.
- the voltage of the pulsating current from the power line goes down, although the voltage is still high, the power is not used and becomes reactive power, and it is understood that the power factor is low.
- FIG. 4 shows the input voltage from the power line, the voltage applied to the load, and the charge / discharge amount of the current of the capacitor C1 along with the time axis in the capacitor input type smoothing circuit 10 of the present invention.
- the voltage is shown at the top and the current at the bottom.
- Vsen When the voltage of the pulsating current from the power line reaches Vsen, current flows into the capacitor C1 and is charged. Charging continues until the voltage of the pulsating current reaches the apex Vmax. At the same time, power to the load is supplied from the power line.
- the current is described as a positive value when the capacitor is charged, and a negative value when the capacitor is discharged.
- the capacitor input type smoothing circuit 10 of the present invention when the pulsating current is a voltage higher than Vsen, the capacitor C1 is set so as not to discharge. At the same time, power to the load B is supplied from the power line. Furthermore, after that, when the voltage of the pulsating current becomes lower than Vsen, the electronic switch FET1 becomes conductive, and the capacitor supplies power to the load. At the same time, the voltage applied to the load B starts from a value obtained by subtracting the loss from the highest voltage Vmax received by the capacitor C1 during charging, and gradually drops.
- the time supplied from the power line is between T1 and T3, and the other time periods are supplied from the capacitor C1.
- Power is supplied from the power line in a region above the lower limit Vsen of the voltage required by the load B.
- the load B uses the power from the capacitor C1 in the time periods other than T1 to T3 in the other smoothing circuits as well.
- the capacitor input type smoothing circuit 10 of the present invention As described above, according to the capacitor input type smoothing circuit 10 of the present invention, the time zone supplied from the power line to the load is better in the capacitor input type smoothing circuit 10 of the present invention than in the simple capacitor input method. Is very long. Also from this, it can be said that the power factor is improved by the present invention.
- the above is a basic description of the capacitor input type smoothing circuit according to the present invention.
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Abstract
Description
このようにキャパシタインプット形は、簡易であるため部品数も少なく、低コストである。その反面、力率の問題があり、PFC回路により力率は改善され得るものの、複雑な回路構成が必要で高コストとなる。さらに、ノイズを抑えるための回路も必要となる。
電圧検知回路はキャパシタを放電させる電圧域を決定し、かつ、電圧域にあることを検知して不通となる第1スイッチ、第1スイッチと接続されその不通時に通電となる第2スイッチ、第2スイッチと接続されその通電時に通電となる第3スイッチを具備し、
脈流電圧がキャパシタの放電電圧域にないとき、第1スイッチが通電、第2スイッチ及び第3スイッチは不通としてキャパシタ電力が負荷へ供給されないようにするとともに、
上記キャパシタの放電電圧として、負荷が必要とする電圧の下限よりもやや高く、かつ、それ以上ではない領域に設定するという手段を講じたものである。
第1分岐線はキャパシタの非放電時に直接負荷へ電力を供給し、
第2分岐線は供給された脈流電圧の上昇時にキャパシタへ電力を供給して充電し、
第3分岐線は供給された脈流電圧を分圧して電圧検知回路に供給するものとされ、
負荷に通じる第1分岐線及びキャパシタに通じる第2分岐線に逆流防止素子を配置し、残る第3分岐線にはキャパシタを放電させる電圧域を決定し検知する電圧検知回路を設け、
電圧検知回路としてキャパシタを放電させる電圧域を決定し、上記電圧域にあることを検知して不通となる第1スイッチ、第1スイッチと接続されその不通時に通電する第2スイッチ、第2スイッチに接続されその導通時に通電する第3スイッチを具備し、上記キャパシタの放電電圧として、脈流電圧が第1スイッチの作動ベース電圧に合わせるように設定するという構成を取ることができる。
第2分岐線は供給された脈流電圧の上昇時にキャパシタへ電力を供給して充電し、
第3分岐線は供給された脈流電圧を分圧して電圧検知回路に供給する。
(合成抵抗)274KΩ=(R2)260KΩ+(R3)14KΩ、
(合成抵抗)133KΩ=(R2+R3)274KΩと(R4)260KΩの並列、
(合成抵抗)2333KΩ=(R1)2200KΩ+133KΩ、
180V時、抵抗R1に流れる電流は、約80uA=180V/2333KΩ、
抵抗R2、R4には、ほぼ半分分流するとして、約40μAずつとなる。
抵抗R3にも約40μA流れるとして、トランジスタTr1のベース電圧は、約0.56V=14KΩ×40μA、
となる。
11 交流電源
12 ブリッジ回路
13 電力線
14 脈流回路
15 キャパシタインプット回路(平滑回路)
16 電圧検知回路
17 第1スイッチ
18 第2スイッチ
19 第3スイッチ
A1、A2 制御回路
B 負荷
C1、C2 キャパシタ
D1、D2、D3 ダイオード
FET1 電界効果トランジスタ
R1、R2、R3、R4、R5、R6 抵抗
Tr1、Tr2 トランジスタ
Claims (3)
- キャパシタの非放電時に脈流電圧を負荷へ供給する脈流回路と、キャパシタの放電を制御する制御回路を備え、上記制御回路は、脈流回路と並列接続された平滑回路とその電圧を検知する電圧検知回路を具備し、
電圧検知回路はキャパシタを放電させる電圧域を決定し、かつ、電圧域にあることを検知して不通となる第1スイッチ、第1スイッチと接続されその不通時に通電となる第2スイッチ、第2スイッチと接続されその通電時に通電となる第3スイッチを具備し、
脈流電圧がキャパシタの放電電圧域にないとき、第1スイッチが通電、第2スイッチ及び第3スイッチは不通としてキャパシタ電力が負荷へ供給されないようにするとともに、
上記キャパシタの放電電圧として、負荷が必要とする電圧の下限よりもやや高く、かつ、それ以上ではない領域に設定された
キャパシタインプット形平滑回路。 - スイッチング電源方式により交流を直流に変換する際に発生する脈流を平滑化するためのキャパシタインプット形平滑回路であって、
交流電源に接続されたブリッジ回路と、上記ブリッジ回路の出力端に接続された電力線とを有するとともに、上記電力線は整流された電力を負荷へ直接接続供給する脈流回路、キャパシタインプット回路及び電圧検知回路に通じる三つの線に分岐し、
第1分岐線はキャパシタの非放電時に直接負荷へ電力を供給し、
第2分岐線は供給された脈流電圧の上昇時にキャパシタへ電力を供給して充電し、
第3分岐線は供給された脈流電圧を分圧して電圧検知回路に供給するものとされ、
負荷に通じる第1分岐線及びキャパシタに通じる第2分岐線に逆流防止素子を配置し、残る第3分岐線にはキャパシタを放電させる電圧域を決定し検知する電圧検知回路を設け、
電圧検知回路としてキャパシタを放電させる電圧域を決定し、上記電圧域にあることを検知して不通となる第1スイッチ、第1スイッチと接続されその不通時に通電する第2スイッチ、第2スイッチに接続されその導通時に通電する第3スイッチを具備し、上記キャパシタの放電電圧として、脈流電圧が第1スイッチの作動ベース電圧に合わせるように設定された
キャパシタインプット形平滑回路。 - 脈流電圧の0V付近における、第2スイッチの通電を保持するために、キャパシタを第1スイッチのコレクタ、第2スイッチのベースに追加接続するようにした
請求項2記載のキャパシタインプット形平滑回路。
Priority Applications (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US14/378,390 US9467062B2 (en) | 2014-01-30 | 2014-01-30 | Capacitor input type smoothing circuit |
CA2862893A CA2862893A1 (en) | 2014-01-30 | 2014-01-30 | Capacitor input type smoothing circuit |
JP2014552438A JP5882500B2 (ja) | 2014-01-30 | 2014-01-30 | キャパシタインプット形平滑回路 |
PCT/JP2014/052122 WO2015114780A1 (ja) | 2014-01-30 | 2014-01-30 | キャパシタインプット形平滑回路 |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
PCT/JP2014/052122 WO2015114780A1 (ja) | 2014-01-30 | 2014-01-30 | キャパシタインプット形平滑回路 |
Publications (1)
Publication Number | Publication Date |
---|---|
WO2015114780A1 true WO2015114780A1 (ja) | 2015-08-06 |
Family
ID=53756392
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/JP2014/052122 WO2015114780A1 (ja) | 2014-01-30 | 2014-01-30 | キャパシタインプット形平滑回路 |
Country Status (4)
Country | Link |
---|---|
US (1) | US9467062B2 (ja) |
JP (1) | JP5882500B2 (ja) |
CA (1) | CA2862893A1 (ja) |
WO (1) | WO2015114780A1 (ja) |
Families Citing this family (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP6814219B2 (ja) * | 2016-08-30 | 2021-01-13 | ヌヴォトンテクノロジージャパン株式会社 | スイッチング電源装置および半導体装置 |
CN110505728B (zh) * | 2018-05-17 | 2022-05-10 | 朗德万斯公司 | 降压转换器 |
Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2005019266A (ja) * | 2003-06-27 | 2005-01-20 | Tabuchi Electric Co Ltd | 高調波電流抑制回路を備えた放電ランプ用電源回路 |
JP2013143122A (ja) * | 2012-01-11 | 2013-07-22 | Gcomm Corp | 直流電源装置 |
Family Cites Families (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US6998786B2 (en) * | 2004-02-04 | 2006-02-14 | Yih-Fang Chiou | Control circuit of electronic ballast for fluorescent lamp |
JP4254884B2 (ja) * | 2007-05-01 | 2009-04-15 | サンケン電気株式会社 | 力率改善回路 |
JP2011205746A (ja) * | 2010-03-24 | 2011-10-13 | Aisin Aw Co Ltd | 放電制御装置 |
KR101187189B1 (ko) * | 2012-03-07 | 2012-10-02 | 유상우 | 효율 개선 기능을 가진 엘이디 구동회로 |
-
2014
- 2014-01-30 WO PCT/JP2014/052122 patent/WO2015114780A1/ja active Application Filing
- 2014-01-30 CA CA2862893A patent/CA2862893A1/en not_active Abandoned
- 2014-01-30 US US14/378,390 patent/US9467062B2/en not_active Expired - Fee Related
- 2014-01-30 JP JP2014552438A patent/JP5882500B2/ja not_active Expired - Fee Related
Patent Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2005019266A (ja) * | 2003-06-27 | 2005-01-20 | Tabuchi Electric Co Ltd | 高調波電流抑制回路を備えた放電ランプ用電源回路 |
JP2013143122A (ja) * | 2012-01-11 | 2013-07-22 | Gcomm Corp | 直流電源装置 |
Also Published As
Publication number | Publication date |
---|---|
US9467062B2 (en) | 2016-10-11 |
CA2862893A1 (en) | 2015-07-30 |
JP5882500B2 (ja) | 2016-03-09 |
JPWO2015114780A1 (ja) | 2017-03-23 |
US20160204715A1 (en) | 2016-07-14 |
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