WO2015070820A1 - 扩频信号的生成方法、生成装置、接收方法和接收装置 - Google Patents

扩频信号的生成方法、生成装置、接收方法和接收装置 Download PDF

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Publication number
WO2015070820A1
WO2015070820A1 PCT/CN2014/093023 CN2014093023W WO2015070820A1 WO 2015070820 A1 WO2015070820 A1 WO 2015070820A1 CN 2014093023 W CN2014093023 W CN 2014093023W WO 2015070820 A1 WO2015070820 A1 WO 2015070820A1
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Prior art keywords
spread spectrum
spectrum signal
signal component
component
code
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PCT/CN2014/093023
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English (en)
French (fr)
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姚铮
陆明泉
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清华大学
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Priority to NZ72128114A priority Critical patent/NZ721281A/en
Application filed by 清华大学 filed Critical 清华大学
Priority to CA2929182A priority patent/CA2929182C/en
Priority to JP2016536544A priority patent/JP6511676B2/ja
Priority to US14/436,456 priority patent/US10027371B2/en
Priority to RU2016125550A priority patent/RU2658625C1/ru
Priority to CN201480060796.8A priority patent/CN105765872B/zh
Priority to AU2014350696A priority patent/AU2014350696B2/en
Priority to BR112016011639-9A priority patent/BR112016011639B1/pt
Priority to KR1020167017774A priority patent/KR101906692B1/ko
Priority to EP14861561.0A priority patent/EP3079264B1/en
Publication of WO2015070820A1 publication Critical patent/WO2015070820A1/zh
Priority to US14/817,391 priority patent/US9287922B1/en
Priority to HK16110122.2A priority patent/HK1222050A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/69—Spread spectrum techniques
    • H04B1/707—Spread spectrum techniques using direct sequence modulation
    • H04B1/7073—Synchronisation aspects
    • H04B1/7087—Carrier synchronisation aspects
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S1/00—Beacons or beacon systems transmitting signals having a characteristic or characteristics capable of being detected by non-directional receivers and defining directions, positions, or position lines fixed relatively to the beacon transmitters; Receivers co-operating therewith
    • G01S1/02—Beacons or beacon systems transmitting signals having a characteristic or characteristics capable of being detected by non-directional receivers and defining directions, positions, or position lines fixed relatively to the beacon transmitters; Receivers co-operating therewith using radio waves
    • G01S1/04—Details
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S19/00—Satellite radio beacon positioning systems; Determining position, velocity or attitude using signals transmitted by such systems
    • G01S19/01—Satellite radio beacon positioning systems transmitting time-stamped messages, e.g. GPS [Global Positioning System], GLONASS [Global Orbiting Navigation Satellite System] or GALILEO
    • G01S19/02—Details of the space or ground control segments
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S19/00—Satellite radio beacon positioning systems; Determining position, velocity or attitude using signals transmitted by such systems
    • G01S19/01—Satellite radio beacon positioning systems transmitting time-stamped messages, e.g. GPS [Global Positioning System], GLONASS [Global Orbiting Navigation Satellite System] or GALILEO
    • G01S19/13—Receivers
    • G01S19/24—Acquisition or tracking or demodulation of signals transmitted by the system
    • G01S19/30—Acquisition or tracking or demodulation of signals transmitted by the system code related
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/69—Spread spectrum techniques
    • H04B1/707—Spread spectrum techniques using direct sequence modulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J13/00—Code division multiplex systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J13/00—Code division multiplex systems
    • H04J13/0003—Code application, i.e. aspects relating to how codes are applied to form multiplexed channels
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
    • H04L27/22—Demodulator circuits; Receiver circuits

Definitions

  • the present application relates to a method for generating a spread spectrum signal, a generating device, a receiving method, and a receiving device.
  • the signals of the Global Navigation Satellite System are all Direct Sequence Spread Spectrum (DSSS) technology is used.
  • BOC modulation In order to make a variety of signals better share the limited frequency band of GNSS, and further improve the range measurement accuracy and anti-interference performance of the signal, new signal modulation methods are continuously presented.
  • BOC modulation This modulation method is implemented by multiplying the signal by a subcarrier in the form of a square wave based on the DSSS modulation of the rectangular non-return-to-zero spread spectrum chip.
  • BOC modulation has two parameters: subcarrier frequency f s and spreading sequence frequency f c , where f s ⁇ f c , so the specific modulation mode of BOC can be recorded as BOC(f s , f c ).
  • An object of the present application is to provide a method, a generating device, a receiving method, and a receiving device for generating a spread spectrum signal.
  • a method for generating a spread spectrum signal includes: generating a first spread spectrum signal component and a second spread spectrum signal component, wherein the first spread spectrum signal component and the second The spread spectrum signal components each include a spreading code and a binary subcarrier, the first spread spectrum signal component and the second spread spectrum signal component have the same spreading code, the first spread spectrum signal component and the second The binary subcarriers of the spread spectrum signal component are different; the first spread spectrum is to be And modulating the signal component and the second spread spectrum signal component to a radio frequency carrier to generate a spread spectrum signal, wherein modulating a phase of the radio frequency carrier of the first spread spectrum signal component and modulating a radio frequency carrier of the second spread spectrum signal component The phase difference is different, and the generated spread spectrum signal is:
  • S RF represents a spread spectrum signal
  • S 1 and S 2 represent a first spread spectrum signal component and a second spread spectrum signal component, respectively
  • a 1 and A 2 represent amplitudes of S 1 and S 2 , respectively
  • c(t) represents The spreading codes of S 1 and S 2
  • q 1 (t) and q 2 (t) represent binary subcarriers of S 1 and S 2 , respectively
  • d(t) represents teletext data
  • ⁇ RF represents the angular frequency of the radio frequency carrier
  • ⁇ represents the phase difference between the modulated RF carrier phase S 1 and of S 2.
  • a device for generating a spread spectrum signal includes: a spread spectrum signal component generating unit that generates a first spread spectrum signal component and a second spread spectrum signal component, wherein the first spread The frequency signal component and the second spread spectrum signal component each include a spreading code and a binary subcarrier, and the first spread spectrum signal component and the second spread spectrum signal component have the same spreading code, the first spread The frequency signal component is different from the binary subcarrier of the second spread spectrum signal component; and the spread spectrum signal generating unit modulates the first spread spectrum signal component and the second spread spectrum signal component to a radio frequency carrier to generate an extension a frequency signal, wherein a phase of a radio frequency carrier modulating the first spread spectrum signal component is different from a phase of a radio frequency carrier modulating the second spread spectrum signal component, wherein the spread spectrum signal generating unit generates an extension by: Frequency signal:
  • S RF represents a spread spectrum signal
  • S 1 and S 2 represent a first spread spectrum signal component and a second spread spectrum signal component, respectively
  • a 1 and A 2 represent amplitudes of S 1 and S 2 , respectively
  • c(t) represents The spreading codes of S 1 and S 2 , q 1 (t) and q 2 (t) represent binary subcarriers of S 1 and S 2 , respectively
  • d(t) represents teletext data
  • ⁇ RF represents the angular frequency of the radio frequency carrier
  • ⁇ represents the phase difference between the phases of the radio frequency carriers modulating S 1 and S 2 .
  • a method for receiving a spread spectrum signal includes: generating a spread code local reproduction code of the spread spectrum signal; generating a binary subcarrier local of the first spread spectrum signal component a replica code and a binary subcarrier of the second spread spectrum signal component a recurring code; generating a local carrier according to a phase difference between a phase of a radio frequency carrier modulating the first spread spectrum signal component and a phase of a radio frequency carrier modulating the second spread spectrum signal component; generating a local carrier according to the generated a spreading code local reproduction code, a binary subcarrier local reproduction code of the first spread spectrum signal component, and a binary subcarrier local reproduction code of the second spread spectrum signal component, performing coherent integration on the received spread spectrum signal The operation is performed and the operation results are linearly combined to obtain an integral in-phase branch component and an integral quadrature branch component.
  • a receiver for receiving a spread spectrum signal includes: a baseband signal generating unit that generates a spread code local reproduction code of the spread spectrum signal to generate the first spread spectrum signal a binary subcarrier local reproduction code of the component and a binary subcarrier local reproduction code of the second spread spectrum signal component; a local carrier generating unit, according to a phase and a modulation scheme of the radio frequency carrier modulating the first spread spectrum signal component a phase difference between phases of the radio frequency carrier of the second spread spectrum signal component to generate a local carrier; and an operation unit, according to the generated local carrier, the spread code local reproduction code, and the binary subcarrier of the first spread spectrum signal component a local recurring code and a binary subcarrier local reproduction code of the second spread spectrum signal component, performing coherent integration operations on the received spread spectrum signal, and linearly combining the operation results to obtain an integral in-phase branch component and an integral Orthogonal branch component.
  • FIG. 1 shows a flow chart of a method of generating a spread spectrum signal according to an embodiment of the present application.
  • FIG. 2 shows a schematic block diagram of a device for generating a spread spectrum signal according to an embodiment of the present application.
  • FIG. 3 shows a schematic block diagram of a device for generating a spread spectrum signal according to another embodiment of the present application.
  • FIG. 4 shows a schematic block diagram of a spread spectrum signal receiver in accordance with an embodiment of the present application.
  • FIG. 5 shows a schematic diagram of a specific implementation of a spread spectrum signal receiver according to an embodiment of the present application.
  • FIG. 6 shows a flow chart of a method of receiving a spread spectrum signal according to an embodiment of the present application.
  • Figure 1 shows a flowchart of a method of generating a spread spectrum signal S RF in accordance with an embodiment of the present disclosure.
  • a first spread spectrum signal component S 1 and a second spread spectrum signal component S 2 are generated, wherein the first spread spectrum signal component S 1 and the second spread spectrum signal component S 2 both comprise a spreading code and a binary
  • the subcarriers, the spreading codes of the first spread spectrum signal component S 1 and the second spread spectrum signal component S 2 are the same, and the binary subcarriers of the first spread spectrum signal component S 1 and the second spread spectrum signal component S 2 are different.
  • step 120 the first spread spectrum signal component S 1 and the second spread spectrum signal component S 2 are modulated onto a radio frequency carrier to generate a spread spectrum signal S RF , wherein the radio frequency carrier of the first spread spectrum signal component S 1 is modulated
  • the phase is different from the phase of the radio frequency carrier modulating the second spread spectrum signal component S 2 .
  • the two spread spectrum signal components including the spreading code and the binary subcarrier are separately modulated on different phases of the carrier, thereby realizing multiplexing of the spread spectrum signal components.
  • the spread spectrum signal S RF generated in step 120 is:
  • S 1 and S 2 represent the first spread spectrum signal component and the second spread spectrum signal component, respectively
  • a 1 and A 2 represent the amplitudes of S 1 and S 2 , respectively
  • c(t) represents the expansion of S 1 and S 2 .
  • the frequency code, q 1 (t) and q 2 (t) represent the binary subcarriers of S 1 and S 2 , respectively
  • d(t) represents the teletext data
  • ⁇ RF represents the angular frequency of the radio frequency carrier
  • ⁇ represents the modulation S 1 and S The phase difference between the RF carrier phases of 2 .
  • the binary subcarrier is a binary coded symbol (BCS) subcarrier.
  • the subcarrier of the first spread spectrum signal component S 1 may be BCS ([1 1 1 1 -1 1 1 1 1], 1)
  • the subcarrier of the second spread spectrum signal component S 2 may be BCS ([1 1 1 1 1 -1 1 1 1 1], 1), etc.
  • BCS subcarriers herein are merely illustrative and that the binary subcarriers of the spread spectrum signal components may be any form of BCS subcarriers.
  • the binary subcarrier is a binary offset carrier BOC subcarrier, BOC(m, n).
  • n is the frequency f c of the spreading code c(t) in the BOC signal is The result of normalization at 1.023 MHz.
  • the subcarrier of the first spread spectrum signal component S 1 may be BOC (1, 1)
  • the subcarrier of the second spread spectrum signal component S 2 may be BOC (6, 1).
  • BOC(1,1) and BOC(6,1) herein are merely illustrative, and the binary subcarrier of the spread spectrum signal component may be any form of BOC subcarrier.
  • the binary subcarrier is a subcarrier BOC binary offset carrier
  • spread spectrum signal component S 1 and S 2 are binary offset carrier signal BOC. It can be understood that multiplexing of two binary offset carrier BOC signals is achieved at this time.
  • two signal components are separately modulated on different phases of a carrier. Such an implementation enables a flexible adjustment of the proportion of the intermodulation components between the two different BOC signal components in the total signal.
  • the performance of the signal during acquisition, tracking, demodulation, anti-multipath, etc. is highly dependent on the spectral characteristics of the signal.
  • the size of the intermodulation component between the two signal components affects the acquisition, tracking, demodulation, and multipath resistance at the time of reception.
  • the phase difference ⁇ may be further set to adjust an intermodulation component between the first spread spectrum signal component S 1 and the second spread spectrum signal component S 2 .
  • the characteristics of the transmitted signal can be adjusted for specific requirements to facilitate acquisition, tracking, demodulation, and multipath performance at the time of reception.
  • the baseband signal can be regarded as
  • R 1 and R 2 are the autocorrelation function of c(t)q 1 (t) and the autocorrelation function of c(t)q 2 (t), respectively, and R c ( ⁇ ) is c(t)q 1 ( t) A cross-correlation function with c(t)q 2 (t). It can be seen that, in the autocorrelation function of the baseband signal, in addition to the autocorrelation function including the first spread spectrum signal component and the autocorrelation function of the second spread spectrum signal component, the first spread spectrum signal component and the second The cross-correlation function of the spread spectrum signal component, which is the intermodulation component mentioned above.
  • phase difference ⁇ By setting the phase difference ⁇ , cos ⁇ can be taken to any value between -1 and +1, thereby changing the size of the intermodulation component.
  • the value of the phase difference ⁇ may be determined according to a demodulation performance index ⁇ and a tracking performance index ⁇ required when receiving a spread spectrum signal.
  • the demodulation performance index ⁇ when receiving the spread spectrum signal refers to the power attenuation introduced by the spread spectrum signal through the filter processing of the transmitter, and the demodulation performance index ⁇ directly affects the correlator output signal-to-noise ratio of the receiver.
  • the tracking performance index ⁇ refers to the root mean square bandwidth of the spread spectrum signal filtered by the transmitter, and the tracking performance index ⁇ affects the error of the tracking loop under thermal noise and multipath.
  • the demodulation performance index ⁇ and the tracking performance index ⁇ can be expressed by the following formula:
  • BW is the bandwidth of the signal transmitter
  • n 0 is a bilateral Gaussian white noise power spectral density
  • a 1 and A 2 represent the first spread spectrum signal component S 1 and the second spread spectrum signal component S 2 , respectively.
  • the amplitude, R 1 represents the autocorrelation function of the product of the spreading code of S 1 and the binary subcarrier c(t)q 1 (t)
  • R 2 represents the product of the spreading code of S 2 and the binary subcarrier c(t)
  • the autocorrelation function of q 2 (t), R c ( ⁇ ) is a cross-correlation function of c(t)q 1 (t) and c(t)q 2 (t).
  • the multipath performance of the signal is related to the tracking performance indicator ⁇ .
  • the set phase difference ⁇ takes the value ⁇ k-opt .
  • phase difference ⁇ ⁇ ⁇ / 2 may be provided to the phase difference ⁇ ⁇ ⁇ / 2, in order to adjust a first spread spectrum signal component S. 1 and the second spread spectrum signal component S 2 between the intermodulation products is zero.
  • the baseband signal when the phase difference ⁇ is ⁇ /2, the baseband signal can be written as
  • the autocorrelation function of the baseband signal is a
  • the autocorrelation function of the baseband signal does not include the intermodulation component.
  • different message data can be carried on the two signal components to increase the amount of information transmitted by the signal.
  • the spread spectrum signal generating apparatus 200 includes a spread spectrum signal component generating unit 210 and a spread spectrum signal generating unit 220.
  • the spread spectrum signal component generating unit 210 generates a first spread spectrum signal component and a second spread spectrum signal component.
  • the first spread spectrum signal component and the second spread spectrum signal component both include a spreading code and a binary subcarrier.
  • the first spread spectrum signal component and the second spread spectrum signal component have the same spreading code, and the first spread spectrum signal component It is different from the binary subcarrier of the second spread spectrum signal component.
  • the spread spectrum signal generating unit 220 modulates the first spread spectrum signal component and the second spread spectrum signal component to a radio frequency carrier to generate a spread spectrum signal.
  • the phase of the radio frequency carrier modulating the first spread spectrum signal component is different from the phase of the radio frequency carrier modulating the second spread spectrum signal component.
  • the spread spectrum signal generating unit 220 generates the spread spectrum signal S RF by :
  • S 1 and S 2 represent the first spread spectrum signal component and the second spread spectrum signal component, respectively
  • a 1 and A 2 represent the amplitudes of S 1 and S 2 , respectively
  • c(t) represents the expansion of S 1 and S 2 .
  • the frequency code, q 1 (t) and q 2 (t) represent the binary subcarriers of S 1 and S 2 , respectively
  • d(t) represents the teletext data
  • ⁇ RF represents the angular frequency of the radio frequency carrier
  • ⁇ represents the modulation S 1 and S The phase difference between the RF carrier phases of 2 .
  • FIG. 3 shows a schematic block diagram of a device for generating a spread spectrum signal according to another embodiment of the present application.
  • the spread spectrum signal generating unit 220 of the spread spectrum signal generating apparatus 200 may further include a phase difference setting module 221 and a signal generating module 222.
  • the phase difference setting module 221 sets a phase difference ⁇ between the radio frequency carrier phases of the modulated first spread spectrum signal component S 1 and the second spread spectrum signal component S 2 to adjust the first spread spectrum signal component S 1 and the second The intermodulation component between the spread spectrum signal components S 2 .
  • the signal generation module 222 generates the spread spectrum signal S RF according to the phase difference ⁇ set by the phase difference setting module 221.
  • the signal generation module 222 generates the spread spectrum signal S RF according to the phase difference ⁇ set by the phase difference setting module 221 by:
  • S 1 and S 2 represent the first spread spectrum signal component and the second spread spectrum signal component, respectively
  • a 1 and A 2 represent the amplitudes of S 1 and S 2 , respectively
  • c(t) represents the expansion of S 1 and S 2 .
  • the frequency code, q 1 (t) and q 2 (t) represent the binary subcarriers of S 1 and S 2 , respectively
  • d(t) represents the teletext data
  • ⁇ RF represents the angular frequency of the radio frequency carrier
  • ⁇ represents the modulation S 1 and S The phase difference between the RF carrier phases of 2 .
  • the phase difference setting module 221 can determine the value of the phase difference ⁇ according to the demodulation performance index and the tracking performance index required when receiving the spread spectrum signal.
  • the phase difference setting module 221 may set the phase difference ⁇ between the radio frequency carrier phases of the first spread spectrum signal component S 1 and the second spread spectrum signal component S 2 to ⁇ /2 to adjust the first The intermodulation component between a spread spectrum signal component S 1 and the second spread spectrum signal component S 2 is zero.
  • the phase difference setting module 221 may further set the phase difference ⁇ to an arbitrary value such that cos ⁇ takes an arbitrary value between ⁇ 1 and +1, thereby changing the first spread spectrum signal component S 1 and the second spread spectrum signal component S 2 .
  • embodiments of the present application described above focus on the transmitting end, that is, the method and apparatus for generating a spread spectrum signal.
  • embodiments of the present application also relate to signals generated by a generating method such as the above-described spread spectrum signal and a generating device.
  • embodiments of the present application are also directed to systems, methods and apparatus for processing spread spectrum signals such as those described above.
  • the receiver 300 includes a baseband signal generating unit 310, a local carrier generating unit 320, and an arithmetic unit 330. Receiver 300 can process the received spread spectrum signal
  • Baseband signal generating unit 310 generates a spread spectrum signal Spreading code local reproduction code And generating a binary subcarrier local reproduction code of the first spread spectrum signal component And a binary subcarrier local reproduction code of the second spread spectrum signal component
  • the local carrier generation unit 320 generates a local carrier based on the phase difference ⁇ between the phase of the radio frequency carrier modulating the first spread spectrum signal component and the phase of the radio frequency carrier modulating the second spread spectrum signal component.
  • the operation unit 330 generates a spreading code local reproduction code according to the local carrier generated by the local carrier generating unit 320 and according to the baseband signal generating unit 310.
  • Binary subcarrier local reproduction code of the first spread spectrum signal component And a binary subcarrier local reproduction code of the second spread spectrum signal component
  • a coherent integration operation is performed, and the operation results are linearly combined to obtain an integral in-phase branch component I and an integral quadrature branch component Q.
  • FIG. 5 shows a schematic diagram of a specific implementation of a spread spectrum signal receiver according to an embodiment of the present application.
  • the baseband signal generating unit 310 further includes a spreading code local replica code generating module 311 and a subcarrier local replica code generating module 312.
  • the spreading code local replica code generation module 311 generates a spread spectrum signal Spreading code local reproduction code
  • the subcarrier local replica code generation module 312 generates a binary subcarrier local replica code of the first spread spectrum signal component. And a binary subcarrier local reproduction code of the second spread spectrum signal component
  • the local carrier generation unit 320 further includes a local carrier generation module 321.
  • the local carrier generation module 321 generates a local carrier according to a phase difference ⁇ between a phase of a radio frequency carrier modulating the first spread spectrum signal component and a phase of a radio frequency carrier modulating the second spread spectrum signal component. among them, Indicates the demodulation angle frequency of the local carrier. It can be understood that if the received spread spectrum signal is directly demodulated, If the spread spectrum signal that has been converted to the intermediate frequency by the down converter is demodulated, among them, It is the carrier IF after passing the down converter.
  • the arithmetic unit 330 further includes a coherent integration calculation module 331 and a linear combination calculation module 332.
  • the coherent integration calculation module 331 is based on the local carrier generated by the local carrier generation unit 320. And according to the spreading code local reproduction code generated by the baseband signal generating unit 310 Binary subcarrier local reproduction code of the first spread spectrum signal component And a binary subcarrier local reproduction code of the second spread spectrum signal component For the received spread spectrum signal Perform a coherent integration operation.
  • the specific coherent integration process is as follows:
  • the linear combination calculation module 332 performs a line on the operation result of the coherent integration calculation module 331 The combination is obtained to obtain an integral in-phase branch component I and an integral quadrature branch component Q.
  • the receiver 300 may further include a processing unit 340 that performs carrier synchronization, code timing synchronization, according to the obtained integrated in-phase branch component and integral orthogonal branch component, Extraction of data demodulation, ranging code phase and carrier phase measurements.
  • a processing unit 340 that performs carrier synchronization, code timing synchronization, according to the obtained integrated in-phase branch component and integral orthogonal branch component, Extraction of data demodulation, ranging code phase and carrier phase measurements.
  • step 410 a spreading code local reproduction code of the spread spectrum signal is generated.
  • step 420 a binary subcarrier local replica code of the first spread spectrum signal component and a binary subcarrier local replica code of the second spread spectrum signal component are generated.
  • a local carrier is generated based on a phase difference between a phase of a radio frequency carrier modulating the first spread spectrum signal component and a phase of a radio frequency carrier modulating the second spread spectrum signal component.
  • step 440 according to the generated local carrier, the spreading code local recurring code, the binary subcarrier local recurring code of the first spread spectrum signal component, and the binary subcarrier local recurring code of the second spread spectrum signal component, Coherent integration operations are performed on the received spread spectrum signals, and the operation results are linearly combined to obtain an integrated in-phase branch component and an integrated quadrature branch component.
  • the coherent integration operation in step 440 is implemented by the following formula:
  • the method for receiving a spread spectrum signal may further include performing carrier synchronization, code timing synchronization, data demodulation, and ranging code according to the obtained integrated in-phase branch component and integral orthogonal branch component.
  • the step of extracting the phase and carrier phase measurements It can be understood that those skilled in the art can perform carrier synchronization, code timing synchronization, data demodulation, ranging code phase and carrier phase according to the integrated in-phase branch component and the integrated orthogonal branch component by various methods in the prior art. Extraction of measured values.
  • Embodiments in accordance with the present application may be implemented in the form of hardware, software, or a combination thereof.
  • One aspect of the present application provides a computer program comprising a method for generating a spread spectrum signal, a method of receiving a spread spectrum signal, and a receiver executable instruction for implementing an embodiment in accordance with the present application.
  • such computer programs can be stored using any form of memory, such as an optical or magnetic readable medium, chip, ROM, PROM, or other volatile or nonvolatile device.
  • a machine readable memory storing such a computer program is provided.

Abstract

本申请提出了一种扩频信号的生成方法、生成装置、接收方法和接收装置。扩频信号的生成方法包括生成第一扩频信号分量和第二扩频信号分量，其中，所述第一扩频信号分量和所述第二扩频信号分量均包含扩频码和二进制副载波，所述第一扩频信号分量和所述第二扩频信号分量的扩频码相同，所述第一扩频信号分量和所述第二扩频信号分量的二进制副载波不同；将所述第一扩频信号分量和所述第二扩频信号分量调制到射频载波以生成扩频信号，其中，调制所述第一扩频信号分量的射频载波的相位与调制所述第二扩频信号分量的射频载波的相位不同。

Description

扩频信号的生成方法、生成装置、接收方法和接收装置 技术领域
本申请涉及扩频信号的生成方法、生成装置、接收方法和接收装置。
背景技术
为了利用扩频码中频繁的相位翻转来精密测距，以及获得良好的多址接入性能和抗多径与干扰性能，全球导航卫星系统(Global Navigation Satellite System，以下简称为GNSS)的信号都使用了直接序列扩频(Direct Sequence Spread Spectrum，以下简称为DSSS)技术。
为了使多种信号可以更好地共享GNSS的有限频段，同时进一步提高信号的测距精度及抗干扰性能，新的信号调制方式不断呈现。例如，二进制偏移载波(Binary Offset Carrier，以下简称为BOC)调制。这种调制方式的实现方法是在采用矩形非归零扩频码片的DSSS调制的基础上再将信号与一个方波形式的副载波相乘。一般而言，BOC调制有两个参数：副载波频率fs和扩频序列频率fc，其中fs≥fc，所以BOC具体的调制方式可以记为BOC(fs,fc)。在导航领域中，更简单的记法是将fs和fc都用1.023MHz进行归一化，直接记为BOC(m,n)，其中m＝fs/1.023MHz，n＝fc/1.023MHz。此外，还出现了多种复用BOC的调制技术。例如，时分复用二进制偏移载波(Time-Multiplexed Binary Offset Carrier)调制，以及合成二进制偏移载波(Composite Binary Offset Carrier)调制。
发明内容
本申请的目的是提供一种扩频信号的生成方法、生成装置、接收方法和接收装置。
根据本申请的一个方面，公开了一种扩频信号的生成方法，包括：生成第一扩频信号分量和第二扩频信号分量，其中，所述第一扩频信号分量和所述第二扩频信号分量均包含扩频码和二进制副载波，所述第一扩频信号分量和所述第二扩频信号分量的扩频码相同，所述第一扩频信号分量和所述第二扩频信号分量的二进制副载波不同；将所述第一扩频 信号分量和所述第二扩频信号分量调制到射频载波以生成扩频信号，其中，调制所述第一扩频信号分量的射频载波的相位与调制所述第二扩频信号分量的射频载波的相位不同，所生成的扩频信号为：
SRF＝S1·cos(ωRFt)+S2·cos(ωRFt+θ)
S1＝A1·c(t)·q1(t)·d(t)
S2＝A2·c(t)·q2(t)·d(t)
其中，SRF表示扩频信号，S1和S2分别表示第一扩频信号分量和第二扩频信号分量，A1和A2分别表示S1和S2的幅度，c(t)表示S1和S2的扩频码，q1(t)和q2(t)分别表示S1和S2的二进制副载波，d(t)表示电文数据，ωRF表示射频载波的角频率，θ表示调制S1和S2的射频载波相位之间的相位差。
根据本申请的另一个方面，公开了一种扩频信号的生成装置，包括：扩频信号分量生成单元，生成第一扩频信号分量和第二扩频信号分量，其中，所述第一扩频信号分量和所述第二扩频信号分量均包含扩频码和二进制副载波，所述第一扩频信号分量和所述第二扩频信号分量的扩频码相同，所述第一扩频信号分量和所述第二扩频信号分量的二进制副载波不同；以及扩频信号生成单元，将所述第一扩频信号分量和所述第二扩频信号分量调制到射频载波以生成扩频信号，其中，调制所述第一扩频信号分量的射频载波的相位与调制所述第二扩频信号分量的射频载波的相位不同，其中，所述扩频信号生成单元通过以下方式生成扩频信号：
SRF＝S1·cos(ωRFt)+S2·cos(ωRFt+θ)
S1＝A1·c(t)·q1(t)·d(t)
S2＝A2·c(t)·q2(t)·d(t)
其中，SRF表示扩频信号，S1和S2分别表示第一扩频信号分量和第二扩频信号分量，A1和A2分别表示S1和S2的幅度，c(t)表示S1和S2的扩频码，q1(t)和q2(t)分别表示S1和S2的二进制副载波，d(t)表示电文数据，ωRF表示射频载波的角频率，θ表示调制S1和S2的射频载波相位之间的相位差。
根据本申请的另一个方面，公开了一种接收扩频信号的方法，包括：生成所述扩频信号的扩频码本地复现码；生成所述第一扩频信号分量的二进制副载波本地复现码以及所述第二扩频信号分量的二进制副载波本 地复现码；根据调制所述第一扩频信号分量的射频载波的相位与调制所述第二扩频信号分量的射频载波的相位之间的相位差生成本地载波；根据所生成的本地载波、扩频码本地复现码、第一扩频信号分量的二进制副载波本地复现码以及第二扩频信号分量的二进制副载波本地复现码，对所接收到的扩频信号进行相干积分运算，并对运算结果进行线性组合，以获得积分同相支路分量和积分正交支路分量。
根据本申请的另一个方面，公开了一种接收扩频信号的接收机，包括：基带信号生成单元，生成所述扩频信号的扩频码本地复现码，生成所述第一扩频信号分量的二进制副载波本地复现码以及所述第二扩频信号分量的二进制副载波本地复现码；本地载波生成单元，根据调制所述第一扩频信号分量的射频载波的相位与调制所述第二扩频信号分量的射频载波的相位之间的相位差生成本地载波；以及运算单元，根据所生成的本地载波、扩频码本地复现码、第一扩频信号分量的二进制副载波本地复现码以及第二扩频信号分量的二进制副载波本地复现码，对所接收到的扩频信号进行相干积分运算，并对运算结果进行线性组合，以获得积分同相支路分量和积分正交支路分量。
附图说明
图1显示了根据本申请的一种实施方式的扩频信号生成方法的流程图。
图2显示了根据本申请的一种实施方式的扩频信号的生成装置的示意方框图。
图3显示了根据本申请的另一种实施方式的扩频信号的生成装置的示意方框图。
图4显示了根据本申请的一种实施方式的扩频信号接收机的示意方框图。
图5显示了根据本申请的一种实施方式的扩频信号接收机的具体实现示意图。
图6显示了根据本申请的一种实施方式的扩频信号接收方法的流程图。
具体实施方式
下面参照附图对本申请公开的扩频信号的生成方法、生成装置、接收方法和接收装置进行详细说明。为简明起见，本申请各实施例的说明中，相同或类似的装置使用了相同或相似的附图标记。
图1显示了根据本申请的一种实施方式生成扩频信号SRF的方法的流程图。
在步骤110中，生成第一扩频信号分量S1和第二扩频信号分量S2，其中，第一扩频信号分量S1和第二扩频信号分量S2均包含扩频码和二进制副载波，第一扩频信号分量S1和第二扩频信号分量S2的扩频码相同，并且第一扩频信号分量S1和第二扩频信号分量S2的二进制副载波不同。
在步骤120中，将第一扩频信号分量S1和第二扩频信号分量S2调制到射频载波以生成扩频信号SRF，其中，调制第一扩频信号分量S1的射频载波的相位与调制第二扩频信号分量S2的射频载波的相位不同。
将包含扩频码和二进制副载波的两个扩频信号分量分别调制在载波的不同相位上，从而实现了扩频信号分量的复用。
其中，在步骤120中所生成的扩频信号SRF为：
SRF＝S1·cos(ωRFt)+S2·cos(ωRFt+θ)
S1＝A1·c(t)·q1(t)·d(t)
S2＝A2·c(t)·q2(t)·d(t)
其中，S1和S2分别表示第一扩频信号分量和第二扩频信号分量，A1和A2分别表示S1和S2的幅度，c(t)表示S1和S2的扩频码，q1(t)和q2(t)分别表示S1和S2的二进制副载波，d(t)表示电文数据，ωRF表示射频载波的角频率，θ表示调制S1和S2的射频载波相位之间的相位差。
根据本申请的一种实施方式，二进制副载波是二进制编码符号(BCS,binary coded symbol)副载波。例如，第一扩频信号分量S1的副载波可以是BCS([1 1 1 1 -1 1 1 1 1]，1)，第二扩频信号分量S2的副载波可以是BCS([1 1 1 1 1 -1 1 1 1 1 1]，1)等。本领域技术人员可以理解，这里的BCS副载波只是示例性说明，扩频信号分量的二进制副载波可以是任 何形式的BCS副载波。
根据本申请的另一种实施方式，二进制副载波是二进制偏移载波BOC副载波，BOC(m,n)。其中，m是BOC分量的方波副载波频率fs被1.023MHz归一化后的结果，即m＝fs/1.023MHz；n是BOC信号中扩频码c(t)的频率fc被1.023MHz归一化后的结果。例如，第一扩频信号分量S1的副载波可以是BOC(1,1)，第二扩频信号分量S2的副载波可以是BOC(6,1)。本领域技术人员可以理解，这里的BOC(1,1)和BOC(6,1)只是示例性说明，扩频信号分量的二进制副载波可以是任何形式的BOC副载波。
当二进制副载波是二进制偏移载波BOC副载波时，扩频信号分量S1和S2为二进制偏移载波BOC信号。可以理解，此时实现了两种二进制偏移载波BOC信号的复用。根据本实施方式的BOC复用方法，将两个信号分量分别调制在载波的不同相位上。这样的实施方式能够实现两个不同的BOC信号分量之间的交调分量在总信号中所占比重的灵活调整。
本领域技术人员可以理解，信号在接收时的捕获、跟踪、解调、抗多径等性能与信号的频谱特征有很大关系。本实施方式的BOC复用信号中，两信号分量之间交调分量的大小会影响到接收时的捕获、跟踪、解调、抗多径性能。
根据本申请的一种实施方式，可以进一步设置相位差θ，以调整第一扩频信号分量S1和第二扩频信号分量S2之间的交调分量。通过设置两信号分量之间的载波相位关系，可以针对特定的需求，调整发射信号的特性，以有利于接收时的捕获、跟踪、解调、抗多径性能。
根据本实施方式，基带信号可以视为
SBB(t)＝S1(t)+S2(t)ejθ
这样，基带信号的自相关函数为
Figure PCTCN2014093023-appb-000001
其中，R1和R2分别为c(t)q1(t)的自相关函数和c(t)q2(t)的自相关函数，Rc(τ)是c(t)q1(t)与c(t)q2(t)的互相关函数。可以看到，在基带信号的自相关函数中，除了包含第一扩频信号分量的自相关函数和第二扩频信号分量的 自相关函数外，还包含有第一扩频信号分量与第二扩频信号分量的互相关函数，也即前文提到的交调分量。
而通过设置相位差θ可以使cosθ取-1到+1之间的任意值，从而改变交调分量的大小。
根据本申请的一种实施方式，可以根据接收扩频信号时所需的解调性能指标η和跟踪性能指标β，确定所述相位差θ的值。接收扩频信号时的解调性能指标η是指扩频信号经过发射机滤波处理时引入的功率衰减，解调性能指标η会直接影响接收机的相关器输出信噪比。跟踪性能指标β是指经过发射机滤波后的扩频信号的均方根带宽，跟踪性能指标β会影响在热噪声和多径下的跟踪环路的误差。
例如，解调性能指标η和跟踪性能指标β可以通过以下公式表示：
Figure PCTCN2014093023-appb-000002
Figure PCTCN2014093023-appb-000003
其中，BW是所述的信号发射机的带宽，n0是双边的高斯白噪声功率谱密度，A1和A2分别表示第一扩频信号分量S1和第二扩频信号分量S2的幅度，R1表示S1的扩频码和二进制副载波的乘积c(t)q1(t)的自相关函数，R2表示S2的扩频码和二进制副载波的乘积c(t)q2(t)的自相关函数，Rc(τ)是c(t)q1(t)与c(t)q2(t)的互相关函数。
根据精度要求以一定步长遍历所有相位差θ的可能取值{θk,k＝1,2,...,N}能够得到相应的解调性能指标{ηk,k＝1,2,...,N}和跟踪性能指标{βk,k＝1,2,...,N}，遍历的相位差θ个数N由所要求的精度确定。本领域的技术人员能够理解，信号的抗多径性能与跟踪性能指标β有关。根据信号设计中对于解调性能，跟踪性能和抗多径性能的要求，在所得的 {ηk,k＝1,2,...}和{θk,k＝1,2,...}中选出满足设计要求的一对(βk-opt,ηk-opt)，则所设置的相位差θ的取值为θk-opt。
根据本申请的一种实施方式，可以设置相位差θ为±π/2，以调整第一扩频信号分量S1和第二扩频信号分量S2之间的交调分量为零。
例如，对于BOC副载波，当相位差θ为±π/2时，基带信号可以写为
SBB(t)＝S1(t)±jS2(t)
基带信号的自相关函数为
Figure PCTCN2014093023-appb-000004
可以看成，当相位差θ为±π/2时，基带信号的自相关函数中不包含交调分量。此时，可以在两信号分量上携带不同的电文数据，以增加信号传输的信息量。
图2显示了根据本申请的一种实施方式的扩频信号的生成装置的示意方框图。如图所示，扩频信号的生成装置200包括扩频信号分量生成单元210和扩频信号生成单元220。
扩频信号分量生成单元210生成第一扩频信号分量和第二扩频信号分量。其中，第一扩频信号分量和第二扩频信号分量均包含扩频码和二进制副载波，第一扩频信号分量和第二扩频信号分量的扩频码相同，第一扩频信号分量和第二扩频信号分量的二进制副载波不同。
扩频信号生成单元220将第一扩频信号分量和第二扩频信号分量调制到射频载波以生成扩频信号。其中，调制第一扩频信号分量的射频载波的相位与调制第二扩频信号分量的射频载波的相位不同。
根据一种实施方式，扩频信号生成单元220通过以下方式生成扩频信号SRF：
SRF＝S1·cos(ωRFt)+S2·cos(ωRFt+θ)
S1＝A1·c(t)·q1(t)·d(t)
S2＝A2·c(t)·q2(t)·d(t)
其中，S1和S2分别表示第一扩频信号分量和第二扩频信号分量，A1和A2分别表示S1和S2的幅度，c(t)表示S1和S2的扩频码，q1(t)和q2(t)分别表示S1和S2的二进制副载波，d(t)表示电文数据，ωRF表示射频载波的角频率，θ表示调制S1和S2的射频载波相位之间的相位差。
图3显示了根据本申请的另一种实施方式的扩频信号的生成装置的示意方框图。如图3所示，扩频信号的生成装置200的扩频信号生成单元220还可以进一步包括相位差设置模块221和信号生成模块222。相位差设置模块221设置所述调制第一扩频信号分量S1和第二扩频信号分量S2的射频载波相位之间的相位差θ，以调整第一扩频信号分量S1和第二扩频信号分量S2之间的交调分量。信号生成模块222根据相位差设置模块221所设置的相位差θ生成扩频信号SRF。例如，信号生成模块222根据相位差设置模块221所设置的相位差θ通过以下方式生成扩频信号SRF：
SRF＝S1·cos(ωRFt)+S2·cos(ωRFt+θ)
S1＝A1·c(t)·q1(t)·d(t)
S2＝A2·c(t)·q2(t)·d(t)
其中，S1和S2分别表示第一扩频信号分量和第二扩频信号分量，A1和A2分别表示S1和S2的幅度，c(t)表示S1和S2的扩频码，q1(t)和q2(t)分别表示S1和S2的二进制副载波，d(t)表示电文数据，ωRF表示射频载波的角频率，θ表示调制S1和S2的射频载波相位之间的相位差。
根据一种实施方式，相位差设置模块221可以根据接收扩频信号时所需的解调性能指标和跟踪性能指标，确定相位差θ的值。
根据一种实施方式，相位差设置模块221可以将第一扩频信号分量S1和第二扩频信号分量S2的射频载波相位之间的相位差θ设置为±π/2，以调整第一扩频信号分量S1和第二扩频信号分量S2之间的交调分量为零。此外，相位差设置模块221还可以设置相位差θ为任意值，使cosθ取-1到+1之间的任意值，从而改变第一扩频信号分量S1和第二扩频信号分量S2之间的交调分量的大小。
以上所描述的本申请的实施方式集中在发射端，即，集中在扩频信号的生成方法和生成装置。不过，本申请的实施方式也涉及通过诸如上述扩频信号的生成方法和生成装置所生成的信号。
此外，本领域技术人员应当理解，能够采用相逆的系统、方法和装置来接收和处理本申请实施方式中生成的扩频信号。因此，本申请的实施方式也涉及用于处理诸如上述扩频信号的系统、方法和装置。
图4显示了根据本申请的一种实施方式的接收机的示意方框图。如图4所示，接收机300包括基带信号生成单元310、本地载波生成单元320以及运算单元330。接收机300可以处理所接收到的扩频信号
Figure PCTCN2014093023-appb-000005
基带信号生成单元310生成扩频信号
Figure PCTCN2014093023-appb-000006
的扩频码本地复现码
Figure PCTCN2014093023-appb-000007
并生成第一扩频信号分量的二进制副载波本地复现码
Figure PCTCN2014093023-appb-000008
以及第二扩频信号分量的二进制副载波本地复现码
Figure PCTCN2014093023-appb-000009
本地载波生成单元320根据调制第一扩频信号分量的射频载波的相位与调制第二扩频信号分量的射频载波的相位之间的相位差θ生成本地载波。
运算单元330根据本地载波生成单元320所生成的本地载波，并根据基带信号生成单元310所生成的扩频码本地复现码
Figure PCTCN2014093023-appb-000010
第一扩频信号分量的二进制副载波本地复现码
Figure PCTCN2014093023-appb-000011
以及第二扩频信号分量的二进制副载波本地复现码
Figure PCTCN2014093023-appb-000012
对所接收到的扩频信号
Figure PCTCN2014093023-appb-000013
进行相干积分运算，并对运算结果进行线性组合，以获得积分同相支路分量I和积分正交支路分量Q。
图5显示了根据本申请的一种实施方式的扩频信号接收机的具体实现示意图。
如图5所示，基带信号生成单元310进一步包括扩频码本地复现码生成模块311和副载波本地复现码生成模块312。扩频码本地复现码生成模块311生成扩频信号
Figure PCTCN2014093023-appb-000014
的扩频码本地复现码
Figure PCTCN2014093023-appb-000015
副载波本地复现码 生成模块312生成第一扩频信号分量的二进制副载波本地复现码
Figure PCTCN2014093023-appb-000016
以及第二扩频信号分量的二进制副载波本地复现码
Figure PCTCN2014093023-appb-000017
本地载波生成单元320进一步包括本地载波生成模块321。本地载波生成模块321根据调制第一扩频信号分量的射频载波的相位与调制第二扩频信号分量的射频载波的相位之间的相位差θ生成本地载波
Figure PCTCN2014093023-appb-000018
Figure PCTCN2014093023-appb-000019
其中，
Figure PCTCN2014093023-appb-000020
表示本地载波的解调角频率。可以理解，如果直接对接收到的扩频信号进行解调时，
Figure PCTCN2014093023-appb-000021
如果对已经过下变频器将载波变到中频的扩频信号进行解调时，
Figure PCTCN2014093023-appb-000022
其中，
Figure PCTCN2014093023-appb-000023
为经过下变频器后的载波中频。
运算单元330进一步包括相干积分计算模块331和线性组合计算模块332。
相干积分计算模块331根据本地载波生成单元320所生成的本地载波
Figure PCTCN2014093023-appb-000024
并根据基带信号生成单元310所生成的扩频码本地复现码
Figure PCTCN2014093023-appb-000025
第一扩频信号分量的二进制副载波本地复现码
Figure PCTCN2014093023-appb-000026
以及第二扩频信号分量的二进制副载波本地复现码
Figure PCTCN2014093023-appb-000027
对所接收到的扩频信号
Figure PCTCN2014093023-appb-000028
进行相干积分运算。具体相干积分过程如下：
Figure PCTCN2014093023-appb-000029
Figure PCTCN2014093023-appb-000030
Figure PCTCN2014093023-appb-000031
Figure PCTCN2014093023-appb-000032
其中，
Figure PCTCN2014093023-appb-000033
表示接收到的扩频信号，
Figure PCTCN2014093023-appb-000034
为扩频码本地复现码，
Figure PCTCN2014093023-appb-000035
和
Figure PCTCN2014093023-appb-000036
分别为第一扩频信号分量的二进制副载波本地复现码以及第二扩频信号分量的二进制副载波本地复现码，
Figure PCTCN2014093023-appb-000037
为本地载波的角频率；t1为相干积分运算的起始时刻，Tcoh为积分持续时间；
Figure PCTCN2014093023-appb-000038
和
Figure PCTCN2014093023-appb-000039
是第一加权系数和第二加权系数，其中，
Figure PCTCN2014093023-appb-000040
L1、L2、L3、L4表示相干积分运算结果；I和Q分别为积分同相支路分量和积分正交支路分量。
线性组合计算模块332对相干积分计算模块331的运算结果进行线 性组合，以获得积分同相支路分量I和积分正交支路分量Q。
Figure PCTCN2014093023-appb-000041
Figure PCTCN2014093023-appb-000042
其中，
Figure PCTCN2014093023-appb-000043
和
Figure PCTCN2014093023-appb-000044
是第一加权系数和第二加权系数，二者之间的比例等于扩频信号生成时S1和S2的幅度A1和A2之间的比例，即
Figure PCTCN2014093023-appb-000045
根据本申请的一种实施方式，如图5所示，接收机300可以进一步包括处理单元340，其根据所获得的积分同相支路分量和积分正交支路分量完成载波同步、码定时同步、数据解调、测距码相位和载波相位测量值的提取。本领域技术人员可以理解，当接收机获得积分同相支路分量I和积分正交支路分量Q后，通过处理单元实现载波同步、码定时同步、数据解调、测距码相位和载波相位测量值的提取等功能的方式与现有技术类似，在此不再赘述。
图6显示了根据本申请的一种实施方式接收扩频信号的方法的流程图。如图所示，在步骤410中，生成扩频信号的扩频码本地复现码。
在步骤420中，生成第一扩频信号分量的二进制副载波本地复现码以及第二扩频信号分量的二进制副载波本地复现码。
在步骤430中，根据调制第一扩频信号分量的射频载波的相位与调制第二扩频信号分量的射频载波的相位之间的相位差生成本地载波。
在步骤440中，根据所生成的本地载波、扩频码本地复现码、第一扩频信号分量的二进制副载波本地复现码以及第二扩频信号分量的二进制副载波本地复现码，对所接收到的扩频信号进行相干积分运算，并对运算结果进行线性组合，以获得积分同相支路分量和积分正交支路分量。
根据本申请的一种实施方式，步骤440中的相干积分运算通过以下公式实现:
Figure PCTCN2014093023-appb-000046
Figure PCTCN2014093023-appb-000047
Figure PCTCN2014093023-appb-000048
Figure PCTCN2014093023-appb-000049
线性组合通过以下公式实现：
Figure PCTCN2014093023-appb-000050
Figure PCTCN2014093023-appb-000051
其中，
Figure PCTCN2014093023-appb-000052
表示接收到的扩频信号，
Figure PCTCN2014093023-appb-000053
为扩频码本地复现码，
Figure PCTCN2014093023-appb-000054
和
Figure PCTCN2014093023-appb-000055
分别为第一扩频信号分量的二进制副载波本地复现码以及第二扩频信号分量的二进制副载波本地复现码，
Figure PCTCN2014093023-appb-000056
为本地载波的角频率；t1为相干积分运算的起始时刻，Tcoh为积分持续时间；
Figure PCTCN2014093023-appb-000057
和
Figure PCTCN2014093023-appb-000058
是第一加权系数和第二加权系数，其中，
Figure PCTCN2014093023-appb-000059
L1、L2、L3、L4表示相干积分运算结果；I和Q分别为积分同相支路分量和积分正交支路分量。
根据本申请的一种实施方式，接收扩频信号的方法还可以进一步包括根据所获得的积分同相支路分量和积分正交支路分量完成载波同步、码定时同步、数据解调、测距码相位和载波相位测量值的提取的步骤。可以理解，本领域技术人员能够采用现有技术中的各种方式来根据积分同相支路分量和积分正交支路分量完成载波同步、码定时同步、数据解调、测距码相位和载波相位测量值的提取。
根据本申请的实施方式可以硬件、软件或其组合的形式来实现。本申请的一个方面提供了包括用于实现根据本申请的实施方式的生成扩频信号的方法、接收扩频信号的方法以及接收器可执行指令的计算机程序。此外，此类计算机程序可使用例如光学或磁性可读介质、芯片、ROM、PROM或其它易失性或非易失性设备的任何形式的存储器来存储。根据本申请的一种实施例，提供了存储此类计算机程序的机器可读存储器。
以上参照附图对本申请的示例性的实施方案进行了描述。本领域技 术人员应该理解，上述实施方案仅仅是为了说明的目的而所举的示例，而不是用来进行限制，凡在本申请的教导和权利要求保护范围下所作的任何修改、等同替换等，均应包含在本申请要求保护的范围内。

Claims (18)

  1. 一种扩频信号的生成方法，包括：
    生成第一扩频信号分量和第二扩频信号分量，其中，所述第一扩频信号分量和所述第二扩频信号分量均包含扩频码和二进制副载波，所述第一扩频信号分量和所述第二扩频信号分量的扩频码相同，所述第一扩频信号分量和所述第二扩频信号分量的二进制副载波不同；以及
    将所述第一扩频信号分量和所述第二扩频信号分量调制到射频载波以生成扩频信号，其中，调制所述第一扩频信号分量的射频载波的相位与调制所述第二扩频信号分量的射频载波的相位不同，所生成的扩频信号为：
    SRF＝S1·cos(ωRFt)+S2·cos(ωRFt+θ)
    S1＝A1·c(t)·q1(t)·d(t)
    S2＝A2·c(t)·q2(t)·d(t)
    其中，SRF表示扩频信号，S1和S2分别表示第一扩频信号分量和第二扩频信号分量，A1和A2分别表示S1和S2的幅度，c(t)表示S1和S2的扩频码，q1(t)和q2(t)分别表示S1和S2的二进制副载波，d(t)表示电文数据，ωRF表示射频载波的角频率，θ表示调制S1和S2的射频载波相位之间的相位差。
  2. 如权利要求1所述的方法，其中，所述二进制副载波是二进制编码符号BCS副载波。
  3. 如权利要求1所述的方法，其中，所述二进制副载波是二进制偏移载波BOC副载波。
  4. 如权利要求1至3中任一项所述的方法，进一步包括设置所述相位差θ，以调整第一扩频信号分量S1和第二扩频信号分量S2之间的交调分量。
  5. 如权利要求4所述的方法，进一步包括根据接收所述扩频信号时 所需的解调性能指标和跟踪性能指标，确定所述相位差θ的值。
  6. 如权利要求1至3中任一项所述的方法，进一步包括设置所述相位差θ为±π/2，以调整第一扩频信号分量S1和第二扩频信号分量S2之间的交调分量为零。
  7. 一种扩频信号的生成装置，包括：
    扩频信号分量生成单元，生成第一扩频信号分量和第二扩频信号分量，其中，所述第一扩频信号分量和所述第二扩频信号分量均包含扩频码和二进制副载波，所述第一扩频信号分量和所述第二扩频信号分量的扩频码相同，所述第一扩频信号分量和所述第二扩频信号分量的二进制副载波不同；以及
    扩频信号生成单元，将所述第一扩频信号分量和所述第二扩频信号分量调制到射频载波以生成扩频信号，其中，调制所述第一扩频信号分量的射频载波的相位与调制所述第二扩频信号分量的射频载波的相位不同，其中，所述扩频信号生成单元通过以下方式生成扩频信号：
    SRF＝S1·cos(ωRFt)+S2·cos(ωRFt+θ)
    S1＝A1·c(t)·q1(t)·d(t)
    S2＝A2·c(t)·q2(t)·d(t)
    其中，SRF表示扩频信号，S1和S2分别表示第一扩频信号分量和第二扩频信号分量，A1和A2分别表示S1和S2的幅度，c(t)表示S1和S2的扩频码，q1(t)和q2(t)分别表示S1和S2的二进制副载波，d(t)表示电文数据，ωRF表示射频载波的角频率，θ表示调制S1和S2的射频载波相位之间的相位差。
  8. 如权利要求7所述的生成装置，其中，所述扩频信号生成单元进一步包括：
    相位差设置模块，设置所述相位差θ，以调整第一扩频信号分量S1和第二扩频信号分量S2之间的交调分量；以及
    信号生成模块，根据所述相位差设置模块所设置的相位差θ生成扩频 信号SRF。
  9. 如权利要求8所述的生成装置，其中，所述相位差设置模块根据接收所述扩频信号时所需的解调性能指标和跟踪性能指标，确定所述相位差θ的值。
  10. 一种通过如前述任一权利要求中所述的扩频信号的生成方法或扩频信号的生成装置所生成的扩频信号。
  11. 一种接收如权利要求1所述的方法生成的扩频信号的方法，包括：
    生成所述扩频信号的扩频码本地复现码；
    生成所述第一扩频信号分量的二进制副载波本地复现码以及所述第二扩频信号分量的二进制副载波本地复现码；
    根据调制所述第一扩频信号分量的射频载波的相位与调制所述第二扩频信号分量的射频载波的相位之间的相位差生成本地载波；以及
    根据所生成的本地载波、扩频码本地复现码、第一扩频信号分量的二进制副载波本地复现码以及第二扩频信号分量的二进制副载波本地复现码，对所接收到的扩频信号进行相干积分运算，并对运算结果进行线性组合，以获得积分同相支路分量和积分正交支路分量。
  12. 如权利要求11所述的方法，其中，所述相干积分运算通过以下公式实现:
    Figure PCTCN2014093023-appb-100001
    Figure PCTCN2014093023-appb-100002
    Figure PCTCN2014093023-appb-100003
    Figure PCTCN2014093023-appb-100004
    所述线性组合通过以下公式实现：
    Figure PCTCN2014093023-appb-100005
    Figure PCTCN2014093023-appb-100006
    其中，
    Figure PCTCN2014093023-appb-100007
    表示接收到的扩频信号，
    Figure PCTCN2014093023-appb-100008
    为扩频码本地复现码，
    Figure PCTCN2014093023-appb-100009
    和
    Figure PCTCN2014093023-appb-100010
    分别为第一扩频信号分量的二进制副载波本地复现码以及第二扩频信号分量的二进制副载波本地复现码，
    Figure PCTCN2014093023-appb-100011
    为本地载波的角频率；t1为相干积分运算的起始时刻，Tcoh为积分持续时间；
    Figure PCTCN2014093023-appb-100012
    和
    Figure PCTCN2014093023-appb-100013
    是第一加权系数和第二加权系数，其中，
    Figure PCTCN2014093023-appb-100014
    L1、L2、L3、L4表示相干积分运算结果；I和Q分别为积分同相支路分量和积分正交支路分量。
  13. 如权利要求11所述的方法，进一步包括根据所获得的积分同相支路分量和积分正交支路分量完成载波同步、码定时同步、数据解调、测距码相位和载波相位测量值的提取。
  14. 一种接收如权利要求1所述的方法生成的扩频信号的接收机，包括：
    基带信号生成单元，生成所述扩频信号的扩频码本地复现码，生成所述第一扩频信号分量的二进制副载波本地复现码以及所述第二扩频信号分量的二进制副载波本地复现码；
    本地载波生成单元，根据调制所述第一扩频信号分量的射频载波的相位与调制所述第二扩频信号分量的射频载波的相位之间的相位差生成本地载波；以及
    运算单元，根据所生成的本地载波、扩频码本地复现码、第一扩频信号分量的二进制副载波本地复现码以及第二扩频信号分量的二进制副载波本地复现码，对所接收到的扩频信号进行相干积分运算，并对运算结果进行线性组合，以获得积分同相支路分量和积分正交支路分量。
  15. 如权利要求14所述的接收机，其中，所述运算单元进一步包括相干积分计算模块和线性组合计算模块，
    所述相干积分计算模块通过以下方法计算所述相干积分，
    Figure PCTCN2014093023-appb-100015
    Figure PCTCN2014093023-appb-100016
    Figure PCTCN2014093023-appb-100017
    Figure PCTCN2014093023-appb-100018
    以及
    所述线性组合计算模块通过以下方法计算所述线性组合，
    Figure PCTCN2014093023-appb-100019
    Figure PCTCN2014093023-appb-100020
    其中，
    Figure PCTCN2014093023-appb-100021
    表示接收到的扩频信号，
    Figure PCTCN2014093023-appb-100022
    为扩频码本地复现码，
    Figure PCTCN2014093023-appb-100023
    和
    Figure PCTCN2014093023-appb-100024
    分别为第一扩频信号分量的二进制副载波本地复现码以及第二扩频信号分量的二进制副载波本地复现码，
    Figure PCTCN2014093023-appb-100025
    为本地载波的角频率；t1为相干积分运算的起始时刻，Tcoh为积分持续时间；
    Figure PCTCN2014093023-appb-100026
    和
    Figure PCTCN2014093023-appb-100027
    是第一加权系数和第二加权系数，其中，
    Figure PCTCN2014093023-appb-100028
    L1、L2、L3、L4表示相干积分运算结果；I和Q分别为积分同相支路分量和积分正交支路分量。
  16. 如权利要求14所述的接收机，其中，所述接收机进一步包括：
    处理单元，根据所获得的积分同相支路分量和积分正交支路分量完成载波同步、码定时同步、数据解调、测距码相位和载波相位测量值的提取。
  17. 一种包括用于实现如前述任一权利要求所述的方法、装置或者用于生成如前述任一权利要求所述的信号的可执行指令的程序。
  18. 一种存储如权利要求17所述的程序的机器可读存储器。
PCT/CN2014/093023 2013-12-06 2014-12-04 扩频信号的生成方法、生成装置、接收方法和接收装置 WO2015070820A1 (zh)

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