WO2014002564A1 - 風計測コヒーレントライダ装置 - Google Patents
風計測コヒーレントライダ装置 Download PDFInfo
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- WO2014002564A1 WO2014002564A1 PCT/JP2013/060483 JP2013060483W WO2014002564A1 WO 2014002564 A1 WO2014002564 A1 WO 2014002564A1 JP 2013060483 W JP2013060483 W JP 2013060483W WO 2014002564 A1 WO2014002564 A1 WO 2014002564A1
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S17/00—Systems using the reflection or reradiation of electromagnetic waves other than radio waves, e.g. lidar systems
- G01S17/02—Systems using the reflection of electromagnetic waves other than radio waves
- G01S17/50—Systems of measurement based on relative movement of target
- G01S17/58—Velocity or trajectory determination systems; Sense-of-movement determination systems
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S17/00—Systems using the reflection or reradiation of electromagnetic waves other than radio waves, e.g. lidar systems
- G01S17/88—Lidar systems specially adapted for specific applications
- G01S17/95—Lidar systems specially adapted for specific applications for meteorological use
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02A—TECHNOLOGIES FOR ADAPTATION TO CLIMATE CHANGE
- Y02A90/00—Technologies having an indirect contribution to adaptation to climate change
- Y02A90/10—Information and communication technologies [ICT] supporting adaptation to climate change, e.g. for weather forecasting or climate simulation
Definitions
- the present invention relates to a wind measurement coherent lidar apparatus that transmits and receives laser light having a single frequency to the atmosphere and detects wind speed from a received signal obtained by heterodyne detection, and in particular, changes in temperature and power of local light.
- the present invention relates to a wind measurement coherent lidar device that can accurately measure the peak frequency and width of a reception spectrum even when the noise level of the reception system fluctuates.
- the coherent lidar device for wind measurement pulsed light is irradiated in the atmosphere to receive scattered light from the aerosol.
- the Doppler shift generated by the movement of the aerosol is obtained by heterodyne detection of the seed light and scattered light of the transmission pulse light, and the wind in the laser irradiation direction is measured.
- a signal after heterodyne detection is subjected to FFT processing, derived from the peak frequency, and further, the wind speed width (degree of turbulence in the wind speed field) is derived from the frequency width.
- a conventional wind measurement lidar apparatus for example, an apparatus described in Patent Document 1 is known. In this device, wind speed measurement at a low SN ratio is performed with high accuracy by using foresight information of the wind speed field.
- a single frequency continuous wave light called local light and scattered light from aerosol etc. floating in the atmosphere are received and heterodyne detected, and the peak value in the frequency domain of the received signal Is calculated by calculating the center of gravity, and the wind speed in the atmosphere is measured from the frequency shift amount.
- the level of the noise spectrum at the time of frequency analysis varies due to a gain variation due to a power variation of continuous wave light or a temperature variation of the optical receiver.
- Patent Document 1 when the level fluctuation of the noise spectrum occurs, an error occurs in the peak frequency position to be detected when calculating the center of gravity in the frequency domain, and the measured wind speed value is affected as an offset error. There was a problem of affecting.
- the present invention has been made to solve the above-described problems, and an object of the present invention is to provide a wind measurement coherent rider device that can perform wind speed measurement with high accuracy even when noise spectrum level fluctuations occur. .
- the wind measurement coherent rider device is a wind measurement coherent rider device that transmits and receives laser light having a single frequency to the atmosphere and detects the wind speed from the received signal obtained by heterodyne detection.
- a noise spectrum recording means for recording a noise spectrum in a state; a noise spectrum difference means for subtracting a noise spectrum from a spectrum of a received signal; and a signal spectrum obtained by subtracting a noise spectrum from a frequency peak position of a received signal.
- Offset correction means that performs offset correction for noise levels at different frequencies, frequency shift analysis means that performs signal processing on the signal spectrum after offset correction and measures frequency shift, and wind speed detection based on the frequency shift amount Wind speed conversion means for performing .
- the wind measurement coherent lidar apparatus of the present invention records a noise spectrum in the absence of a received signal, subtracts this noise spectrum from the spectrum of the received signal, and makes a predetermined difference from the frequency peak position with respect to this signal spectrum. Since the offset correction is performed with respect to the noise level at a frequency that is different from the above value, the wind speed can be measured with high accuracy even when the noise spectrum level fluctuates.
- FIG. 1 It is a block diagram which shows the wind measurement coherent rider apparatus by Embodiment 1 of this invention. It is explanatory drawing (the 1) which shows the operation
- FIG. 1 is a configuration diagram showing a wind measurement coherent rider apparatus according to Embodiment 1 of the present invention.
- the light source 1 is connected to the optical distributor 2, and the optical distributor 2 is connected to the pulse modulator 3 and the optical coupler 6.
- the pulse modulator 3 is connected to an optical circulator 4, and the optical circulator 4 is connected to an optical antenna 5 and an optical coupler 6.
- the optical coupler 6 is further connected to the optical receiver 7.
- the optical receiver 7 is connected to an analog-digital converter (hereinafter referred to as an A / D converter) 8, and the A / D converter 8 is connected to a fast Fourier analysis device (hereinafter referred to as an FFT device) 9.
- the FFT device 9 is connected to a noise spectrum difference device 10, and the noise spectrum difference device 10 is connected to an offset correction device 11.
- the offset correction device 11 is connected to the frequency shift analysis device 12, and the frequency shift analysis device 12 is connected to the wind speed conversion device 13.
- FIG. 1 As indicated by a bold line, between the light source 1 and the optical distributor 2, between the optical distributor 2 and the pulse modulator 3, between the optical distributor 2 and the optical coupler 6, and the pulse modulator. 3 and optical circulator 4, optical circulator 4 and optical antenna 5, optical circulator 4 and optical coupler 6, optical coupler 6 and optical receiver 7 are connected by an optical line such as an optical fiber cable. .
- an optical line such as an optical fiber cable.
- the optical receiver 7 and the A / D converter 8 between the A / D converter 8 and the FFT device 9, and between the FFT device 9 and the noise spectrum difference device 10.
- an electric circuit such as an electric signal cable. Connect with.
- the light source 1 has a function of transmitting continuous wave light having a single frequency
- the optical distributor 2 divides the light from the light source 1 into two parts, one for the pulse modulator 3 and the other for the optical coupler 6. It is a distributor.
- the pulse modulator 3 is a modulator that applies a predetermined frequency shift to input light and further applies pulse modulation.
- the optical circulator 4 has a function of sending the optical signal from the pulse modulator 3 to the optical antenna 5 and sending the optical signal from the optical antenna 5 to the optical coupler 6.
- the optical antenna 5 is a transmission / reception antenna for transmitting an optical signal from the optical circulator 4 to the atmosphere and transmitting scattered light from the atmosphere to the optical circulator 4 as received light.
- the optical coupler 6 is an optical multiplexer for combining the optical signals from the optical distributor 2 and the optical circulator 4 and sending them to the optical receiver 7.
- the optical receiver 7 is a receiver for converting the optical signal from the optical coupler 6 into an electrical signal by heterodyne detection and sending it to the A / D converter 8.
- the A / D converter 8 is a circuit that performs analog / digital conversion on the received electrical signal of the optical receiver 7, and the FFT device 9 is a device that performs frequency analysis of the received electrical signal by fast Fourier transform.
- the noise spectrum difference device 10 is a device that constitutes a noise spectrum recording means for recording a noise spectrum in the absence of a received signal, and a noise spectrum difference means for subtracting the noise spectrum from the spectrum of the received signal.
- the noise spectrum difference device 10 is configured to record in advance a received spectrum in a state in which scattered light is not received as a noise spectrum and take a difference in the noise spectrum from the received spectrum in a received state.
- the offset correction apparatus 11 is an apparatus that constitutes an offset correction unit that performs offset correction on a noise level having a frequency that is a predetermined value away from the frequency peak position of the received signal with respect to the signal spectrum obtained by subtracting the noise spectrum.
- the offset correction device 11 is configured to perform offset correction on the signal spectrum obtained by subtracting the noise spectrum so that the noise level at a frequency position sufficiently away from the frequency peak position becomes zero.
- the frequency shift analysis device 12 is a device that constitutes frequency shift analysis means for performing signal processing on the signal spectrum after offset correction and measuring the frequency shift.
- the frequency shift analyzer 12 is configured to perform a peak detection process, a centroid calculation process, and the like on the signal spectrum after the offset correction, and measure the frequency shift amount.
- the wind speed conversion device 13 constitutes wind speed conversion means for detecting the wind speed based on the frequency shift amount, and is configured to convert the frequency shift amount into a wind speed value and output it.
- a continuous wave light having a single frequency is transmitted from the light source 1, and after the optical signal is distributed by the optical distributor 2, one is transmitted to the pulse modulator 3 and the other is transmitted to the optical coupler 6.
- the pulse modulator 3 applies a predetermined frequency shift to the input light and further pulsates with a modulation signal having a predetermined pulse width and repetition period.
- This pulsed optical signal is transmitted to the atmosphere via the optical circulator 4 and the optical antenna 5.
- the optical signal transmitted to the atmosphere is scattered by a scatterer such as an aerosol floating in the atmosphere, and the scattered light is received as received light by the optical antenna 5.
- the received light is sent to the optical coupler 6 via the optical antenna 5 and the optical circulator 4.
- the continuous wave light from the optical distributor 2 and the received light are combined and sent to the optical receiver 7.
- a method of giving a predetermined frequency shift to the light input by the pulse modulator 3 and further pulsing with a modulation signal having a predetermined pulse width and repetition period is shown.
- a configuration may be adopted in which an acousto-optic element or the like that gives a predetermined frequency shift is inserted between the optical distributor 2 and the optical coupler 6 by pulsing with a modulation signal having a period.
- the continuous wave light and the received light are subjected to heterodyne detection and converted to a received signal which is an electric signal region.
- the frequency of the received signal has the same value as the Doppler frequency shift corresponding to the wind speed.
- the A / D converter 8 performs A / D conversion of the received signal from the optical receiver 7, and sends this digital signal to the FFT device 9.
- the FFT device 9 performs FFT on the received digital signal to obtain a received spectrum.
- the noise spectrum difference device 10 in the process of transmitting continuous wave light from the above-described light source 1 and obtaining the received spectrum by the FFT device 9, for example, the received spectrum in a state in which no scattered light is received without irradiating laser light.
- the spectrum is recorded in advance as a spectrum, and the difference from the reception spectrum when the scattered light is received is performed in the dB region to obtain the signal spectrum. Furthermore, the intensity level is converted into a linear region.
- the noise spectrum to be recorded in advance may be measured with a time resolution corresponding to one shot of the laser pulse, or may be measured by integrating n times.
- FIG. 2 and 3 are explanatory diagrams showing the operation in the case of offset correction based on the difference in noise spectrum.
- 2 and the left end in FIG. 3 show the same figure after linear transformation.
- the leftmost diagram in FIG. 2 shows an example of a reception spectrum (noise spectrum) when the scattered light is not received and a reception spectrum when the scattered light is received.
- 2 and 3 (a) shows a case where the noise level of the reception spectrum is substantially the same as the pre-recorded noise spectrum, and (b) shows a reception spectrum with respect to the pre-recorded noise spectrum.
- C) is an example in which the noise level of the received spectrum is smaller than the previously recorded noise spectrum. These fluctuations are caused by temperature changes and light source power changes.
- the “shape” of the noise spectrum is corrected, and a signal spectrum in which an offset is superimposed on the relative intensity of 0 dB can be obtained.
- the intensity of the noise spectrum is higher than the signal spectrum, it is possible to prevent erroneous detection of the peak frequency of the noise spectrum in the measurement of the peak frequency position in the offset correction device 11 and the frequency shift analysis device 12 described later.
- the signal spectrum in the linear region obtained by the noise spectrum difference device 10 has an offset. Further, when the intensity level of the noise spectrum varies with respect to the noise spectrum recorded in advance, the offset amount varies.
- the offset correction apparatus 11 measures the approximate peak frequency position by applying a correlation filter of the signal spectrum shape to the signal spectrum in the linear region, and obtains an offset amount at a frequency position sufficiently away from the frequency position. The offset amount is subtracted from the signal spectrum. As a result, an offset-corrected signal spectrum is obtained.
- FIG. 4 is a diagram showing the derivation principle of the peak frequency and the offset amount and the offset correction in the offset correction device 11, and (a), (b), and (c) show the same cases as those in FIGS. Yes.
- deriving the offset amount first, a correlation value is calculated using a filter corresponding to the signal spectrum shape. At this time, the frequency having the maximum correlation value is set to an approximate peak frequency. Next, a frequency that is ⁇ ⁇ n (n is an integer of 1 or more) times from the frequency peak position is referred to as an offset value from the frequency width ⁇ of the correlation waveform at this time, and correction is performed.
- the derivation of the offset amount at a frequency position sufficiently away from the frequency peak position it may be obtained from a time average value at one point or from an average value of a certain frequency width.
- an offset amount may be calculated in a predetermined frequency band for a frequency position sufficiently away from the frequency peak position, or an offset amount may be calculated at a position away from the measured frequency peak position by a predetermined frequency. Also good. Further, based on the measured frequency peak position, it may be selected whether to measure an offset amount at a frequency position far away from the high frequency side or to measure an offset amount at a frequency position far away from the low frequency side.
- the frequency shift analyzer 12 obtains a signal peak frequency by calculating the center of gravity of the signal spectrum after the offset correction, and the wind speed converter 13 calculates a wind speed value from the laser frequency and the peak frequency.
- the center of gravity calculation may be performed in the entire frequency region, or may be performed only around the frequency peak position obtained by the offset correction device 11 in order to reduce the signal processing load.
- the centroid calculation is affected by the noise, and the true value of the frequency peak position
- the frequency peak is detected at a position deviated from the above. That is, an error occurs in the frequency shift amount to be measured, and accurate wind speed measurement cannot be performed.
- the center of gravity of the signal peak position is generally It is derived from the first moment of the signal spectrum defined by
- fg is a gravity center position
- f is a frequency
- x is an amplitude at each frequency. Therefore, when the offset is large with respect to the amplitude of the signal spectrum, the center of gravity position cannot be accurately derived. That is, an error occurs in the frequency shift amount to be measured, and accurate wind speed measurement cannot be performed.
- the signal is obtained by subtracting the noise spectrum from the reception spectrum even when the noise spectrum has frequency characteristics and the noise spectrum intensity level varies.
- the frequency peak position of the signal spectrum can be detected with high accuracy by the centroid calculation. That is, the frequency shift amount can be measured accurately, and high-precision wind speed measurement is possible.
- the signal spectrum is derived by subtracting the noise spectrum from the received spectrum, and offset from the signal spectrum in the linear region.
- the frequency width of the signal spectrum can be accurately detected from the second moment defined by. Thereby, it becomes possible to estimate the disturbance of the wind velocity field to be measured.
- the noise level and the signal level are recorded for each measurement. Therefore, even when the noise level fluctuates, It is possible to accurately derive the noise ratio (hereinafter referred to as reception S / N ratio).
- reception S / N ratio the noise ratio
- the noise is white noise
- the reception signal-to-noise ratio is low, the signal intensity varies greatly, and the frequency peak position detection accuracy also varies. Therefore, it is possible to obtain an index related to the reliability and accuracy with respect to the frequency peak position (wind speed value) detected from the reception SN ratio.
- the wind measurement is performed by transmitting and receiving laser light having a single frequency to the atmosphere and detecting the wind speed from the received signal obtained by heterodyne detection.
- a noise spectrum recording means for recording a noise spectrum in the absence of a received signal
- a noise spectrum difference means for subtracting the noise spectrum from the spectrum of the received signal
- a signal spectrum obtained by subtracting the noise spectrum An offset correction unit that performs offset correction on a noise level at a frequency that is a predetermined value away from the frequency peak position of the received signal
- a frequency shift analysis unit that performs signal processing on the signal spectrum after the offset correction and measures a frequency shift
- Wind speed detection based on the amount of frequency shift Since a calculation means, it is possible to perform the wind speed measured with high accuracy even when the level variation of the noise spectrum occurs.
- any component of the embodiment can be modified or any component of the embodiment can be omitted within the scope of the invention.
- the wind measurement coherent lidar device records a noise spectrum in the absence of a received signal, subtracts the noise spectrum from the spectrum of the received signal, and from the frequency peak position with respect to the signal spectrum. It is configured to perform offset correction for noise levels at frequencies away from a predetermined value, and even when noise spectrum level fluctuations occur, wind speed can be measured with high accuracy, so wind measurement that measures the wind speed in the atmosphere Suitable for use as a coherent rider device.
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Abstract
Description
従来の風計測用のライダ装置として、例えば、特許文献1に記載の装置が知られている。この装置では、風速場の先見情報を利用し、低SN比での風速測定を高精度で行う。
実施の形態1.
図1は、この発明の実施の形態1による風計測コヒーレントライダ装置を示す構成図である。
図1に示す風計測コヒーレントライダ装置において、光源1は光分配器2と接続し、光分配器2はパルス変調器3と光カプラ6に接続する。パルス変調器3は光サーキュレータ4に接続し、光サーキュレータ4は光アンテナ5と光カプラ6に接続する。光カプラ6はさらに光受信機7に接続する。光受信機7はアナログ-ディジタル変換器(以下、A/D変換器という)8に接続し、A/D変換器8は高速フーリエ解析装置(以下、FFT装置という)9に接続する。FFT装置9は雑音スペクトル差分装置10に接続し、雑音スペクトル差分装置10はオフセット補正装置11に接続する。オフセット補正装置11は周波数シフト解析装置12に接続し、周波数シフト解析装置12は風速換算装置13に接続する。
一方、図1中、細線で示しているように、光受信機7とA/D変換器8の間、A/D変換器8とFFT装置9の間、FFT装置9と雑音スペクトル差分装置10の間、雑音スペクトル差分装置10とオフセット補正装置11の間、オフセット補正装置11と周波数シフト解析装置12の間、周波数シフト解析装置12と風速換算装置13の間は電気信号ケーブルのような電気回路で接続する。
光源1から、単一周波数からなる連続波光を送信し、この光信号を光分配器2により分配した後、一方をパルス変調器3に、もう一方を光カプラ6に送信する。パルス変調器3では、入力した光に対して所定の周波数シフトを与え、さらに所定のパルス幅と繰り返し周期からなる変調信号によりパルス化する。このパルス化された光信号を光サーキュレータ4、光アンテナ5を介して大気中に送信する。大気中に送信された光信号は、大気中に浮遊するエアロゾル等の散乱体により散乱され、この散乱光を光アンテナ5により受信光として受信する。この際、エアロゾル等の散乱体が風に乗って移動しているため、受信光には風速に相当するドップラーシフト周波数が生じている。上記受信光を、光アンテナ5、光サーキュレータ4、を介して光カプラ6に送る。光カプラ6において、光分配器2からの連続波光と上記受信光を合波し、光受信機7に送る。
図2における左端の図は、散乱光を受光しないときの受信スペクトル(雑音スペクトル)と散乱光を受光した場合の受信スペクトルの例を示す。また、図2および図3において、(a)は予め記録した雑音スペクトルに対して、受信スペクトルの雑音レベルがほぼ同じレベルである場合、(b)は予め記録した雑音スペクトルに対して、受信スペクトルの雑音レベルが大きい場合、(c)は予め記録した雑音スペクトルに対して、受信スペクトルの雑音レベルが小さい場合の例である。これらの変動は、温度変化や光源のパワー変化により生じる。
で定義される信号スペクトルの1次モーメントより導出する。ここで、fgは重心位置、fは周波数、xは各周波数における振幅である。したがって、信号スペクトルの振幅に対して前記オフセットが大きい場合には、重心位置が正確に導出することができない。つまり、測定する周波数シフト量に誤差が生じ、正確な風速測定ができない。
で定義される2次モーメントより、信号スペクトルの周波数幅を正確に検出することができる。これにより、測定する風速場の乱れを推定することが可能となる。
Claims (1)
- 単一周波数からなるレーザ光を大気中に対し送受し、ヘテロダイン検波により得られた受信信号より風速検出を行う風計測コヒーレントライダ装置において、
前記受信信号がない状態での雑音スペクトルを記録する雑音スペクトル記録手段と、
前記受信信号のスペクトルから前記雑音スペクトルを差分する雑音スペクトル差分手段と、
前記雑音スペクトルを差分した信号スペクトルに対して、前記受信信号の周波数ピーク位置から所定の値離れた周波数の雑音レベルに対するオフセット補正を行うオフセット補正手段と、
前記オフセット補正後の信号スペクトルに対して信号処理を行い、周波数シフトを測定する周波数シフト解析手段と、
前記周波数シフト量に基づいて風速検出を行う風速換算手段とを備えたことを特徴とする風計測コヒーレントライダ装置。
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JP2014522455A JP5868504B2 (ja) | 2012-06-25 | 2013-04-05 | 風計測コヒーレントライダ装置 |
US14/391,252 US9599714B2 (en) | 2012-06-25 | 2013-04-05 | Wind measurement coherent lidar |
CN201380027771.3A CN104335068B (zh) | 2012-06-25 | 2013-04-05 | 风测量相干雷达装置 |
EP13810413.8A EP2866050B1 (en) | 2012-06-25 | 2013-04-05 | Wind measurement coherent lidar device |
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WO2020246269A1 (ja) * | 2019-06-06 | 2020-12-10 | 三菱電機株式会社 | コヒーレントライダ装置 |
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US9599714B2 (en) | 2017-03-21 |
JPWO2014002564A1 (ja) | 2016-05-30 |
JP5868504B2 (ja) | 2016-02-24 |
CN104335068A (zh) | 2015-02-04 |
EP2866050B1 (en) | 2018-08-01 |
EP2866050A4 (en) | 2015-12-09 |
CN104335068B (zh) | 2016-04-06 |
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US20150331110A1 (en) | 2015-11-19 |
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