WO2012144373A1 - スイッチ回路、選択回路、及び電圧測定装置 - Google Patents
スイッチ回路、選択回路、及び電圧測定装置 Download PDFInfo
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- WO2012144373A1 WO2012144373A1 PCT/JP2012/059756 JP2012059756W WO2012144373A1 WO 2012144373 A1 WO2012144373 A1 WO 2012144373A1 JP 2012059756 W JP2012059756 W JP 2012059756W WO 2012144373 A1 WO2012144373 A1 WO 2012144373A1
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- voltage
- mos transistor
- terminal
- switch
- power supply
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R31/00—Arrangements for testing electric properties; Arrangements for locating electric faults; Arrangements for electrical testing characterised by what is being tested not provided for elsewhere
- G01R31/36—Arrangements for testing, measuring or monitoring the electrical condition of accumulators or electric batteries, e.g. capacity or state of charge [SoC]
- G01R31/396—Acquisition or processing of data for testing or for monitoring individual cells or groups of cells within a battery
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R31/00—Arrangements for testing electric properties; Arrangements for locating electric faults; Arrangements for electrical testing characterised by what is being tested not provided for elsewhere
- G01R31/005—Testing of electric installations on transport means
- G01R31/006—Testing of electric installations on transport means on road vehicles, e.g. automobiles or trucks
- G01R31/007—Testing of electric installations on transport means on road vehicles, e.g. automobiles or trucks using microprocessors or computers
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R31/00—Arrangements for testing electric properties; Arrangements for locating electric faults; Arrangements for electrical testing characterised by what is being tested not provided for elsewhere
- G01R31/36—Arrangements for testing, measuring or monitoring the electrical condition of accumulators or electric batteries, e.g. capacity or state of charge [SoC]
- G01R31/382—Arrangements for monitoring battery or accumulator variables, e.g. SoC
- G01R31/3835—Arrangements for monitoring battery or accumulator variables, e.g. SoC involving only voltage measurements
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/04—Modifications for accelerating switching
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
- H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
- H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors
- H03K17/6871—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors the output circuit comprising more than one controlled field-effect transistor
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
- H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
- H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors
- H03K17/693—Switching arrangements with several input- or output-terminals, e.g. multiplexers, distributors
Definitions
- the present invention relates to a switch circuit, a selection circuit, and a voltage measuring device, and more particularly to a technique effective when applied to a voltage measuring device that selects and measures one voltage from a plurality of voltages.
- EV electric vehicles
- HEV hybrid vehicles
- a vehicle-mounted power source having a high voltage of several hundred volts is required.
- the on-vehicle power source is realized by an assembled battery in which a plurality of unit cells (also referred to as “battery cells”) that generate a voltage of about several volts are connected in series.
- each battery cell VCL 1 is used to determine the state of the battery (for example, overcharged state, overdischarged state, remaining charge amount, etc.) under all use environments such as when the vehicle is running or charged. It is necessary to measure the voltage with high accuracy.
- a highly accurate battery voltage detection technique is essential for the effective use of battery energy, and is particularly important as a vehicle power source that leads to vehicle safety and longer vehicle travel distance.
- a voltage measuring device in a vehicle-mounted power supply has one AD converter (hereinafter referred to as ADC (Analog-to-to-hereinafter)) per battery cell VCL.
- ADC Analog-to-to-hereinafter
- the voltage measuring device is equipped with a multiplexer circuit (hereinafter also referred to as MUX (multiplexer)), and is designed based on the lowest potential (ground (GND) level) by MUX. Voltage measurement is realized by sequentially switching battery voltages at different voltage levels in time to ADC signal input.
- MUX multiplexer circuit
- Patent Document 1 As a circuit method for measuring the battery voltage, a method using a flying capacitor circuit has been most commonly used (see, for example, Patent Document 1).
- This scheme is configured using at least one capacitor as part of the MUX circuit. Normally, neither terminal of both electrodes is fixed at a specific potential, and this capacitor can be connected to the input voltage terminals of both electrodes of each battery through the switch circuit on the battery side, and 2 of the ADC through the switch circuit on the ADC side. It can be connected to two input terminals. Further, one terminal of the capacitor can be connected to the GND potential or a predetermined fixed potential by another switch circuit.
- the operation at the time of measurement of the flying capacitor circuit described in Patent Document 1 will be briefly described as follows.
- a battery-side switch that connects both ends of the battery whose voltage is to be measured and the capacitor C is turned on to charge the capacitor C with the battery voltage.
- the battery side switch is turned off, one of the electrodes of the capacitor C is connected to the GND potential or a constant potential.
- the ADC side switch is turned on to electrically connect to the ADC, and the voltage value is read by the ADC.
- a buffer amplifier or a differential amplifier may be used between the capacitor C and the ADC, the operation procedure is the same.
- Patent Documents 1 to 9 disclose the conventional voltage measuring device, and Patent Documents 10 to 12 disclose other related techniques.
- Patent Document 1 discloses a method for equalizing a switch drive current consumed from a battery when a switch element connecting a battery voltage input and a capacitor is turned on in each switch circuit of a flying capacitor type voltage measuring device.
- a technique is disclosed in which the drive current is weighted for each battery so as to increase current consumption flowing in the level shift circuit. .
- Patent Document 2 discloses a method of connecting to a voltage detection circuit using N + 1 PNP structure or NPN structure switching elements for connection to a capacitor for N battery cells.
- Patent Documents 3 to 6 disclose a configuration in which the same number of capacitors as the voltage sources to be measured are used, and only one N-type or P-type MOSFET is used as the switch element of each switch circuit. Further, in Patent Document 5, in order to improve a measurement error due to the parasitic capacitance of the switch used in the flying capacitor, the floating capacitance including the parasitic capacitance of the switch group is measured in advance, the capacitance of the flying capacitor, the measured floating capacitance, and the like. A method is disclosed in which an error voltage due to charges accumulated in the stray capacitance is calculated based on the above and a measurement voltage is calculated based on the error voltage. Further, Patent Document 6 discloses a method for improving an error due to a parasitic capacitance component of a switch.
- Patent Document 7 in order to cope with a charge loss due to a parasitic diode between the source and drain of a MOS transistor used as a switch element, capacitors corresponding to the number of battery cells are used in the voltage measurement circuit.
- a method using a MOSFET is disclosed.
- Patent Document 8 discloses a method of turning on a switch with an AC signal by using a capacitor in a signal level shift circuit for turning on a switch for connecting a battery voltage input and the capacitor.
- Patent Document 9 discloses a method using a sample and hold circuit in which a switch and a differential amplifier circuit (OP amplifier) are combined in order to improve a measurement error due to the parasitic capacitance of the switch as in Patent Document 5. .
- OP amplifier differential amplifier circuit
- Patent Document 10 discloses a method for controlling the opening and closing of a power supply path between an external electrode and a battery for stably charging the battery in the battery protection circuit.
- Patent Document 11 discloses a method for connecting cascaded transistors in a system in which one MOS transistor has insufficient withstand voltage.
- Patent Document 12 discloses a technique for preventing a backflow of current from a battery due to battery overcharge or input voltage drop in battery charge control.
- the inventor of the present application has found the following new problems as a result of reviewing the technical problems in accordance with the demand for higher accuracy of voltage measurement in the voltage measuring apparatus and equalization of current consumption of the battery.
- the first problem is a decrease in battery sustainability due to an imbalance in battery energy consumption to be measured.
- FIG. 19 is an example of a switch circuit using a P-type MOS transistor as a switch element, which is not a publicly known technique, but was examined by the inventors of the present application prior to the present invention.
- FIG. 20 is an example of a switch circuit using an N-type MOS transistor as a switch element, which was examined prior to the present invention by the inventor of the present application, similarly to FIG.
- the switch circuits shown in FIGS. 19 and 20 are controlled by a bidirectional switch that commonly connects the sources of two MOS transistors and a gate that are commonly connected, and a control signal (ENABLE) for controlling the switch.
- a switch drive unit including a MOS transistor for generating a constant current, a MOS transistor for generating a constant current, and a resistor R.
- the switch circuit shown in the figure is used as the switch circuit in the MUX circuit of the voltage measuring apparatus.
- the switch drive circuit is turned on to measure the input terminal (VIN) to which the battery cell to be measured is connected. Connect to the output terminal (VOUT) connected to the circuit side.
- a drive current I for turning on the switch flows from the input side (VIN) through the resistor R to the ground (GND).
- VIN input side
- R resistor
- GND ground
- Patent Document 1 discloses a method of weighting the drive current of the switch drive circuit, but in this method, when the number of battery cells connected in series is increased, The drive current increases according to the number, and the unit current of the drive current needs to be considerably reduced in order to suppress the power consumption of the battery. Further, the switch element near the lowest position must generate an on-voltage with a very small current, and a resistance element (for example, a resistance element corresponding to the resistance R in FIGS. 19 and 20) for generating the on-voltage of the drive circuit. ) Becomes a high resistance, which increases the area of the voltage measuring device.
- the second problem is deterioration of voltage measurement accuracy due to a voltage drop caused by the resistance component of the switch element and the signal path and the drive current of the switch element.
- the first problem when a driving current for turning on the switching element is supplied from the battery cell to be measured, the on-resistance of the switching element, the resistance component of the signal path through which the driving current flows, the battery cell
- the drive current flows through the resistance component of the external noise cut filter between the electrode and the switch element, a voltage drop occurs.
- These resistance components cannot be manufactured uniformly in all products, and variations in the elements always occur. However, the variations in the resistance components cause a difference in voltage drop between the respective components. This difference in voltage drop becomes a factor that degrades the voltage measurement accuracy.
- Patent Document 2 a PMOS transistor is used as a switch on the positive electrode side and an NMOS switch is used on the negative electrode side as a switch element corresponding to each battery cell.
- a PMOS transistor is used as a switch on the positive electrode side and an NMOS switch is used on the negative electrode side as a switch element corresponding to each battery cell.
- the method for improving the measurement error due to the drive current is not particularly mentioned in Patent Documents 1 to 12.
- Patent Document 8 as described above, a method of using a drive capacitor to drive a switch element is shown. However, an AC signal for turning on a switch may become measurement noise.
- a flying capacitor circuit that holds the voltage so that measurement can be performed when the switch to the battery side is OFF is considered necessary.
- a capacitive element having a large area must be used, resulting in an increase in circuit scale.
- the third problem is a deterioration in measurement accuracy due to an unexpected current leak path in the switch element in the off state.
- a MOS transistor is used as each switch element in a MUX circuit in which battery cells are selectively connected to one flying capacitor.
- the switch element (MOS transistor) of the battery cell is turned on, the switch element (MOS transistor) of the other battery cell is turned off.
- the gate of the MOS transistor of another battery cell is controlled to be turned off, a current path from the battery cell to be measured to the flying capacitor will occur if a voltage relationship occurs that causes a parasitic diode between the source and the drain to conduct.
- Patent Documents 3 to 7 propose a configuration in which a parasitic diode does not work.
- a flying capacitor corresponding to the number of battery cells must be built in, so that the circuit area is large. turn into.
- Patent Document 9 even when a bidirectional switch that commonly connects the sources of two MOS transistors and commonly connects the gates is used as a switch element, When the voltage of the battery to be measured is higher than the source node of the PMOS transistor, the parasitic diode of the PMOS transistor operates and a load current is generated. Further, when the voltage of the battery to be measured is lower than the source node of the NMOS transistor of the switch element in the off state, the parasitic diode of the NMOS transistor operates and a load current is generated.
- the fourth problem is the generation of a measurement error due to the device due to the parasitic capacitance of the switch element and the offset error of the OP amplifier in the flying capacitor type voltage measuring device.
- the processing for correcting the error is complicated, which causes an increase in circuit scale.
- an OP amplifier is added between a capacitor and an ADC in a flying capacitor circuit as in Patent Document 9 or a sample and hold circuit using an OP amplifier is used, the offset voltage of the OP amplifier itself is reduced. It becomes an error factor.
- There are various methods for correcting the error but it takes a lot of time and may increase measurement time and power consumption.
- An object of the present invention is to provide a technique that contributes to improvement of voltage measurement accuracy and equalization of current consumption of a battery in a voltage measurement device.
- the switch circuit includes a switch element provided between the input terminal and the output terminal, and a first power supply voltage and a second power supply voltage that are different from each other across the input voltage supplied to the input terminal.
- the switch driving unit has a drain side connected to a first power supply terminal side to which the first power supply voltage is supplied, inputs a voltage corresponding to the input voltage, and drives the switch element with a voltage generated on an output side
- a source follower circuit to be supplied to the switch element as a driving voltage, and a current path between an output side of the source follower circuit and a second power supply terminal to which the second power supply voltage is supplied according to the control signal
- a current control unit that opens and closes.
- this switch circuit contributes to improvement of voltage measurement accuracy in the voltage measurement device and equalization of current consumption of the battery.
- FIG. 1 is a block diagram illustrating an example of a voltage measuring apparatus according to the first embodiment.
- FIG. 2 is an explanatory diagram showing an example of power supply of the voltage measuring device 2.
- FIG. 3 is an explanatory diagram showing connection portions of some switch circuits of the MUX circuit 30 in the voltage measuring device 2.
- FIG. 4 is a timing chart showing an example of the operation timing of the voltage measuring device 2.
- FIG. 5 is a circuit diagram showing an example of a switch circuit using the P-type MOS transistor of the MUX circuit 30 as a switch element.
- FIG. 6 is a circuit diagram showing an example of a switch circuit using the N-type MOS transistor of the MUX circuit 30 as a switch element.
- FIG. 1 is a block diagram illustrating an example of a voltage measuring apparatus according to the first embodiment.
- FIG. 2 is an explanatory diagram showing an example of power supply of the voltage measuring device 2.
- FIG. 3 is an explanatory diagram showing connection portions of some switch circuits of the MUX circuit
- FIG. 7 is a block diagram illustrating a configuration example of the MUX circuit 30 using two types of switch circuits.
- FIG. 8 is a block diagram showing an example of a battery voltage measurement system for EV or HEV.
- FIG. 9 is a block diagram showing another example of a battery voltage measurement system for EV or HEV.
- FIG. 10 is a circuit diagram showing another example of a switch circuit using a bidirectional switch element of a P-type MOS transistor.
- FIG. 11 is an explanatory diagram showing an off signal (OFF) in FIG.
- FIG. 12 is a circuit diagram showing another example of a switch circuit using a bidirectional switch element of a P-type MOS transistor.
- FIG. 13 is an explanatory diagram showing an off signal (OFF) in FIG.
- FIG. 14 is a circuit diagram showing another example of a switch circuit using a bidirectional switch element of an N-type MOS transistor.
- FIG. 15 is an explanatory diagram showing an off signal (OFF) in FIG.
- FIG. 16 is a block diagram illustrating an example of the case where the power supply of the voltage measuring device 2 is supplied from another power source.
- FIG. 17 is a block diagram showing an example of a flying capacitor type voltage measuring apparatus to which the MUX circuit 30 is applied.
- FIG. 18 is a timing chart showing an example of the operation timing of the voltage measuring device 4.
- FIG. 19 is a circuit diagram of a switch circuit using a P-type MOS transistor as a switch element, which was examined by the inventor prior to the present invention.
- FIG. 20 is a circuit diagram of a switch circuit using an N-type MOS transistor as a switch element, which was examined by the inventor prior to the present invention.
- the switch circuit (SWP, SWN) according to a representative embodiment of the present invention includes a switch element (MP1 and MP2 or MN1 and MN2) provided between an input terminal (VIN) and an output terminal (VOUT). And a switch drive unit (401 to 409) for driving the switch element based on a control signal (ENABLE) for instructing on / off of the switch element.
- the switch driving unit is driven between a first power supply voltage (VCC or GND) and a second power supply voltage (GND or VCC) that are different from each other across an input voltage supplied to the input terminal.
- the switch driver is connected to the drain side on the first power supply terminal side to which the first power supply voltage is supplied, inputs a voltage corresponding to the input voltage, and outputs the voltage generated on the output side to the switch element.
- Source follower circuits (401, 404) to be supplied to the switch element as drive voltages for driving, and a second power supply terminal to which the output side of the source follower circuit and the second power supply voltage are supplied according to the control signal Current control units (402, 405) for opening and closing the current path between them.
- the switch circuit of Item 1 does not supply a drive current from the input terminal side of the switch circuit, but by a drive current flowing between the first power supply terminal and the second power supply terminal via the source follower circuit.
- the switch element is driven.
- a voltage drop due to the switch drive current and the resistance component between the input and output terminals of the switch does not occur, and power on the input terminal side is not consumed for driving the switch. Therefore, for example, if the switch circuit of Item 1 is applied to the MUX circuit of the voltage measuring device described above, the first and second problems can be solved.
- the switch circuit according to Item 1 wherein the switch element includes a first conductivity type first MOS transistor (MP1 or MN2) having a drain terminal connected to the input terminal side and the drive voltage supplied to the gate terminal, and a drain terminal. Is connected to the output terminal side, the gate terminal is connected to the gate terminal side of the first MOS transistor, and the source terminal is connected in common with the source terminal of the first MOS transistor (MP2). Or MN2).
- the source follower circuit has a second conductivity type third MOS transistor (MN3 or MN3) having a drain terminal connected to the first power supply terminal side and a gate terminal connected to the source terminal side of the first MOS transistor and the second MOS transistor.
- the current control unit opens a current path between the other end of the voltage generation unit and the second power supply terminal when the control signal instructs the switch element to be turned on, and the control signal is When instructing to turn off the element, the current path is closed.
- the switch circuit of Item 1 can be realized with a simple configuration.
- the gate-source voltages of the first MOS transistor and the second MOS transistor are generated based on the current flowing through the voltage generator, an on-voltage that is independent of the input voltage can be generated.
- the switch driver has a current path through which a current smaller than a current flowing through a current path formed by the current control unit is routed, the first power supply terminal, the first MOS transistor, and the second MOS And an off-acceleration unit (403, 406) formed between the other end of the voltage generation unit and the gate terminals of the first MOS transistor and the second MOS transistor between the source terminal of the transistor.
- the switch element when the switch element is in the OFF state, the potential of the node at the other end of the voltage generation unit transitions to the first power supply voltage side, so that the OFF state of the switch element becomes more stable.
- the potentials of the source terminals of the first MOS transistor and the second MOS transistor are shifted to the first power supply voltage side, the movement of charges through the parasitic diodes of the first MOS transistor and the second MOS transistor in the off state is prevented. Can be prevented. Therefore, for example, if the switch circuit of Item 3 is applied to the MUX circuit of the voltage measuring device described above, the third problem can be solved in addition to the first and second problems described above.
- the switch driver includes a first power supply terminal, a source terminal of the first MOS transistor, and a source terminal of the second MOS transistor during a predetermined period of the period in which the current control unit closes the current path And an off-acceleration unit (407 to 409) formed through the other end of the voltage generation unit.
- the OFF state of the switch element becomes more stable, and the movement of electric charges via the parasitic diodes of the first MOS transistor and the second MOS transistor in the OFF state can be prevented. Therefore, for example, if the switch circuit of Item 3 is applied to the MUX circuit of the voltage measuring device described above, the third problem can be solved in addition to the first and second problems described above. Further, since the off acceleration unit does not flow current when the switch element is in an on state, current consumption can be reduced, and the current control is performed as a current flowing through the voltage generation unit that determines the on voltage of the switch element. Since only the current flowing through the part needs to be considered, it contributes to improving the accuracy of the on-voltage.
- the off-acceleration unit operates as a switch, the time until the switch element shifts to the off state can be shortened compared to the case where the off-acceleration unit operates at a constant current, and the parasitic diode is inserted at an earlier timing. Movement of the generated charges can be prevented.
- the period during which the off-acceleration unit forms the current path can be set as a period for instructing the off state of the switch element, for example, design is facilitated.
- the first power supply voltage is set to a voltage value (VCC) equal to or higher than the input voltage
- the first conductivity type is a P-channel type
- the second conductivity type is N-channel type.
- the first power supply voltage is a ground voltage
- the second power supply voltage is a voltage value (VCC) equal to or higher than the input voltage
- the first conductivity type is an N channel.
- the second conductivity type is a P-channel type.
- a selection circuit (30) includes one or a plurality of unit cells among a plurality of unit cells (VCL_1 to VCL_n) that constitute one assembled battery by connecting one end and the other end.
- the block to be configured is defined as one unit, and a signal line connected to both ends of any one of the blocks is selected according to an input control signal, and a first output terminal (INP (+)) and a second output terminal Connect to (INN (-)).
- the selection circuit has an input terminal (VIN) connected to a signal line connected to one end of the block (positive electrode of the battery cell VCL) and an output connected to a signal line connected to the first output terminal.
- a first switch circuit having a terminal (VOUT) and electrically connecting the input terminal and the output terminal in accordance with the control signal; and the other end of the block (negative of the battery cell VCL).
- the second switch circuit (SWN) that electrically connects the input terminal and the output terminal is provided corresponding to each of the blocks.
- the first switch circuit and the second switch circuit are configured according to a switch element (MP1 and MP2 or MN1 and MN2) provided between an input terminal and an output terminal of the switch circuit and the control signal.
- a switch driver (401 to 409) for driving the switch element.
- the switch driving unit is disposed between a first power supply terminal to which the first power supply voltage (VCC or GND) is supplied and a second power supply terminal to which the second power supply voltage (GND or VCC) is supplied.
- a source follower circuit (401, 404) that inputs a voltage corresponding to the input voltage and supplies the voltage generated on the output side to the switch element as a drive voltage for driving the switch element; and the control signal
- a current control unit (402, 405) that opens and closes a current path in which the source follower circuit is disposed between the first power supply terminal and the second power supply terminal.
- the first switch circuit and the second switch circuit there is no voltage drop due to the drive current of the switch and the resistance component between the input and output terminals of the switch, and the switch The power on the input terminal side is not consumed for driving. Therefore, for example, if the selection circuit of Item 9 is applied as the MUX circuit of the voltage measuring device described above, the first and second problems can be solved.
- the first power supply voltage is a voltage (voltage of the positive electrode of VCL_1) corresponding to the voltage at one end of the highest-order unit cell among the unit cells constituting the assembled battery.
- drive currents of the first switch circuit and the second switch circuit are supplied from the assembled battery. That is, since power consumption is equally performed from each unit cell in the selection operation of the selection circuit, the balance of battery energy consumption among the unit cells can be maintained.
- the switch element includes a P-type MOS transistor (MP1, MP2) or an N-type MOS transistor (MN1, MN2) whose gate terminal is controlled by the drive voltage,
- MP1, MP2 P-type MOS transistor
- MN1, MN2 N-type MOS transistor
- the selection circuit according to item 11 uses the same type of switch element connected to each electrode of the block to be selected, the resistance component from each electrode of the block to the first output terminal and the first Contributes to the reduction of deviation from the resistance component up to 2 output terminals.
- [12] (Method of connecting the same type of switch circuit) Item 12.
- the selection circuit according to any one of Items 9 to 11, wherein the switch of the first switch circuit and the second switch circuit corresponding to a first block in which the potential of the other end of the block is equal to or higher than a predetermined potential (VT).
- the element is a P-type MOS transistor (MP1, MP2), and the first switch circuit and the second switch circuit corresponding to the second block of the block whose potential at the other end is lower than the predetermined potential.
- the switch elements are N-type MOS transistors (MN1, MN2).
- the switch elements connected to both ends of each block are provided.
- the types can be equal.
- N-type third MOS transistor MN3 connected to the source terminal side of the second MOS transistor, one end connected to the source terminal side of the third MOS transistor, and the other end to the first MOS transistor and the second MOS transistor.
- a voltage generation unit (R1) that generates a voltage at both ends in accordance with the supplied current.
- the current control unit (402) of the first switch circuit and the second switch circuit corresponding to the first block is configured so that when the control signal (ENABLE) instructs to turn on the switch element, A current path between the other end of the voltage generation unit and the second power supply terminal (GND) is opened. When the control signal instructs the switch element to be turned off, the current path is closed.
- the first switch circuit and the second switch circuit can be realized with a simple configuration.
- the gate-source voltages of the first MOS transistor and the second MOS transistor are generated based on the current flowing through the voltage generator, an on-voltage that is independent of the input voltage can be generated.
- the first switch circuit corresponding to the second block and the switch element of the second switch circuit have a drain terminal connected to the input terminal side and a gate terminal connected to the drive voltage.
- the first switch circuit corresponding to the second block and the source follower circuit (404) of the second switch circuit have a drain terminal connected to the second power supply terminal side and a gate terminal connected to the fourth MOS transistor.
- a P-type sixth MOS transistor MP5 connected to the source terminal side of the fifth MOS transistor, one end connected to the source terminal side of the sixth MOS transistor, and the other end to the fourth MOS transistor and the fifth MOS transistor.
- a voltage generation unit R2 that generates a voltage at both ends in accordance with the supplied current.
- the current control unit of the first switch circuit and the second switch circuit corresponding to the second block may be configured such that the other end of the voltage generation unit is provided when the control signal instructs the switch element to be turned on. And the first power supply terminal (VCC) are opened, and when the control signal instructs the switch element to be turned off, the current path is closed.
- the first switch circuit and the second switch circuit can be realized with a simple configuration.
- the gate-source voltages of the fourth MOS transistor and the fifth MOS transistor are generated based on the current flowing through the voltage generator, an on-voltage that is independent of the input voltage can be generated.
- Switch circuit with constant current type off acceleration circuit Item 14.
- the switch elements are more stable in the off-state and in the off-state. It is possible to prevent charge movement through the parasitic diodes of the first MOS transistor and the second MOS transistor. Therefore, for example, if the selection circuit of item 15 is applied as the MUX circuit of the voltage measuring device described above, the third problem can be solved in addition to the first and second problems described above.
- Switch circuit with switch type off acceleration circuit Item 12.
- the off state of the switch element becomes more stable and It is possible to prevent the movement of charges through the parasitic diode. Therefore, according to the selection circuit of item 16, in addition to the first problem and the second problem, the third problem can be solved, as in the case of the item 15.
- the off-acceleration unit can reduce current consumption and contribute to improving the accuracy of the on-voltage of the switch element, as in item 4.
- the off-acceleration unit operates as a switch, the time until the switch element shifts to the off state can be shortened compared to the case where the off-acceleration unit operates at a constant current, and the parasitic diode is inserted at an earlier timing. Movement of the generated charges can be prevented.
- Switch circuit having a constant current type off acceleration circuit Item 12.
- the selection circuit according to any one of Items 12 to 16, wherein the first switch circuit corresponding to the second block and the switch driving unit of the second switch circuit have a current flowing in a current path formed by the current control unit.
- the switch element is more stable in the off state, and It is possible to prevent charge movement through the parasitic diodes of the fourth MOS transistor and the fifth MOS transistor. Therefore, for example, if the selection circuit of Item 17 is applied as the MUX circuit of the voltage measuring device described above, the third problem can be solved in addition to the first and second problems described above.
- the switch element is more stable in the off state and It is possible to prevent the movement of charges through the parasitic diode. Therefore, according to the selection circuit of item 18, in the same way as item 16, in addition to the first and second problems, the third problem can be solved.
- the off-acceleration unit can reduce current consumption and contribute to improving the accuracy of the on-voltage of the switch element, as in item 16.
- the off-acceleration unit operates as a switch, the time until the switch element shifts to the off state can be shortened compared to the case where the off-acceleration unit operates at a constant current, and the parasitic diode is inserted at an earlier timing. Movement of the generated charges can be prevented.
- a voltage measuring device (2) includes one or more unit cells among a plurality of unit cells (VCL_1 to VCL_n) that constitute an assembled battery with one end and the other end connected to each other. Is a voltage measuring device for measuring the voltage across the block for each block. The voltage measuring device selects a signal line connected to both ends of the block for each block according to an input control signal, and outputs a first output terminal (INP (+)) and a second output terminal (INN).
- the selection unit includes an input terminal (VIN) to which a signal line connected to one end (positive electrode of the battery cell) of the block is connected and an output terminal to which a signal line connected to the first output terminal is connected.
- the first switch circuit and the second switch circuit include a switch element (MP1 and MP2 or MN1 and MN2) provided between an input terminal (VIN) and an output terminal (VOUT) of the switch circuit. And a switch driver (401 to 409) for driving the switch element in response to the control signal.
- the switch driving unit is disposed between a first power supply terminal to which the first power supply voltage VCC or GND) is supplied and a second power supply terminal to which the second power supply voltage (GND or VCC) is supplied.
- a source follower circuit (401, 404) that inputs a voltage according to the input voltage and supplies the voltage generated on the output side to the switch element as a drive voltage for driving the switch element, and according to the control signal Current control units (402, 405) for opening and closing a current path in which the source follower circuit is disposed between the first power supply terminal and the second power supply terminal.
- the voltage measuring device since the drive currents of the first switch circuit and the second switch circuit flow between the first power supply terminal and the second power supply terminal, as in Item 1, A voltage drop due to the drive current and the resistance component between the input and output terminals of the switch does not occur, and power on the input terminal side is not consumed for driving the switch.
- the voltage measurement device of item 19 since a voltage measurement device that does not employ the flying capacitor method can be configured, the measurement error due to the device due to the parasitic capacitance of the switch element or the like can be reduced when measuring the voltage. It is possible to prevent the occurrence of errors due to the use of a buffer or an amplifier circuit for sampling. Therefore, for example, if the voltage measuring device according to item 19 is applied as the voltage measuring device described above, the first, second, and fourth problems can be solved.
- the first power supply voltage is a voltage (voltage of the positive electrode of VCL_1) corresponding to a voltage at one end of the highest-order unit cell among the unit cells constituting the assembled battery.
- the switch circuit for each block is the same type of transistor
- the switch element includes a P-type MOS transistor (MP1, MP2) or an N-type MOS transistor (MN1, MN2) whose gate terminal is controlled by the drive voltage,
- MP1, MP2 P-type MOS transistor
- MN1, MN2 N-type MOS transistor
- the type of the switch element connected to each electrode of the block to be selected is the same as in item 11, from the positive electrode of the block to be measured to the first output terminal This reduces the difference between the resistance component of the signal path and the resistance component of the signal path from the negative electrode to the second output terminal.
- common-mode noise due to disturbance it is possible to prevent differential noise from occurring at the input of the measurement unit. Therefore, for example, even if a delta-sigma analog-to-digital converter that requires a relatively long measurement time is used, it is possible to prevent the noise removal performance of the entire voltage measurement system from being reduced and to prevent measurement errors. Can do.
- the first switch circuit and the second switch circuit corresponding to a first block in which the potential of the other end of the block is equal to or higher than a predetermined potential (VT).
- the switch element is a P-type MOS transistor (MP1, MP2), and the first switch circuit and the second switch circuit corresponding to a second block in the block where the potential at the other end is lower than the predetermined potential.
- These switch elements are N-type MOS transistors (MN1, MN2).
- the switch elements of the first switch circuit and the second switch circuit corresponding to the first block have a drain terminal connected to the input terminal side, and the drive voltage is applied to the gate terminal.
- the supplied P-type first MOS transistor (MP1) the drain terminal is connected to the output terminal side, the gate terminal is connected to the gate terminal side of the first MOS transistor, and the source terminal is the source terminal of the first MOS transistor And a P-type second MOS transistor (MP2) connected in common.
- the source follower circuit (401) of the first switch circuit and the second switch circuit corresponding to the first block has a drain terminal connected to the first power supply terminal side and a gate terminal connected to the first MOS transistor.
- N-type third MOS transistor MN3 connected to the source terminal side of the second MOS transistor, one end connected to the source terminal side of the third MOS transistor, and the other end to the first MOS transistor and the second MOS transistor.
- a voltage generation unit R1 that generates a voltage at both ends in accordance with the supplied current.
- the current control units of the first switch circuit and the second switch circuit corresponding to the first block are configured such that when the control signal instructs the switch element to turn on, the other end of the voltage generation unit and the current control unit A current path to the second power supply terminal (GND) is opened, and when the control signal instructs the switch element to turn off, the current path is closed.
- the first switch circuit and the second switch circuit can be realized with a simple configuration.
- the gate-source voltages of the first MOS transistor and the second MOS transistor are generated based on the current flowing through the voltage generator, an on-voltage that is independent of the input voltage can be generated.
- the first switch circuit corresponding to the second block and the source follower circuit (404) of the second switch circuit have a drain terminal connected to the second power supply terminal side and a gate terminal connected to the fourth MOS transistor.
- a P-type sixth MOS transistor (MP5) connected to the source terminal side of the fifth MOS transistor, one end connected to the source terminal side of the sixth MOS transistor, and the other end to the fourth MOS transistor and the fifth MOS transistor.
- a voltage generation unit (R2) that generates a voltage at both ends in accordance with the supplied current.
- the current control unit (405) of the first switch circuit and the second switch circuit corresponding to the second block is configured such that when the control signal instructs the switch element to be turned on, the voltage generation unit The current path between the other end of the switch and the first power supply terminal (VCC) is opened, and when the control signal instructs the switch element to be turned off, the current path is closed.
- the first switch circuit and the second switch circuit can be realized with a simple configuration.
- the gate-source voltages of the fourth MOS transistor and the fifth MOS transistor are generated based on the current flowing through the voltage generator, an on-voltage that is independent of the input voltage can be generated.
- Switch circuit (Pch) having a constant current type off acceleration circuit) 24 In the voltage measuring device according to any one of Items 22 to 24, the switch driving unit of the first switch circuit and the second switch circuit corresponding to the first block flows in a current path formed by the current control unit.
- the switch element is more stable in the OFF state, and It is possible to prevent charge movement through the parasitic diodes of the first MOS transistor and the second MOS transistor. Therefore, for example, according to the voltage measurement device of Item 25, in addition to the first problem, the second problem, and the fourth problem, the third problem can be solved.
- switch circuit (Pch) having a switch type off acceleration circuit) 24 In the voltage measuring device according to any one of Items 22 to 24, the switch control unit of the first switch circuit and the second switch circuit corresponding to the first block is a period in which the current control unit closes a current path. And an off-acceleration unit that forms a current path between the first power supply terminal and the source terminals of the first MOS transistor and the second MOS transistor via the other end of the voltage generation unit.
- the third problem can be solved.
- the off-acceleration unit operates like a switch, so that the time until the switch element shifts to the off state can be shortened compared with the case where the off-acceleration unit operates at a constant current, and more It is possible to prevent the movement of charges via the parasitic diode at an early timing.
- Switch circuit (Nch) having a constant current type off acceleration circuit In the voltage measurement device according to any one of Items 22 to 26, the first switch circuit corresponding to the second block and the switch driving unit of the second switch circuit flow in a current path formed by the current control unit.
- the switch element is more stable in the OFF state, and It is possible to prevent charge movement through the parasitic diodes of the fourth MOS transistor and the fifth MOS transistor. Therefore, for example, according to the voltage measurement device of Item 26, in addition to the first problem, the second problem, and the fourth problem, the third problem can be solved.
- the first switch circuit corresponding to the second block and the switch driving unit of the second switch circuit are periods in which the current control unit closes a current path. And an off-acceleration unit that forms a current path between the second power supply terminal and the source terminals of the first MOS transistor and the second MOS transistor via the other end of the voltage generation unit.
- the third problem can be solved. Further, since the off acceleration unit operates like a switch as in the item 18, the time until the switch element shifts to the off state can be shortened as compared with the case where the off acceleration unit operates at a constant current, and more It is possible to prevent the movement of charges via the parasitic diode at an early timing.
- ADC is a ⁇ / ⁇ type ADC for measuring battery voltage
- the measurement unit includes delta-sigma analog-digital converters (601 to 603).
- FIG. 1 is a block diagram illustrating an example of a voltage measuring apparatus according to the first embodiment.
- the voltage measuring device 2 shown in the figure includes one or more battery cells among a plurality of battery cells VCL_1 to VCL_n connected in series (when battery cells are collectively referred to as VCL).
- the voltage at both ends is measured for each battery cell block (hereinafter also referred to as “block”).
- the block is a single battery cell. That is, the voltage measuring device 2 measures the voltage by selecting one battery cell from the plurality of battery cells VCL connected in series one by one.
- the plurality of battery cells VCL connected in series are not limited to battery cell rows connected in series in one row, but also include battery cell rows in which a plurality of battery cell rows connected in series are connected in parallel. . In addition, it means that a plurality of battery cells connected in parallel is regarded as one battery, and a plurality of battery cells are connected in series.
- the voltage measuring device 2 selects a voltage input terminal 20 for inputting a voltage from electrodes at both ends of each block, power supply terminals VCC and GND for inputting a power supply voltage, and one battery voltage to be measured.
- Output MUX circuit 30, measurement circuit 60 that measures the input voltage difference, and protection element 40 In the figure, for the sake of simplicity, only functional units related to voltage measurement among the functional units of the voltage measuring device 2 are displayed.
- the power supply of the voltage measuring device 2 is supplied from the plurality of battery cells VCL, for example.
- FIG. 2 is an explanatory diagram showing an example of power supply of the voltage measuring device 2.
- the voltage measuring apparatus 2 is configured such that the voltage of the positive electrode of the uppermost battery cell VCL_1 among the plurality of battery cells VCL is supplied to the power supply terminal VCC, and among the plurality of battery cells VCL, The voltage of the negative electrode of the lowest battery cell VCL_n is supplied to the power supply terminal GND.
- the MUX circuit 30 includes a plurality of switch circuits for connecting a signal path connected to each of the plurality of voltage input terminals 20 and the two input terminals INP (+) and INN ( ⁇ ) of the measurement circuit 60.
- the MUX circuit 30 displays switch circuits SWP_1 to SWP_n that connect the positive side electrode of the battery cell VCL and the positive side input terminal INP (+) of the measuring unit 60 (in a general term, simply SWP).
- switch circuits SWN_1 to SWN_n in the generic name, simply denoted as SWP that connect the negative electrode of the battery cell VCL and the negative input terminal INN ( ⁇ ) of the measuring unit 60.
- the MUX circuit 30 needs 2N switch circuits in order to measure the voltage of each battery cell.
- the switch circuit SWX that connects the voltage input terminal 20 that inputs the positive voltage of the uppermost battery cell and the negative input terminal INN of the measurement circuit 60, and the negative voltage of the lowermost battery cell.
- 2N + 2 switch circuits including a voltage input terminal 20 for inputting the voltage on the side and a switch circuit SWY for connecting the input terminal INP on the positive side of the measurement circuit 60 are provided.
- the MUX circuit 30 is appropriately arranged according to the system to which the MUX circuit 30 is applied.
- the on state and the off state of the switch are controlled by a control signal from the control unit 50.
- the control unit 50 controls the switch circuit of the MUX circuit 30 so that the voltage across the battery cell is applied between the input terminals of the measurement circuit 60. Details of the MUX circuit 30 will be described later.
- the protection element 40 is connected between the two input terminals INP and INN of the measurement circuit 60 and is a protection element for protecting the input stage of the measurement circuit 60, for example, a Zener diode.
- the control unit 50 controls the MUX circuit 30 and the measurement circuit 60 to perform overall control for voltage measurement of each battery cell.
- the control unit 50 is, for example, a dedicated logic circuit or a microcomputer.
- the measurement circuit 60 measures the potential difference input to the two input terminals INP and INN according to the control signal from the control unit 50, and outputs the measurement result.
- the measurement circuit 60 is realized by, for example, a delta-sigma A / D converter.
- the measurement circuit 60 includes, for example, a switch unit 601 and a capacitor 602 for taking in the voltages input to the input terminals INP and INN, and a measurement unit 603 for measuring the voltage by inputting the taken-in voltage.
- the capacitor 602 is a high withstand voltage element
- the measurement unit 603 is a circuit composed of low withstand voltage elements.
- FIG. 3 is an explanatory diagram showing connection parts of some switch circuits of the MUX circuit 30 in the voltage measuring device 2.
- FIG. 4 is a timing chart showing an example of the operation timing of the voltage measuring device 2.
- the control unit 50 first controls the MUX circuit 30 at the timing of reference numeral 201 to turn on the switch circuits SWP_1 and SWN_1. Accordingly, the voltage of the battery cell VCL_1 is input to the measurement circuit 60. After the input voltage is stabilized, the control unit 50 controls the measurement circuit 60 at the timing of reference numeral 202 to execute voltage measurement. When the measurement of the voltage of the battery cell VCL_1 is completed, the control unit 50 turns off the switch circuits SWP_1 and SWN_1 at the timing of reference numeral 203.
- the control unit 50 controls the MUX circuit 30 at the timing of reference numeral 204 to turn on the switch circuits SWP_2 and SWN_2.
- the timing 204 at which the switch is turned on is a timing after a predetermined time has elapsed since the switch circuits SWP_1 and SWN_1 are turned off in order to prevent a short circuit caused by turning on all the switch circuits SWP1 to SWN_2.
- the switch circuits SWP_2 and SWN_2 are turned on, the voltage of the battery cell VCL_2 is input to the measurement circuit 60.
- the control unit 50 controls the measurement circuit 60 at the timing of reference numeral 205 to execute voltage measurement.
- the control unit 50 turns off the switch circuits SWP_2 and SWN_2 at the timing of reference numeral 206.
- a flying capacitor and an OP amplifier as a buffer are not required when the flying capacitor method is adopted, a measurement error caused by a device such as a parasitic capacitance of a switch element of a switch circuit, A measurement error due to an offset voltage of an OP amplifier or the like does not occur.
- switch circuits constituting the MUX circuit 30: a switch circuit using a P-type MOS transistor as a switch element and a switch circuit using an N-type MOS transistor as a switch element. Hereinafter, details of each switch circuit will be described.
- FIG. 5 is a circuit diagram showing an example of a switch circuit using the P-type MOS transistor of the MUX circuit 30 as a switch element.
- the switch circuit has a bidirectional switch element composed of two P-type MOS transistors MP1 and MP2.
- the source terminals of MP1 and MP2 are connected in common, and the gate terminals are also connected in common.
- the drain terminal of MP1 is connected to the input terminal VIN on the battery voltage input terminal side, and the drain terminal of MP2 is connected to the output terminal VOUT on the signal output side of the MUX circuit.
- a diode D1 is inserted between the common source terminal and the gate terminal, and the anode is connected to the common gate terminal side and the cathode is connected to the common source terminal side.
- a Zener diode having a breakdown voltage equal to or higher than the ON voltage of the bidirectional switch element may be used in place of the diode D1.
- the switch circuit further includes an on-voltage generator 401, a current controller 402, and an off-accelerator 403.
- the on-voltage generator 401 is a source follower circuit composed of an N-type MOS transistor MN3 and a resistor R1 that is a voltage generating element.
- the gate terminal of MN3 is connected to the common source terminal of the bidirectional switch element, the drain terminal is connected to the power supply terminal VCC which is the highest potential, and the source terminal is connected to the common gate terminal of the bidirectional switch element via the resistor R1. Is done.
- An element other than a resistor may be used as the voltage generating element.
- a MOS transistor in which a bias voltage is applied to the gate terminal may be used, or a depletion type MOS transistor may be used as a current source.
- the depletion type MOS transistor here is a MOS transistor whose threshold value is adjusted so that a current is generated even when the potential difference between the gate and the source is 0V, for example.
- a resistance element may be inserted in series in each gate terminal and each drain terminal of the MN3 and the bidirectional switch elements MP1 and MP2 to prevent electrostatic breakdown.
- the current control unit 402 is applied with a bias voltage (BIAS), for example, and an N-type MOS transistor MN4 for supplying a current (2I) and an enable signal for controlling on / off of the bidirectional switch elements MP1 and MP2 (
- the N-type MOS transistor MN5 to which (ENABLE) is applied is connected to the cascode.
- the drain terminal of MN4 is connected to the gate terminals of bidirectional switch elements MP1 and MP2.
- the enable signal is a control signal from the control unit 50. Note that the connection relationship between MN4 and MN5 may be reversed.
- MN4 and MN6 for supplying current are configured by, for example, a current mirror circuit, but may be configured by a cascode current mirror circuit in order to suppress a current value fluctuation due to a channel length modulation effect.
- the current mirror circuit composed of MP3 and MP4 may be a cascode type current mirror circuit.
- the off-acceleration unit 403 is applied with a bias voltage (BIAS) common to MN4, and returns an N-type MOS transistor MN6 for supplying current (I) and a current (I) of MN6 to return the gate of the bidirectional switch element It comprises P-type MOS transistors MP3 and MP4 constituting a current mirror circuit for supplying to the terminal.
- BIAS bias voltage
- the drive current of the switch circuit is not supplied from the input terminal VIN side but from the power supply terminal VCC.
- a voltage drop due to on-resistance does not occur, and measurement errors can be reduced.
- the drive current is supplied from the power supply terminal VCC, the power consumption of each battery cell constituting the assembled battery is evenly performed, thus preventing the unbalanced power consumption between the battery cells as in the past. can do.
- the current I from the off-accelerator 403 flows into the source terminals of MP1 and MP2 via the diode D1, thereby charging the parasitic capacitance connected to the source terminal and setting the potential of the source terminal to the highest potential ( Lift to VCC).
- the effect of this is as follows. As described above, the voltage at both ends of the selected battery cell is input to the measurement unit 603 via the capacitor 602 in the measurement circuit 60, but the charge is transferred from the battery cell to the capacitor 602 via the switch circuit of the MUX circuit 30. By being charged, the voltage of the battery cell is input to the measurement unit 603.
- the off acceleration unit 403 prevents a state in which the signal potential on the drain terminal side of the bidirectional switch elements MP1 and MP2 is higher than the potential on the source terminal side, thereby preventing the movement of charges via the parasitic diode. Therefore, the OFF state can be further stabilized and measurement errors can be prevented from occurring.
- the drive current (2I) and the current value of the current (I) supplied from the off-acceleration unit do not have to be designed at a constant ratio, and the on-voltage generator 401 turns on the bidirectional switch element. As long as the difference voltage VGS can be generated, an arbitrary current value may be used.
- FIG. 6 is a circuit diagram showing an example of a switch circuit using the N-type MOS transistor of the MUX circuit 30 as a switch element.
- the switch circuit has a bidirectional switch element composed of two N-type MOS transistors MN1 and MN2.
- the source terminals of MN1 and MN2 are connected in common, and the gate terminals are also connected in common.
- the drain terminal of MN1 is connected to the input terminal VIN on the battery voltage input terminal side, and the drain terminal of MN2 is connected to the output terminal VOUT on the signal output side of the MUX circuit.
- a diode D2 is inserted between the common source terminal and the gate terminal, and the anode is connected to the common source terminal side and the cathode is connected to the common gate terminal side. If gate breakdown voltage protection is required, a Zener diode having a breakdown voltage higher than the on-voltage of the bidirectional switch element may be used instead of the diode D2.
- the switch circuit including the N-type bidirectional switch element further includes an on-voltage generator 404, a current controller 405, and an off-accelerator 406.
- the on-voltage generator 404 is a source follower circuit composed of a P-type MOS transistor MP5 and a resistor R2 that is a voltage generating element.
- the gate terminal of MP5 is connected to the common source terminal of the bidirectional switch element, the drain terminal is connected to the power supply terminal GND which is the lowest potential, and the source terminal is connected to the common gate terminal of the bidirectional switch element via the resistor R2. Is done.
- an element other than a resistor may be used as the voltage generating element.
- a resistance element may be inserted in series in each gate terminal and each drain terminal of MP5 and bidirectional switch elements MN1 and MN2 to prevent electrostatic breakdown.
- the current control unit 405 is applied with a bias voltage (BIAS), for example, an N-type MOS transistor MN4 for supplying a current (2I), and an enable signal for controlling on / off of the bidirectional switch elements MP1 and MP2 ( N-type MOS transistor MN4 to which (ENABLE) is applied, and P-type MOS transistors MP6 and MP7 constituting a current mirror circuit for turning back the current (2I) of MN4 and supplying it to the gate terminal of the bidirectional switch element, Composed.
- the enable signal is a control signal from the control unit 50 as described above.
- the gate terminals of MN1 and MN2 constituting the bidirectional switch element can sufficiently be switched on / off even when a low voltage is applied, the gate terminals of the bidirectional switch element are not connected via the current mirror circuits MP6 and MP7.
- a signal may be directly applied to the drive.
- the connection relationship between MN4 and MN5 may be reversed.
- MN4 and MN6 for supplying current are configured by a current mirror circuit, for example, but may be configured by a cascode type current mirror circuit in order to suppress a current value fluctuation due to a channel length modulation effect.
- the current mirror circuit composed of MP6 and MP7 may be a cascode type current mirror circuit.
- the off acceleration unit 406 includes an N-type MOS transistor MN6 to which a bias voltage (BIAS) common to MN4 is applied and generates a current (I) between the gate terminal and the GND terminal of the bidirectional switch element.
- BIAS bias voltage
- MN5 When the enable signal is set to a high level and an instruction to turn on the bidirectional switch element is given, MN5 is turned on, and a drive current 2I is generated by MN4.
- the drive current 2I flows into the node to which the common gate terminal of the bidirectional switch element is connected via the current mirror circuits MP6 and MP7, and a part of the drive current I flows to the off acceleration unit 406.
- the difference current I is drawn to the highest potential (GND) via the on-voltage generator 404.
- a potential difference VGS sufficient to turn on MN1 and MN2 is generated between the gate and source of the bidirectional switch element, whereby the voltage input terminal side of the battery and the output side of the MUX circuit are electrically connected.
- the drive current of the switch circuit is not supplied from the input terminal VIN side but from the power supply terminal VCC.
- a voltage drop due to on-resistance does not occur, and measurement errors can be reduced.
- the drive current is supplied from the power supply terminal VCC, the power consumption of each battery cell constituting the assembled battery is evenly performed, thus preventing the unbalanced power consumption between the battery cells as in the past. can do.
- the enable signal is set to a low level and the bidirectional switch element is instructed to be turned off
- MN5 is turned off and the drive current 2I does not flow.
- no current flows through the on-voltage generator 404, no potential difference occurs between the gate and source of the bidirectional switch elements MN1 and MN2, and the switch circuit is connected to the voltage input terminal side of the battery and the output side of the MUX circuit. Is opened electrically.
- the off acceleration unit 403 causes the current I to flow to the GND side, thereby pulling down the gate terminals of the bidirectional switch elements MN1 and MN2 to the highest potential (GND), thereby stabilizing the off state.
- the off-acceleration unit 404 extracts charges from the source terminals of MN1 and MN2 via the diode D2, thereby discharging the parasitic capacitance connected to the source terminal, and setting the potential of the source terminal to the lowest potential (GND). Pull down. This prevents the signal potential on the drain terminal side of MP1 and MP2 from becoming lower than the potential on the source terminal side and prevents the movement of charges via the parasitic diodes of MN1 and MN2, thereby preventing the bidirectional switch element. Is further stabilized. Note that the drive current (2I) and the current value of the current (I) supplied from the off-acceleration unit do not have to be designed at a constant ratio, as described above. An arbitrary current value may be used as long as the differential voltage VGS for turning on the switch element can be generated.
- FIG. 7 is a block diagram showing a configuration example of the MUX circuit 30 using two types of switch circuits.
- this figure shows the connection relationship up to the previous stage of the measurement circuit 60.
- a plurality of battery cells (external voltage source) 1 connected in series, the voltage input terminal 20, and the MUX circuit 30
- the connection relationship with the measurement circuit 60 is shown.
- a case where a low-pass filter (LPF) 3 is inserted between the plurality of battery cells VCL and the voltage input terminal 20 is shown as an example for noise removal.
- the low-pass filter 3 is composed of, for example, an external resistor and capacitor, but may be composed of an inductor or the like.
- the switch circuit is configured as follows.
- the negative electrode is connected to a plurality of continuous battery cells from the battery cell having a potential equal to or higher than a predetermined potential (VT) to the battery cell having the positive electrode at the highest potential.
- a switch circuit including a bidirectional switch element configured by commonly connecting the sources of two P-channel MOSFETs is used (PMOS switch group).
- PMOS switch group a switch circuit including a bidirectional switch element configured by commonly connecting the sources of two P-channel MOSFETs.
- a switch circuit of a P-type switch element in order for the bidirectional switch elements MP1 and MP2 to be turned on, a voltage range is required in the direction in which the gate voltages of MP1 and MP2 are lower than the source voltage. Therefore, a switch circuit of a P-type switch element is used as a switch circuit connected to a battery cell having a higher potential.
- the positive electrode is connected to a plurality of continuous battery cells from the battery cell in which the potential of the positive electrode is a predetermined potential (VT) or less to the battery cell having the lowest potential.
- a switch circuit including a bidirectional switch element configured by commonly connecting the sources of two N-channel MOSFETs is used (NMOS switch group).
- NMOS switch group a switch circuit including a bidirectional switch element configured by commonly connecting the sources of two N-channel MOSFETs.
- switch elements of the switch circuits SWP_1 to SWP_n that connect the positive electrode of the battery cell and the positive output of the output signal line of the MUX circuit 30 (the positive input terminal INP of the measurement circuit 60) are the same type of switch elements. That is, by making the type of the MOS transistor of the switch element that forms the negative signal path the same as the positive signal line that inputs the voltage of the selected battery cell to the measurement circuit 60, the on-resistance of the switch element is reduced. Configure to be equal.
- the switch connected to a plurality of continuous battery cells from the battery cell in which the potential of the negative electrode is equal to or higher than the predetermined potential (VT) to the battery cell in which the positive electrode is the highest potential.
- the circuit uses a switch circuit using a P-type MOS transistor as a switching element, and continues from a battery cell in which the potential of the positive electrode is a predetermined potential (VT) or less to a battery cell in which the negative electrode is the lowest potential.
- VT predetermined potential
- the predetermined potential VT is determined according to the input voltage range of the MUX circuit 30, the characteristics of the bidirectional switch element, the required specifications of the MUX circuit 30, and the like.
- FIGS. 1-10 An example of a system to which the voltage measuring device 2 is applied is shown in FIGS.
- FIG. 8 is a block diagram showing an example of a battery voltage measurement system for EV or HEV.
- the motor is driven by supplying power from the battery to both ends of the inverter for driving the motor.
- the battery device 10 constituting the voltage measurement system shown in the figure includes a battery 101 composed of an assembled battery in which a plurality of unit cells are connected in series, and several to dozens of battery cells constituting the battery. A plurality of voltage measuring devices 2 assigned to each battery cell 1 and a battery monitoring microcomputer (MCU) 6 are provided.
- the battery 101 is composed of several hundred unit cells in the whole vehicle such as an electric vehicle, for example, and the highest voltage is about 400V, for example.
- the unit cell constituting the battery 101 is, for example, a lithium ion battery.
- the battery monitoring microcomputer (MCU) 3 controls the voltage measuring device 2 to measure the battery voltage, and controls the power supply from the battery to the motor driving inverter based on the measurement result. Further, CAN communication or the like is performed with the battery control microcomputer 7.
- Each voltage measuring device 2 measures the voltage of a set of battery cells 1 to be measured among the batteries 101 by the method described above.
- the voltage measuring apparatus 2 further includes communication function units 70 and 71 in addition to the above-described function units.
- the communication function units 70 and 71 are used to control instructions, voltage measurement results, and the like from the battery monitoring microcomputer 6. Communicate with each other.
- FIG. 9 is a block diagram showing another example of a battery voltage measurement system for EV or HEV.
- the battery device 11 constituting the voltage measuring system shown in FIG. 1 is a set of several to dozens of battery cells constituting the battery 101, and the voltage measuring device 2 and the battery for each set of battery cells 1.
- a monitoring microcomputer (MCU) 6 is assigned. The voltage measurement is performed in the same manner as described above, but each voltage measurement instruction and voltage measurement result are exchanged between the voltage measuring device 2 and the battery monitoring microcomputer 6 corresponding to a set of battery cells 1. Between.
- the voltage measuring device 2 and the battery monitoring microcomputer 6 for each set of battery cells 1 may be, for example, an LSI formed on a separate semiconductor substrate, or may be a single chip formed on a single semiconductor substrate. LSI may be used.
- the voltage measuring apparatus 2 when the switch is in the on state, a voltage drop based on the drive current and the resistance component such as the on-resistance of the switch element in the signal path does not occur. Can be reduced. Further, since the drive current is supplied from the power supply terminal VCC, unbalanced power consumption between the unit cells can be prevented. Furthermore, the off-acceleration units 403 and 406 can further stabilize the off state of the bidirectional switch element. In addition, since the voltage measuring apparatus 2 according to the first embodiment does not employ the flying capacitor method, the capacitor 602 in the measurement circuit 60 needs to be a high voltage element, but the device such as the parasitic capacitance of the switch element of the switch circuit. The measurement error due to the measurement error and the measurement error due to the offset voltage of the OP amplifier or the like do not occur, so that a voltage measurement circuit with smaller measurement error can be realized.
- FIG. 10 is a circuit diagram showing another example of a switch circuit using a bidirectional switch element of a P-type MOS transistor.
- the same components as those of the switch circuit of FIG. 5 are denoted by the same reference numerals, and detailed description thereof is omitted.
- the switch circuit shown in FIG. 10 includes an off acceleration unit 407 controlled by an off signal (OFF) in response to an enable signal (ENABLE), instead of the off acceleration unit 403 configured to flow a constant current I.
- the off acceleration unit 407 includes an N-type MOS transistor MN7 whose gate terminal receives an off signal (OFF), and a resistance element R3 for adjusting a current value provided between the source terminal and the GND terminal of the MN7.
- the resistor R4 that converts the current flowing through the MN7 into voltage with respect to the power supply VCC and the voltage generated by the resistor R4 are input, and the power supply terminal VCC and the common gate terminal of the bidirectional switch element are connected in a switch manner.
- P-type MOS transistor MP8 is whose MOS transistor MN7 whose gate terminal receives an off signal (OFF), and a resistance element R3 for adjusting a current value provided between the source terminal and the GND terminal of the MN7.
- the resistor R4 that converts the current flowing through the
- FIG. 11 is an explanatory diagram showing an off signal in FIG.
- the off signal (OFF) is a signal that is set to high for a predetermined period after the enable signal (ENABLE) is switched from high to low.
- the off signal is one of control signals output from the control unit 50, for example, like the enable signal.
- the off acceleration unit 407 turns on MN7 and turns on the power supply VCC by the resistor R4.
- a reference voltage is generated, MP8 is turned on, and a large current instantaneously flows from the power supply VCC side to the gate terminals of the bidirectional switch elements MP1 and MP2.
- the gate terminal of the bidirectional switch element is raised to the highest potential, and the current flows through the diode D1, so that the source terminal of the bidirectional switch element is also raised to the highest potential.
- the bias current I is not passed when the switch element is on.
- the ON voltage of the switch element is determined based on the current I flowing through the resistors R1 and MN4. That is, since it is not necessary to consider the off-acceleration bias current I in determining the on-voltage of the bidirectional switch element, the design is facilitated and the accuracy of the on-voltage can be increased. In addition, since the bias current I is not passed unnecessarily, the current consumption can be further reduced.
- the current is generated by the MN7 to which the off signal is input and the resistor R3.
- the current is not limited to the configuration in FIG. 10, and the MN7 is operated as a bias current source when the off signal is applied by adjusting the voltage of the off signal. It may be configured.
- a MOS transistor in which a bias voltage is applied to the gate terminal may be used, or a depletion type MOS transistor may be used as a current source.
- the depletion type MOS transistor here is a MOS transistor whose threshold value is adjusted so that a current is generated even when the potential difference between the gate and the source is 0V, for example.
- FIG. 12 is a circuit diagram showing another example of a switch circuit using a bidirectional switch element of a P-type MOS transistor.
- the same components as those in the switch circuits of FIGS. 5 and 10 are denoted by the same reference numerals, and detailed description thereof is omitted.
- the switch circuit shown in FIG. 12 includes an off acceleration unit 408 controlled by an off signal (OFF) in response to an enable signal (ENABLE), instead of the off acceleration unit 403 configured to flow a constant current I.
- the off-accelerator 408 inputs an N-type MOS transistor MN8 and a P-type MOS transistor MP9 that constitute a logic circuit to which an off signal (OFF) is input, and an output of the logic circuit, and is bidirectional with the power supply terminal VCC.
- a P-type MOS transistor MP8 that switches-connects the common gate terminals of the switch elements.
- the inverter circuit is driven between a power supply VCC and a voltage based on the power supply VCC.
- the potential based on the power supply VCC is, for example, a potential generated so as to be 5 V lower than the power supply VCC.
- the power supply VCC reference potential is 5 V lower than the highest voltage, but this voltage can be set according to various conditions such as the withstand voltage of the element used.
- an inverter circuit composed of MN8 and MP9 is shown as the logic circuit. However, if MP8 can be controlled in accordance with an off signal, a more complex logic circuit is used. May be.
- FIG. 13 is an explanatory diagram showing an off signal in FIG.
- the OFF signal is, for example, a signal having a phase opposite to that of the enable signal (ENABLE), and is a signal that is set to HIGH only when the enable signal is LOW. is there.
- the off signal is one of control signals output from the control unit 50, for example, like the enable signal.
- the off-acceleration unit 408 turns on MP8 when a high-off signal is applied while the enable signal (ENABLE) is switched to Low, and the bidirectional switch element MP1 is turned on from the power supply VCC side. And a large current flows instantaneously into the gate terminal of MP2. As a result, the gate terminal of the bidirectional switch element is raised to the highest potential, and the current flows through the diode D1, so that the source terminal of the bidirectional switch element is also raised to the highest potential. With the above operation, the state where the potential on the drain terminal side of the bidirectional switch element is higher than the potential on the source terminal side can be prevented, and the OFF state of the bidirectional switch element can be further stabilized. In addition, it is possible to shift to a stable state at a higher speed than when charging with a constant current.
- the bias current I is not supplied from the off acceleration circuit 408 when the switch element is turned on. This eliminates the need to consider the off-acceleration bias current I in determining the on-voltage of the bidirectional switch element, thereby facilitating the design and improving the accuracy of the on-voltage. In addition, since the bias current I is not passed unnecessarily, the current consumption can be further reduced.
- FIG. 14 is a circuit diagram showing another example of a switch circuit using a bidirectional switch element of an N-type MOS transistor.
- the same components as those in the switch circuit of FIG. 6 are denoted by the same reference numerals, and detailed description thereof is omitted.
- the off acceleration unit 409 includes an off acceleration unit 409 that is controlled by an off signal (OFF) corresponding to an enable signal (ENABLE), instead of the off acceleration unit 406 configured to flow a constant current I.
- the off acceleration unit 409 includes an N-type MOS transistor MN9 having an off signal (OFF) input to the gate terminal, a source terminal connected to the GND terminal, and a drain terminal connected to the common gate terminal of the bidirectional switch element. Is done.
- FIG. 15 is an explanatory diagram showing an off signal (OFF) in FIG.
- the OFF signal (OFF) is, for example, a signal having a phase opposite to that of the enable signal (ENABLE), and is a signal that is set to HIGH only when the enable signal is LOW. is there.
- the off signal is one of control signals output from the control unit 50, for example, like the enable signal.
- the off acceleration unit 409 turns on MN9 and turns on the gates of the bidirectional switch elements MP1 and MP2 when an off signal that becomes high during the period when the enable signal (ENABLE) is switched to low is applied.
- a large current flows instantaneously from the terminal side to the power supply GND side.
- the gate terminal of the bidirectional switch element is pulled down to the lowest potential, and the current flows through the diode D2, whereby the source terminal of the bidirectional switch element is also pulled down to the lowest potential.
- the bias current I is not supplied from the off acceleration circuit 409 when the switch element is turned on. This eliminates the need to consider the off-acceleration bias current I in determining the on-voltage of the bidirectional switch element, thereby facilitating the design and improving the accuracy of the on-voltage. In addition, since the bias current I is not passed unnecessarily, the current consumption can be further reduced.
- the source terminal of MN9 is directly connected to the GND terminal.
- the present invention is not limited to this, and a resistance element for adjusting the current value may be inserted between the source terminal and the GND terminal.
- the MN9 may be operated as a bias current source when the off signal is applied by adjusting the voltage of the off signal. With these configurations, the peak current during discharge is reduced, which contributes to the reduction of system noise radiation.
- the off signal is not limited to the pulse shown in FIG. 15, and may be a short-time pulse as shown in FIG. 11, or the pulse is not limited to once but may be applied a plurality of times.
- FIG. 16 is a block diagram illustrating an example of the case where the power supply of the voltage measuring device 2 is supplied from another power source.
- the power supply of the voltage measuring device 2 is performed from the highest voltage of the plurality of battery cells VCL connected in series.
- the power source is supplied from a different power source different from the plurality of battery cells. Supply.
- the voltage measuring device 2 when the voltage measuring device 2 is applied to a voltage measuring system for an EV or HEV battery, power is supplied from a voltage VA generated based on a lead battery power source mounted to drive a vehicle-mounted illumination or the like. To do.
- a plurality of voltage measuring devices 2 are used. Since the GND voltages are also different, the power supply circuit cannot be electrically connected directly.
- the voltage VA is stepped up or stepped down using the isolated DC / DC converter 5 in order to supply energy by electrically insulating the voltage VA generated by stepping up or stepping down the voltage of a lead battery power source or the like.
- the voltage VCC is supplied to the voltage measuring device 2.
- the power supply voltage VCC supplies a voltage equal to or higher than the highest voltage of the plurality of battery cells connected in series. For example, assuming that the voltage of the battery cell is 4.3 V at the maximum with respect to the voltage measuring device when twelve lithium ion batteries are connected in series, the power supply voltage VCC needs to be 52 V or more. Therefore, the output voltage of the insulation type DC / DC converter 5 is adjusted so as to supply, for example, about 55 V as the power supply voltage VCC.
- the drive current of the switch circuit in the MUX circuit 30 of the voltage measuring device 2 is not supplied from the plurality of battery cells connected in series, the power of the plurality of battery cells is measured in the voltage measurement operation of the battery cell. Consumption can be suppressed, and reduction in battery sustainability due to imbalance in battery energy consumption of battery cells can also be prevented.
- Embodiment 6 In the first embodiment, the voltage measuring device 2 having a configuration that does not use a flying capacitor is shown. However, the MUX circuit 30 including the switch circuit can also be applied to a flying capacitor type voltage measuring device.
- FIG. 17 is a block diagram showing an example of a flying capacitor type voltage measuring apparatus to which the MUX circuit 30 is applied.
- the voltage measurement device 4 shown in the figure includes a MUX circuit 30, a flying capacitor C1, a voltage input switch unit 80, an OP amplifier (buffer amplifier) U1 that constitutes a buffer, a measurement circuit 61, and a control unit. 51.
- the measurement circuit 61 includes a delta-sigma type AD conversion circuit or a SAR (Successive Application Register) type AD conversion circuit.
- the voltage of the positive electrode of the highest battery cell VCL_1 among the plurality of battery cells VCL is input to the power supply terminal VCC of the voltage measuring device 4, and the power supply terminal GND includes, for example, the plurality of battery cells VCL. Among them, the voltage of the negative electrode of the lowest battery cell VCL_n is input.
- FIG. 18 is a timing chart showing an example of operation timing of the voltage measuring device 4 shown in FIG.
- the control unit 51 first controls the MUX circuit 30 at the timing of reference numeral 501 to turn on the switch circuits SWP_1 and SWN_1. As a result, the voltage of the battery cell VCL_1 is input to both ends of the flying capacitor C1. After the input voltage is stabilized, the control unit 51 turns off the switch circuits SWP_1 and SWN_1 at the timing of reference numeral 502, and causes the flying capacitor C1 to float. At the timing indicated by reference numeral 503, the control unit 51 turns on the switch circuit SWB and connects one electrode of the flying capacitor C1 to the negative side input terminal INN (GND potential) of the measurement circuit 61.
- INN negative side input terminal
- the control unit 51 controls the measurement circuit 61 at the timing of reference numeral 505 to execute voltage measurement.
- the control unit 51 turns off the switch circuits SWA and SWB at the timing indicated by reference numeral 506.
- the control unit 51 controls the MUX circuit 30 at the timing of reference numeral 507 to turn on the switch circuits SWP_2 and SWN_2.
- the control unit 51 turns off the switch circuits SWP_1 and SWN_1 at the timing indicated by reference numeral 508, and causes the flying capacitor C1 to float.
- the control unit 51 turns on the switch circuit SWB and connects one electrode of the flying capacitor C1 to the negative side input terminal INN (GND potential) of the measurement circuit 61.
- the switch circuit SWA is turned on at the timing of reference numeral 510, and the voltage of the flying capacitor C1 is input to the measurement circuit 61 via the buffer amplifier U1.
- control unit 51 controls the measurement circuit 61 at the timing indicated by reference numeral 511 to execute voltage measurement.
- the control unit 51 turns off the switch circuits SWA and SWB at the timing of reference numeral 512.
- the voltage of all the battery cells of the unit cells connected in series is measured by repeatedly executing the above operation.
- the measurement circuit 60 can be configured without using a high voltage element by applying the flying capacitor type voltage measurement device 4 as the voltage measurement device.
- the MUX circuit 30 is applied to the voltage measuring device 4, as in the first embodiment, generation of measurement error due to a voltage drop based on the driving current of the switch circuit and the resistance component such as the on-resistance of the signal path. , Prevention of unbalanced power consumption between battery cells, and further stabilization of the OFF state of the switch element.
- the voltage measuring device is applied to a battery voltage measuring system such as an electric vehicle
- a digital camera, notebook PC, electric tool, electric assist bicycle It can also be applied to the measurement of the battery voltage of products using multi-straight batteries such as electric motorcycles.
- the lithium ion battery was illustrated as a battery cell which comprises an external voltage source, it is not restricted to this, It can apply also to various batteries, such as a nickel metal hydride battery and a fuel battery.
- the switch circuit according to Embodiments 1 to 6 is applied to the MUX circuit 30 in the voltage measuring device is illustrated, the present invention is not limited to this, and if it is used as a switch, it may be applied to circuits for other purposes. Can do.
- the present invention relates to a switch circuit, a selection circuit, and a voltage measurement device, and in particular, can be widely applied to a voltage measurement device that selects and measures one voltage from a plurality of voltages.
- VCL_1 to VCL_n Battery cell 1 A set of battery cells 2, 4 Voltage measuring device 3 External LPF 20 Voltage input terminal 30 Multiplexer circuit (MUX circuit) SWP_1 to SWP_n Switch circuits for connecting the positive electrode of the battery cell and the positive input terminal of the measurement circuit SWN_1 to SWN_n
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Abstract
Description
先ず、本願において開示される発明の代表的な実施の形態について概要を説明する。代表的な実施の形態についての概要説明で括弧を付して参照する図面中の参照符号はそれが付された構成要素の概念に含まれるものを例示するに過ぎない。
本発明の代表的な実施の形態に係るスイッチ回路(SWP、SWN)は、入力端子(VIN)と出力端子(VOUT)の間に設けられたスイッチ素子(MP1及びMP2、又はMN1及びMN2)と、前記スイッチ素子のオンオフを指示する制御信号(ENABLE)に基づいて、前記スイッチ素子を駆動するスイッチ駆動部(401~409)とを有する。前記スイッチ駆動部は、前記入力端子に供給される入力電圧を挟んで相互に異なる第1電源電圧(VCC又はGND)と第2電源電圧(GND又はVCC)との間で駆動される。また、前記スイッチ駆動部は、前記第1電源電圧が供給される第1電源端子側にドレイン側が接続され、前記入力電圧に応じた電圧を入力し、出力側に生じた電圧を前記スイッチ素子を駆動するための駆動電圧として前記スイッチ素子に供給するソースフォロア回路(401、404)と、前記制御信号に応じて前記ソースフォロア回路の出力側と前記第2電源電圧が供給される第2電源端子との間の電流経路を開閉する電流制御部(402、405)とを有する。
項1のスイッチ回路において、前記スイッチ素子は、ドレイン端子が前記入力端子側に接続され、ゲート端子に前記駆動電圧が供給される第1導電型の第1MOSトランジスタ(MP1又はMN2)と、ドレイン端子が前記出力端子側に接続され、ゲート端子が前記第1MOSトランジスタのゲート端子側に接続され、ソース端子が前記第1MOSトランジスタのソース端子と共通に接続される第1導電型の第2MOSトランジスタ(MP2又はMN2)と、を有する。前記ソースフォロア回路は、ドレイン端子が前記第1電源端子側に接続され、ゲート端子が前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子側に接続される第2導電型の第3MOSトランジスタ(MN3又はMP5)と、一端が前記第3MOSトランジスタのソース端子側に接続され、他端が前記第1MOSトランジスタ及び前記第2MOSトランジスタのゲート端子側に接続され、供給された電流に応じて両端に電圧を生成する電圧生成部(402、405)とを有する。前記電流制御部は、前記制御信号が前記スイッチ素子のオンを指示する場合には、前記電圧生成部の他端と前記第2電源端子との間の電流経路を開き、前記制御信号が前記スイッチ素子のオフを指示する場合には当該電流経路を閉じる。
項1又は2のスイッチ回路において、前記スイッチ駆動部は、前記電流制御部によって形成された電流経路に流れる電流よりも小さい電流が流れる電流経路を、前記第1電源端子と第1MOSトランジスタ及び第2MOSトランジスタのソース端子との間に前記電圧生成部の他端、並びに、前記第1MOSトランジスタ及び前記第2MOSトランジスタのゲート端子を介して形成するオフ加速部(403、406)と、を更に有する。
項1又は2のスイッチ回路において、前記スイッチ駆動部は、前記電流制御部が電流経路を閉じている期間のうち所定の期間に前記第1電源端子と第1MOSトランジスタ及び第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して形成するオフ加速部(407~409)と、を更に有する。
項4のスイッチ回路において、前記オフ加速部が電流経路を形成する期間は、前記電流制御部が電流経路を閉じている期間のうち一部の期間(図11のオフ信号のハイレベル期間)である。
項4のスイッチ回路において、前記オフ加速部が電流経路を形成する期間は、前記電流制御部が電流経路を閉じている期間に対応する期間(図13又は図15のオフ信号のハイレベル期間)である。
項2乃至6のいずれかのスイッチ回路において、前記第1電源電圧は、前記入力電圧以上の電圧値(VCC)とされ、前記第1導電型はPチャネル型であり、前記第2導電型はNチャネル型である。
項2乃至6のいずれかのスイッチ回路において、前記第1電源電圧はグラウンド電圧とされ、前記第2電源電圧は前記入力電圧以上の電圧値(VCC)とされ、前記第1導電型はNチャネル型であり、前記第2導電型はPチャネル型である。
本発明の代表的な実施の形態に係る選択回路(30)は、一端と他端が接続されて組電池を構成する複数個の素電池(VCL_1~VCL_n)のうち1又は複数の素電池から構成されるブロックを1単位とし、入力された制御信号に応じて、いずれかの前記ブロックの両端に接続される信号線を選択して第1出力端子(INP(+))と第2出力端子(INN(-))に接続する。前記選択回路は、前記ブロックの一端(電池セルVCLの正側電極)に接続される信号線が接続される入力端子(VIN)と前記第1出力端子に接続される信号線が接続される出力端子(VOUT)とを有して、前記制御信号に応じて当該入力端子と当該出力端子とを電気的に接続する第1スイッチ回路(SWP)と、前記ブロックの他端(電池セルVCLの負側電極)に接続される信号線が接続される入力端子(VIN)と前記第2出力端子に接続される信号線が接続される出力端子(VOUT)とを有して、前記制御信号に応じて当該入力端子と当該出力端子とを電気的に接続する第2スイッチ回路(SWN)とを夫々の前記ブロックに対応して有する。また、前記第1スイッチ回路及び前記第2スイッチ回路は、当該スイッチ回路の入力端子と出力端子の間に設けられたスイッチ素子(MP1及びMP2、又はMN1及びMN2)と、前記制御信号に応じて前記スイッチ素子を駆動するスイッチ駆動部(401~409)と、を有する。前記スイッチ駆動部は、前記第1電源電圧(VCC又はGND)が供給される第1電源端子と、前記第2電源電圧(GND又はVCC)が供給される第2電源端子との間に配置され、前記入力電圧に応じた電圧を入力し、出力側に生じた電圧を前記スイッチ素子を駆動するための駆動電圧として前記スイッチ素子に供給するソースフォロア回路(401、404)と、前記制御信号に応じて、前記第1電源端子と前記第2電源端子との間の前記ソースフォロア回路が配置された電流経路を開閉する電流制御部(402、405)とを有する。
項9の選択回路において、前記第1電源電圧は、前記組電池を構成する素電池のうち最高位の素電池の一端の電圧に応じた電圧(VCL_1の正側電極の電圧)である。
項10の選択回路において、前記スイッチ素子は、ゲート端子が前記駆動電圧により制御されるP型のMOSトランジスタ(MP1、MP2)又はN型のMOSトランジスタ(MN1、MN2)を有し、前記ブロックに対応される前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子のトランジスタの種類は同一とされる。
項9乃至11のいずれかの選択回路において、前記ブロックのうち前記他端の電位が所定の電位(VT)以上となる第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子は、P型のMOSトランジスタ(MP1、MP2)とされ、前記ブロックのうち前記他端の電位が前記所定の電位より低い第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子は、N型のMOSトランジスタ(MN1、MN2)とされる。
項12の選択回路において、前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ素子は、ドレイン端子が前記入力端子側に接続され、ゲート端子に前記駆動電圧が供給されるP型の第1MOSトランジスタ(MP1)と、ドレイン端子が前記出力端子側に接続され、ゲート端子が前記第1MOSトランジスタのゲート端子側に接続され、ソース端子が前記第1MOSトランジスタのソース端子と共通に接続されるP型の第2MOSトランジスタ(MP2)と、を有する。また、前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記ソースフォロア回路(401)は、ドレイン端子が前記第1電源端子側に接続され、ゲート端子が前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子側に接続されるN型の第3MOSトランジスタ(MN3)と、一端が前記第3MOSトランジスタのソース端子側に接続され、他端が前記第1MOSトランジスタ及び前記第2MOSトランジスタのゲート端子側に接続され、供給された電流に応じて両端に電圧を生成する電圧生成部(R1)とを有する。更に、前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記電流制御部(402)は、前記制御信号(ENABLE)が前記スイッチ素子のオンを指示する場合には、前記電圧生成部の他端と前記第2電源端子(GND)との間の電流経路を開き、前記制御信号が前記スイッチ素子のオフを指示する場合には当該電流経路を閉じる。
項12又は13の選択回路において、前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ素子は、ドレイン端子が前記入力端子側に接続され、ゲート端子に前記駆動電圧が供給されるN型の第4MOSトランジスタ(MN1)と、ドレイン端子が前記出力端子側に接続され、ゲート端子が前記第4MOSトランジスタのゲート端子側に接続され、ソース端子が前記第4MOSトランジスタのソース端子と共通に接続されるN型の第5MOSトランジスタ(MN2)と、を有する。また、前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記ソースフォロア回路(404)は、ドレイン端子が前記第2電源端子側に接続され、ゲート端子が前記第4MOSトランジスタ及び前記第5MOSトランジスタのソース端子側に接続されるP型の第6MOSトランジスタ(MP5)と、一端が前記第6MOSトランジスタのソース端子側に接続され、他端が前記第4MOSトランジスタ及び前記第5MOSトランジスタのゲート端子側に接続され、供給された電流に応じて両端に電圧を生成する電圧生成部(R2)と、を有する。更に、前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記電流制御部は、前記制御信号が前記スイッチ素子のオンを指示する場合には、前記電圧生成部の他端と前記第1電源端子(VCC)との間の電流経路を開き、前記制御信号が前記スイッチ素子のオフを指示する場合には当該電流経路を閉じる。
項12乃至14のいずれかの選択回路において、前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ駆動部は、前記電流制御部によって形成される電流経路に流れる電流よりも小さい電流が流れる電流経路を、前記第1電源端子(VCC)と前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して形成するオフ加速部(403)と、を更に有する。
項12乃至14のいずれかの選択回路において、前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ駆動部は、前記電流制御部が電流経路を閉じている期間に、前記第1電源端子と前記第1MOSトランジスタ及び第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して形成するオフ加速部(407、408)と、を更に有する。
項12乃至16のいずれかの選択回路において、前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ駆動部は、前記電流制御部によって形成される電流経路に流れる電流よりも小さい電流が流れる電流経路を前記第2電源端子と前記第4MOSトランジスタ及び前記第5MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して形成するオフ加速部(406)と、を更に有する。
項12乃至16のいずれかの選択回路において、前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ駆動部は、前記電流制御部が電流経路を閉じている期間に前記第2電源端子と前記第4MOSトランジスタ及び前記第5MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して形成するオフ加速部(409)と、を更に有する。
本発明の代表的な実施の形態に係る電圧測定装置(2)は、一端と他端が接続されて組電池を構成する複数個の素電池(VCL_1~VCL_n)のうち1又は複数の素電池から構成されるブロックを1単位とし、1ブロック毎に前記ブロックの両端の電圧を測定するための電圧測定装置である。前記電圧測定装置は、入力された制御信号に応じて、前記ブロックの両端に接続される信号線を1ブロック毎に選択して第1出力端子(INP(+))と第2出力端子(INN(-))に接続する選択部(30)と、前記第1出力端子と前記第2出力端子の電圧を入力して、両端子間の電圧を測定する測定部(60)と、を有する。前記選択部は、前記ブロックの一端(電池セルの正側電極)に接続される信号線が接続される入力端子(VIN)と前記第1出力端子に接続される信号線が接続される出力端子(VOUT)とを有して前記制御信号に応じて前記入力端子と前記出力端子とを電気的に接続する第1スイッチ回路(SWP)と、前記ブロックの他端(電池セルの負側電極)に接続される信号線が接続される入力端子(VIN)と前記第2出力端子に接続される信号線が接続される出力端子(VOUT)とを有して前記制御信号に応じて前記入力端子と前記出力端子とを電気的に接続する第2スイッチ回路(SWN)と、を夫々の前記ブロックに対応して有する。また、前記第1スイッチ回路及び前記第2スイッチ回路は、当該スイッチ回路の入力端子(VIN)と出力端子(VOUT)との間に設けられたスイッチ素子(MP1及びMP2、又はMN1及びMN2)と、前記制御信号に応じて前記スイッチ素子を駆動するスイッチ駆動部(401~409)と、を有する。前記スイッチ駆動部は、前記第1電源電圧VCC又はGND)が供給される第1電源端子と、前記第2電源電圧(GND又はVCC)が供給される第2電源端子との間に配置され、前記入力電圧に応じた電圧を入力し、出力側に生じた電圧を前記スイッチ素子を駆動するための駆動電圧として前記スイッチ素子に供給するソースフォロア回路(401、404)と、前記制御信号に応じて、前記第1電源端子と前記第2電源端子との間の前記ソースフォロア回路が配置された電流経路を開閉する電流制御部(402、405)と、を有する。
項19の電圧測定装置において、前記第1電源電圧は、前記組電池を構成する素電池のうち最高位の素電池の一端の電圧に応じた電圧(VCL_1の正側電極の電圧)である。
項19又は20の電圧測定装置において、前記スイッチ素子は、ゲート端子が前記駆動電圧により制御されるP型のMOSトランジスタ(MP1、MP2)又はN型のMOSトランジスタ(MN1、MN2)を有し、前記ブロックに対応される前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子のトランジスタの種類は同一とされる。
項19乃至21のいずれかの電圧測定装置において、前記ブロックのうち前記他端の電位が所定の電位(VT)以上となる第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子は、P型のMOSトランジスタ(MP1、MP2)とされ、前記ブロックのうち前記他端の電位が前記所定の電位より低い第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子は、N型のMOSトランジスタ(MN1、MN2)とされる。
項22の電圧測定装置において、前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ素子は、ドレイン端子が前記入力端子側に接続され、ゲート端子に前記駆動電圧が供給されるP型の第1MOSトランジスタ(MP1)と、ドレイン端子が前記出力端子側に接続され、ゲート端子が前記第1MOSトランジスタのゲート端子側に接続され、ソース端子が前記第1MOSトランジスタのソース端子と共通に接続されるP型の第2MOSトランジスタ(MP2)と、有する。また、前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記ソースフォロア回路(401)は、ドレイン端子が前記第1電源端子側に接続され、ゲート端子が前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子側に接続されるN型の第3MOSトランジスタ(MN3)と、一端が前記第3MOSトランジスタのソース端子側に接続され、他端が前記第1MOSトランジスタ及び前記第2MOSトランジスタのゲート端子側に接続され、供給された電流に応じて両端に電圧を生成する電圧生成部(R1)と、を有する。前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記電流制御部は、前記制御信号が前記スイッチ素子のオンを指示する場合には、前記電圧生成部の他端と前記第2電源端子(GND)との間の電流経路を開き、前記制御信号が前記スイッチ素子のオフを指示する場合には当該電流経路を閉じる。
項22又は23の電圧測定装置において、前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ素子は、ドレイン端子が前記入力端子側に接続され、ゲート端子に前記駆動電圧が供給されるN型の第4MOSトランジスタ(MN1)と、ドレイン端子が前記出力端子側に接続され、ゲート端子が前記第4MOSトランジスタのゲート端子側に接続され、ソース端子が前記第4MOSトランジスタのソース端子と共通に接続されるN型の第5MOSトランジスタ(MN2)と、を有する。また、前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記ソースフォロア回路(404)は、ドレイン端子が前記第2電源端子側に接続され、ゲート端子が前記第4MOSトランジスタ及び前記第5MOSトランジスタのソース端子側に接続されるP型の第6MOSトランジスタ(MP5)と、一端が前記第6MOSトランジスタのソース端子側に接続され、他端が前記第4MOSトランジスタ及び前記第5MOSトランジスタのゲート端子側に接続され、供給された電流に応じて両端に電圧を生成する電圧生成部(R2)と、を有する。更に、前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記電流制御部(405)は、前記制御信号が前記スイッチ素子のオンを指示する場合には、前記電圧生成部の他端と前記第1電源端子(VCC)との間の電流経路を開き、前記制御信号が前記スイッチ素子のオフを指示する場合には当該電流経路を閉じる。
項22乃至24のいずれかの電圧測定装置において、前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ駆動部は、前記電流制御部によって形成される電流経路に流れる電流よりも小さい電流が流れる電流経路を、前記第1電源端子と前記第1MOSトランジスタ及び第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して形成するオフ加速部(403)、を更に有する。
項22乃至24のいずれかの電圧測定装置において、前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ駆動部は、前記電流制御部が電流経路を閉じている期間に、前記第1電源端子と前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して電流経路を形成するオフ加速部と、を更に有する。
項22乃至26のいずれかの電圧測定装置において、前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ駆動部は、前記電流制御部によって形成される電流経路に流れる電流よりも小さい電流が流れる電流経路を、前記第2電源端子と前記第4MOSトランジスタ及び前記第5MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して形成するオフ加速部(406)、を更に有する。
項22乃至26のいずれかの電圧測定装置において、前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路の前記スイッチ駆動部は、前記電流制御部が電流経路を閉じている期間に、前記第2電源端子と前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して電流経路を形成するオフ加速部と、を更に有する。
項19乃至28のいずれかの電圧測定装置において、前記測定部は、デルタ・シグマ方式のアナログデジタル変換器(601~603)を有する。
実施の形態について更に詳述する。
図1は、実施の形態1に係る電圧測定装置の一例を示すブロック図である。
図10は、P型MOSトランジスタの双方向スイッチ素子を用いたスイッチ回路の別の一例を示す回路図である。図5のスイッチ回路と同様の構成要素には同一の符号を付してその詳細な説明を省略する。
図12は、P型MOSトランジスタの双方向スイッチ素子を用いたスイッチ回路の別の一例を示す回路図である。図5及び図10のスイッチ回路と同様の構成要素には同一の符号を付してその詳細な説明を省略する。
図14は、N型MOSトランジスタの双方向スイッチ素子を用いたスイッチ回路の別の一例を示す回路図である。図6のスイッチ回路と同様の構成要素には同一の符号を付してその詳細な説明を省略する。
図16は、電圧測定装置2の電源供給を別電源から供給する場合の一例を示すブロック図である。
実施の形態1では、フライングキャパシタを用いない構成の電圧測定装置2を示したが、前記スイッチ回路を備えるMUX回路30をフライングキャパシタ方式の電圧測定装置にも適用することができる。
1 一組の電池セル
2、4 電圧測定装置
3 外付けLPF
20 電圧入力端子
30 マルチプレクサ回路(MUX回路)
SWP_1~SWP_n 電池セルの正側電極と計測回路の正側の入力端子を接続するためのスイッチ回路
SWN_1~SWN_n 電池セルの負側電極と計測回路の負側の入力端子を接続するためのスイッチ回路
40 保護用ダイオード
50、51 制御部
60、61 計測回路
INP(+) 正側の入力端子
INN(-) 負側の入力端子
601 スイッチ部
602 容量
603 計測部
201~206 動作タイミング
401、404 オン電圧生成部
402、405 電流制御部
403、406~409 オフ加速部
MP1、MP2 双方向スイッチ素子(P型MOSトランジスタ)
MN1、MN2 双方向スイッチ素子(N型MOSトランジスタ)
MN3~MN9 N型MOSトランジスタ
MP3~MP9 P型MOSトランジスタ
R1~R4 抵抗素子
D1、D2 ダイオード
VIN スイッチ回路の入力端子
VOUT スイッチ回路の出力端子
101 バッテリ
10、11 バッテリ装置
70、71、72 通信機能部
5 絶縁型DC/DCコンバータ
6 電池監視用マイクロコンピュータ
7 電池制御用マイクロコンピュータ
VA 鉛バッテリ等に基づいて生成される電圧
80 スイッチ部
SWA、SWB スイッチ回路
U1 バッファアンプ
501~512 動作タイミング
VCC 電源電圧、電源電圧端子
GND グラウンド電圧、グラウンド端子
VT スイッチ回路の種別を決定するための基準となる電圧
Claims (29)
- 入力端子と出力端子の間に設けられたスイッチ素子と、
前記スイッチ素子のオンオフを指示する制御信号に基づいて、前記スイッチ素子を駆動するスイッチ駆動部と、を有し、
前記スイッチ駆動部は、前記入力端子に供給される入力電圧を挟んで、相互に異なる第1電源電圧と第2電源電圧との間で駆動され、
前記第1電源電圧が供給される第1電源端子側にドレイン側が接続され、前記入力電圧に応じた電圧を入力し、出力側に生じた電圧を前記スイッチ素子を駆動するための駆動電圧として前記スイッチ素子に供給するソースフォロア回路と、
前記制御信号に応じて、前記ソースフォロア回路の出力側と前記第2電源電圧が供給される第2電源端子との間の電流経路を開閉する電流制御部と、を有するスイッチ回路。 - 前記スイッチ素子は、ドレイン端子が前記入力端子側に接続され、ゲート端子に前記駆動電圧が供給される第1導電型の第1MOSトランジスタと、
ドレイン端子が前記出力端子側に接続され、ゲート端子が前記第1MOSトランジスタのゲート端子側に接続され、ソース端子が前記第1MOSトランジスタのソース端子と共通に接続される第1導電型の第2MOSトランジスタと、を有し、
前記ソースフォロア回路は、ドレイン端子が前記第1電源端子側に接続され、ゲート端子が前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子側に接続される第2導電型の第3MOSトランジスタと、
一端が前記第3MOSトランジスタのソース端子側に接続され、他端が前記第1MOSトランジスタ及び前記第2MOSトランジスタのゲート端子側に接続され、供給された電流に応じて両端に電圧を生成する電圧生成部と、を有し、
前記電流制御部は、前記制御信号が前記スイッチ素子のオンを指示する場合には、前記電圧生成部の他端と前記第2電源端子との間の電流経路を開き、前記制御信号が前記スイッチ素子のオフを指示する場合には当該電流経路を閉じる、請求項1記載のスイッチ回路。 - 前記スイッチ駆動部は、前記電流制御部によって形成された電流経路に流れる電流よりも小さい電流が流れる電流経路を、前記第1電源端子と前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子との間に、前記電圧生成部の他端、並びに、前記第1MOSトランジスタ及び前記第2MOSトランジスタのゲート端子を介して形成するオフ加速部と、を更に有する請求項2記載のスイッチ回路。
- 前記スイッチ駆動部は、前記電流制御部が電流経路を閉じている期間に前記第1電源端子と前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して電流経路を形成するオフ加速部と、を更に有する請求項2記載のスイッチ回路。
- 前記オフ加速部が電流経路を形成する期間は、前記電流制御部が電流経路を閉じている期間のうち一部の期間である、請求項4記載のスイッチ回路。
- 前記オフ加速部が電流経路を形成する期間は、前記電流制御部が電流経路を閉じている期間に対応する期間である、請求項4記載のスイッチ回路。
- 前記第1電源電圧は、前記入力電圧以上の電圧値とされ、
前記第1導電型はPチャネル型であり、前記第2導電型はNチャネル型である、請求項3記載のスイッチ回路。 - 前記第1電源電圧はグラウンド電圧とされ、前記第2電源電圧は前記入力電圧以上の電圧値とされ、
前記第1導電型はNチャネル型であり、前記第2導電型はPチャネル型である、請求項3記載のスイッチ回路。 - 素電池の一端と他端が接続されて組電池を構成する複数個の素電池のうち1又は複数の素電池から構成されるブロックを1単位とし、入力された制御信号に応じて、いずれかの前記ブロックの両端に接続される信号線を選択して第1出力端子と第2出力端子に接続する選択回路であって、
前記ブロックの一端に接続される信号線が接続される入力端子と前記第1出力端子に接続される信号線が接続される出力端子とを有し、前記制御信号に応じて当該入力端子と当該出力端子とを電気的に接続する第1スイッチ回路と、
前記ブロックの他端に接続される信号線が接続される入力端子と前記第2出力端子に接続される信号線が接続される出力端子とを有し、前記制御信号に応じて当該入力端子と当該出力端子とを電気的に接続する第2スイッチ回路と、を夫々の前記ブロックに対応して有し、
前記第1スイッチ回路及び前記第2スイッチ回路は、当該スイッチ回路の入力端子と出力端子の間に設けられたスイッチ素子と、前記制御信号に応じて前記スイッチ素子を駆動するスイッチ駆動部と、を有し、
前記スイッチ駆動部は、前記入力端子に供給される入力電圧を挟んで、相互に異なる第1電源電圧と第2電源電圧との間で駆動され、
前記第1電源電圧が供給される第1電源端子と、前記第2電源電圧が供給される第2電源端子との間に配置され、前記入力電圧に応じた電圧を入力し、出力側に生じた電圧を前記スイッチ素子を駆動するための駆動電圧として前記スイッチ素子に供給するソースフォロア回路と、
前記制御信号に応じて、前記第1電源端子と前記第2電源端子との間の前記ソースフォロア回路が配置された電流経路を開閉する電流制御部と、を有する選択回路。 - 前記第1電源電圧は、前記組電池を構成する素電池のうち最高位の素電池の一端の電圧に応じた電圧である、請求項9記載の選択回路。
- 前記スイッチ素子は、ゲート端子が前記駆動電圧により制御されるP型のMOSトランジスタ又はN型のMOSトランジスタを有し、
前記ブロックに対応される前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子のトランジスタの種類は同一とされる、請求項10記載の選択回路。 - 前記ブロックのうち前記他端の電位が所定の電位以上となる第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子は、P型のMOSトランジスタとされ、
前記ブロックのうち前記他端の電位が前記所定の電位より低い第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子は、N型のMOSトランジスタとされる、請求項11記載の選択回路。 - 前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ素子は、ドレイン端子が前記入力端子側に接続され、ゲート端子に前記駆動電圧が供給されるP型の第1MOSトランジスタと、ドレイン端子が前記出力端子側に接続され、ゲート端子が前記第1MOSトランジスタのゲート端子側に接続され、ソース端子が前記第1MOSトランジスタのソース端子と共通に接続されるP型の第2MOSトランジスタと、を有し、
前記ソースフォロア回路は、ドレイン端子が前記第1電源端子側に接続され、ゲート端子が前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子側に接続されるN型の第3MOSトランジスタと、
一端が前記第3MOSトランジスタのソース端子側に接続され、他端が前記第1MOSトランジスタ及び前記第2MOSトランジスタのゲート端子側に接続され、供給された電流に応じて両端に電圧を生成する電圧生成部と、を有し、
前記電流制御部は、前記制御信号が前記スイッチ素子のオンを指示する場合には、前記電圧生成部の他端と前記第2電源端子との間の電流経路を開き、前記制御信号が前記スイッチ素子のオフを指示する場合には当該電流経路を閉じる、請求項12記載の選択回路。 - 前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ素子は、ドレイン端子が前記入力端子側に接続され、ゲート端子に前記駆動電圧が供給されるN型の第4MOSトランジスタと、ドレイン端子が前記出力端子側に接続され、ゲート端子が前記第4MOSトランジスタのゲート端子側に接続され、ソース端子が前記第4MOSトランジスタのソース端子と共通に接続されるN型の第5MOSトランジスタと、を有し、
前記ソースフォロア回路は、ドレイン端子が前記第2電源端子側に接続され、ゲート端子が前記第4MOSトランジスタ及び前記第5MOSトランジスタのソース端子側に接続されるP型の第6MOSトランジスタと、
一端が前記第6MOSトランジスタのソース端子側に接続され、他端が前記第4MOSトランジスタ及び前記第5MOSトランジスタのゲート端子側に接続され、供給された電流に応じて両端に電圧を生成する電圧生成部と、を有し、
前記電流制御部は、前記制御信号が前記スイッチ素子のオンを指示する場合には、前記電圧生成部の他端と前記第1電源端子との間の電流経路を開き、前記制御信号が前記スイッチ素子のオフを指示する場合には当該電流経路を閉じる、請求項13記載の選択回路。 - 前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ駆動部は、前記電流制御部によって形成される電流経路に流れる電流よりも小さい電流が流れる電流経路を、前記第1電源端子と前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して形成するオフ加速部と、を更に有する請求項14記載の選択回路。 - 前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ駆動部は、前記電流制御部が電流経路を閉じている期間に、前記第1電源端子と前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して電流経路を形成するオフ加速部と、を更に有する請求項14記載の選択回路。 - 前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ駆動部は、前記電流制御部によって形成される電流経路に流れる電流よりも小さい電流が流れる電流経路を、前記第2電源端子と前記第4MOSトランジスタ及び前記第5MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して形成するオフ加速部と、を更に有する請求項15記載の選択回路。 - 前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ駆動部は、前記電流制御部が電流経路を閉じている期間に、前記第2電源端子と前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して電流経路を形成するオフ加速部と、を更に有する請求項16記載の選択回路。 - 素電池の一端と他端が接続されて組電池を構成する複数個の素電池のうち1又は複数の素電池から構成されるブロックを1単位とし、1ブロック毎に前記ブロックの両端の電圧を測定するための電圧測定装置であって、
入力された制御信号に応じて、前記ブロックの両端に接続される信号線を1ブロック毎に選択して第1出力端子と第2出力端子に接続する選択部と、
前記第1出力端子と前記第2出力端子の電圧を入力して、両端子間の電圧を測定する測定部と、を有し、
前記選択部は、前記ブロックの一端に接続される信号線が接続される入力端子と前記第1出力端子に接続される信号線が接続される出力端子とを有し、前記制御信号に応じて前記入力端子と前記出力端子とを電気的に接続する第1スイッチ回路と、
前記ブロックの他端に接続される信号線が接続される入力端子と前記第2出力端子に接続される信号線が接続される出力端子とを有し、前記制御信号に応じて前記入力端子と前記出力端子とを電気的に接続する第2スイッチ回路と、を夫々の前記ブロックに対応して有し、
前記第1スイッチ回路及び前記第2スイッチ回路は、当該スイッチ回路の入力端子と出力端子との間に設けられたスイッチ素子と、前記制御信号に応じて前記スイッチ素子を駆動するスイッチ駆動部と、を有し、
前記スイッチ駆動部は、前記入力端子に供給される入力電圧を挟んで、相互に異なる第1電源電圧と第2電源電圧との間で駆動され、
前記第1電源電圧が供給される第1電源端子と、前記第2電源電圧が供給される第2電源端子との間に配置され、前記入力電圧に応じた電圧を入力し、出力側に生じた電圧を前記スイッチ素子を駆動するための駆動電圧として前記スイッチ素子に供給するソースフォロア回路と、
前記制御信号に応じて、前記第1電源端子と前記第2電源端子との間の前記ソースフォロア回路が配置された電流経路を開閉する電流制御部と、を有する電圧測定装置。 - 前記第1電源電圧は、前記組電池を構成する素電池のうち最高位の素電池の一端の電圧に応じた電圧である、請求項19記載の電圧測定装置。
- 前記スイッチ素子は、ゲート端子が前記駆動電圧により制御されるP型のMOSトランジスタ又はN型のMOSトランジスタを有し、
前記ブロックに対応される前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子のトランジスタの種類は同一とされる、請求項20記載の電圧測定装置。 - 前記ブロックのうち前記他端の電位が所定の電位以上となる第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子は、P型のMOSトランジスタとされ、
前記ブロックのうち前記他端の電位が前記所定の電位より低い第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路のスイッチ素子は、N型のMOSトランジスタとされる、請求項21記載の電圧測定装置。 - 前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ素子は、ドレイン端子が前記入力端子側に接続され、ゲート端子に前記駆動電圧が供給されるP型の第1MOSトランジスタと、ドレイン端子が前記出力端子側に接続され、ゲート端子が前記第1MOSトランジスタのゲート端子側に接続され、ソース端子が前記第1MOSトランジスタのソース端子と共通に接続されるP型の第2MOSトランジスタと、を有し、
前記ソースフォロア回路は、ドレイン端子が前記第1電源端子側に接続され、ゲート端子が前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子側に接続されるN型の第3MOSトランジスタと、
一端が前記第3MOSトランジスタのソース端子側に接続され、他端が前記第1MOSトランジスタ及び前記第2MOSトランジスタのゲート端子側に接続され、供給された電流に応じて両端に電圧を生成する電圧生成部と、を有し、
前記電流制御部は、前記制御信号が前記スイッチ素子のオンを指示する場合には、前記電圧生成部の他端と前記第2電源端子との間の電流経路を開き、前記制御信号が前記スイッチ素子のオフを指示する場合には当該電流経路を閉じる、請求項22記載の電圧測定装置。 - 前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ素子は、ドレイン端子が前記入力端子側に接続され、ゲート端子に前記駆動電圧が供給されるN型の第4MOSトランジスタと、ドレイン端子が前記出力端子側に接続され、ゲート端子が前記第4MOSトランジスタのゲート端子側に接続され、ソース端子が前記第4MOSトランジスタのソース端子と共通に接続されるN型の第5MOSトランジスタと、を有し、
前記ソースフォロア回路は、ドレイン端子が前記第2電源端子側に接続され、ゲート端子が前記第4MOSトランジスタ及び前記第5MOSトランジスタのソース端子側に接続されるP型の第6MOSトランジスタと、
一端が前記第6MOSトランジスタのソース端子側に接続され、他端が前記第4MOSトランジスタ及び前記第5MOSトランジスタのゲート端子側に接続され、供給された電流に応じて両端に電圧を生成する電圧生成部と、を有し、
前記電流制御部は、前記制御信号が前記スイッチ素子のオンを指示する場合には、前記電圧生成部の他端と前記第1電源端子との間の電流経路を開き、前記制御信号が前記スイッチ素子のオフを指示する場合には当該電流経路を閉じる、請求項23記載の電圧測定装置。 - 前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ駆動部は、前記電流制御部によって形成される電流経路に流れる電流よりも小さい電流が流れる電流経路を、前記第1電源端子と前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して形成するオフ加速部、を更に有する請求項24記載の電圧測定装置。 - 前記第1ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ駆動部は、前記電流制御部が電流経路を閉じている期間に、前記第1電源端子と前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して電流経路を形成するオフ加速部と、を更に有する請求項24記載の電圧測定装置。 - 前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ駆動部は、前記電流制御部によって形成される電流経路に流れる電流よりも小さい電流が流れる電流経路を、前記第2電源端子と前記第4MOSトランジスタ及び前記第5MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して形成するオフ加速部、を更に有する請求項25記載の電圧測定装置。 - 前記第2ブロックに対応する前記第1スイッチ回路及び前記第2スイッチ回路において、
前記スイッチ駆動部は、前記電流制御部が電流経路を閉じている期間に、前記第2電源端子と前記第1MOSトランジスタ及び前記第2MOSトランジスタのソース端子との間に前記電圧生成部の他端を介して電流経路を形成するオフ加速部と、を更に有する請求項26記載の電圧測定装置。 - 前記測定部は、デルタ・シグマ方式のアナログデジタル変換器を有する、請求項19記載の電圧測定装置。
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US14/112,893 A-371-Of-International US9453886B2 (en) | 2011-04-21 | 2012-04-10 | Switch circuit, selection circuit, and voltage measurement device |
US15/258,018 Continuation US20160377685A1 (en) | 2011-04-21 | 2016-09-07 | Switch circuit, selection circuit, and voltage measurement device |
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WO2012144373A1 true WO2012144373A1 (ja) | 2012-10-26 |
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US (2) | US9453886B2 (ja) |
EP (1) | EP2700958B1 (ja) |
JP (1) | JP5640147B2 (ja) |
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JP2014093635A (ja) * | 2012-11-02 | 2014-05-19 | Rohm Co Ltd | アナログスイッチ回路およびそれを備える電気機器 |
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CN104467774A (zh) * | 2013-07-24 | 2015-03-25 | 赵恩海 | 一种采用固体开关的开关网络电路 |
JP2017539158A (ja) * | 2014-11-24 | 2017-12-28 | バン アンド オルフセン アクティー ゼルスカブBang And Olufsen A/S | 固体スイッチ・リレー |
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CN111971564A (zh) * | 2018-04-26 | 2020-11-20 | 株式会社自动网络技术研究所 | 车载用的电压检测电路 |
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CN109870950B (zh) * | 2019-01-16 | 2024-06-11 | 金卡智能集团股份有限公司 | 一种基于gprs通信的控制系统 |
JP2019184586A (ja) * | 2019-03-15 | 2019-10-24 | カルソニックカンセイ株式会社 | 診断装置及び診断方法 |
Also Published As
Publication number | Publication date |
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US20160377685A1 (en) | 2016-12-29 |
EP2700958B1 (en) | 2019-01-16 |
CN103492888B (zh) | 2016-11-23 |
US20140043032A1 (en) | 2014-02-13 |
EP2700958A4 (en) | 2014-12-17 |
JPWO2012144373A1 (ja) | 2014-07-28 |
CN103492888A (zh) | 2014-01-01 |
US9453886B2 (en) | 2016-09-27 |
JP5640147B2 (ja) | 2014-12-10 |
EP2700958A1 (en) | 2014-02-26 |
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