WO2012093423A1 - Dispositif d'alimentation électrique pour système de charge sans contact - Google Patents

Dispositif d'alimentation électrique pour système de charge sans contact Download PDF

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Publication number
WO2012093423A1
WO2012093423A1 PCT/JP2011/001901 JP2011001901W WO2012093423A1 WO 2012093423 A1 WO2012093423 A1 WO 2012093423A1 JP 2011001901 W JP2011001901 W JP 2011001901W WO 2012093423 A1 WO2012093423 A1 WO 2012093423A1
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Prior art keywords
power
switching elements
power supply
output voltage
voltage
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PCT/JP2011/001901
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English (en)
Japanese (ja)
Inventor
秀樹 定方
藤田　篤志
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パナソニック株式会社
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Publication of WO2012093423A1 publication Critical patent/WO2012093423A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/007—Regulation of charging or discharging current or voltage
    • H02J7/00712—Regulation of charging or discharging current or voltage the cycle being controlled or terminated in response to electric parameters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/80—Circuit arrangements or systems for wireless supply or distribution of electric power involving the exchange of data, concerning supply or distribution of electric power, between transmitting devices and receiving devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to a power feeding device in a contactless charging system that charges a secondary battery mounted in, for example, an electric propulsion vehicle (electric vehicle or hybrid vehicle) in a contactless manner.
  • a contactless charging system that charges a secondary battery mounted in, for example, an electric propulsion vehicle (electric vehicle or hybrid vehicle) in a contactless manner.
  • each of the power feeding device and the power receiving device includes a resonance unit that resonates an AC signal, thereby reducing the restriction on the positional relationship between the power feeding device and the power receiving device (for example, see Patent Document 1).
  • the present invention has been made in view of such problems of the prior art, and not only can reduce the current / voltage ripple of the commercial frequency component in the output of the power supply apparatus, but also reduce the number of parts of the power supply apparatus. Accordingly, it is an object of the present invention to provide a power supply device for a non-contact charging system that can reduce the size or cost of the power supply device and can reduce power supply loss as much as possible.
  • the present invention provides a power supply device that supplies power to a power receiving device in a non-contact manner, a power factor improvement circuit that outputs a DC voltage by improving the power factor, and an output of the power factor improvement circuit
  • a DC voltage When a DC voltage is applied, it has an electrolytic capacitor that accumulates electric charge and a plurality of switching elements, operates using the electrolytic capacitor as a power source, generates an AC signal, and receives an AC signal from the inverter circuit Then, a resonance capacitor and an inductor that perform power supply to the power receiving device in a non-contact manner, and a power supply side control circuit that changes at least one of the energization rate and the drive frequency of the plurality of switching elements are provided.
  • the power supply apparatus can be reduced in size or cost by reducing the number of parts of the power supply apparatus, and power supply loss can be minimized. Can be reduced.
  • FIG. 1 is a circuit diagram of a contactless charging system according to an embodiment of the present invention.
  • FIG. 2 is a circuit diagram of a feeding power detection unit provided in the non-contact charging system of FIG.
  • FIG. 3 is a diagram showing waveforms of respective parts of a conventional non-contact charging system for comparison with waveforms of respective parts in the non-contact charging system of FIG.
  • FIG. 4 is a diagram illustrating waveforms of respective parts in the non-contact charging system when the energization rates of a plurality of switching elements provided in the non-contact charging system of FIG. 1 are changed.
  • FIG. 5 is a diagram showing waveforms of respective parts in the non-contact charging system when the driving frequency of a plurality of switching elements is changed.
  • FIG. 6 is a diagram showing waveforms of respective parts in the non-contact charging system when both the energization rate and the driving frequency of the plurality of switching elements are changed.
  • FIG. 7 is a diagram showing operation waveforms of the main part of the power feeding device when the input power to the inverter circuit 4 of FIG. 1 is high.
  • FIG. 8 is a diagram illustrating operation waveforms of main parts of the power feeding device when the input power to the inverter circuit 4 in FIG. 1 is low.
  • FIG. 9 is a circuit diagram of another contactless charging system according to the present invention.
  • the present invention is a power supply device that supplies power to a power receiving device in a non-contact manner.
  • the power factor improvement circuit that performs power factor improvement and outputs a DC voltage, and the output DC voltage of the power factor improvement circuit is given a charge.
  • an inverter circuit that operates using the electrolytic capacitor as a power source to generate an AC signal, and when an AC signal from the inverter circuit is input, the power receiving device is A resonance capacitor and an inductor that perform power supply by contact, and a power supply-side control circuit that changes at least one of a conduction rate and a drive frequency of the plurality of switching elements are provided.
  • the power supply device further includes a power supply power detection unit that detects a current flowing through the inductor or a voltage of the inductor, and the power supply side control circuit performs a plurality of switching operations based on the current or voltage detected by the power supply power detection unit. You may change at least one of the electricity supply rate and drive frequency of an element.
  • the power supply side control circuit receives the power command value by wireless communication with the power receiving device side, determines the basic energization rate of the plurality of switching elements so as to become the received power command value, and When the output voltage is high, the energization rate of the plurality of switching elements may be set lower than the basic energization rate, and when the output voltage is low, the energization rate of the plurality of switching elements may be set higher than the basic energization rate.
  • the power supply side control circuit receives the power command value by wireless communication with the power receiving device side, determines the basic drive frequency of the plurality of switching elements so as to become the received power command value, and detects the power supply power When the output voltage of the unit is high, the driving frequency of the plurality of switching elements can be set higher than the basic driving frequency, and when the output voltage is low, the driving frequency of the plurality of switching elements can be set lower than the basic driving frequency.
  • the power supply side control circuit has an output voltage detection unit that detects the output voltage of the power factor correction circuit, and based on the output voltage of the power factor correction circuit detected by the output voltage detection unit, the energization of a plurality of switching elements. At least one of the rate and the driving frequency may be changed.
  • the power supply side control circuit receives the power command value by wireless communication with the power receiving device side, determines the basic energization rate of the plurality of switching elements so as to become the received power command value, and outputs the power command value.
  • the energization rate of the plurality of switching elements is set lower than the basic energization rate, and when low, the energization rate of the plurality of switching elements is set higher than the basic energization rate.
  • the power supply side control circuit receives the power command value by wireless communication with the power receiving device side, determines the basic drive frequency of the plurality of switching elements so as to become the received power command value, and detects the output voltage.
  • the driving frequency of the plurality of switching elements can be set higher than the basic driving frequency
  • the driving frequency of the plurality of switching elements can be set lower than the basic driving frequency
  • FIG. 1 is a circuit diagram of the non-contact charging system in the present embodiment.
  • the contactless charging system includes, for example, a power feeding device installed in a parking space and a power receiving device mounted in, for example, an electric propulsion vehicle.
  • the non-contact charging system includes a commercial power source 1, a first rectifier circuit 2, a power factor correction circuit 3, an inverter circuit 4, a feed power detection unit 5, a first resonance capacitor 6, and a first power supply device.
  • control circuit 13 The inductor 7 and the control circuit 13 on the power feeding device side (hereinafter simply referred to as “control circuit 13”), and the configuration on the power receiving device side include a second inductor 8, a second resonance capacitor 9, a second rectifier circuit 11, A load (battery) 12, a control circuit 14 on the power receiving device side (hereinafter simply referred to as “control circuit 14”), and a received power detection unit 10 are provided.
  • the power factor improving circuit 3 is a circuit for improving the power factor of the commercial power source 1, and includes a bypass capacitor 29, a choke coil 15 serving as a first choke coil, and a first switching element 16 (in the present embodiment, a MOSFET). ), A diode 17 that is a first diode, and a smoothing capacitor (electrolytic capacitor) 18.
  • the commercial power source 1 is a 200 V commercial power source that is a low-frequency AC power source, and is connected to the input terminal of the first rectifier circuit 2 including a bridge diode and an input filter.
  • the high potential terminal (positive electrode side) output terminal of the first rectifier circuit 2 is connected to the high potential terminal of the bypass capacitor 29 and the input terminal of the choke coil 15. Further, the high potential side terminal (drain) of the switching element 16 is connected to a connection line between the output side terminal of the choke coil 15 and the anode side terminal of the diode 17.
  • a low potential side terminal of the bypass capacitor 29, a low potential side terminal (source) of the switching element 16, and a low potential side terminal of the smoothing capacitor 18 are connected to the low potential side (negative electrode side) output terminal of the first rectifier circuit 2.
  • the high potential side terminal of the smoothing capacitor 18 is connected to the cathode side terminal of the diode 17.
  • the power factor correction circuit 3 is supplied with the output voltage of the first rectifier circuit 2 as a DC power supply, and the voltage fluctuation of the input output voltage of the first rectifier circuit 2 is suppressed by the bypass capacitor 29.
  • 15 and the switching element 16 are turned on and off, and a DC voltage having a peak value larger than the peak value and boosted to an arbitrary voltage is supplied across the smoothing capacitor 18 and smoothed.
  • a MOSFET having a high switching speed is used as a typical example of the switching element 16 in order to increase the power factor improvement effect by operating the power factor improvement circuit 3 at a high frequency.
  • a diode is attached to the MOSFET in the opposite direction, it is not shown in the figure because it does not affect the basic operation of the present embodiment even without this diode.
  • the output voltage of the smoothing capacitor 18 is supplied between the input terminals of the inverter circuit 4.
  • the input terminal of the inverter circuit 4 is connected to the output terminal of the power factor correction circuit 3, that is, to both ends of the smoothing capacitor 18.
  • a series connection body of switching elements (second and third switching elements) 19 and 20 and a series connection body of switching elements (fourth and fifth switching elements) 24 and 26 are parallel. Connected to.
  • Diodes (second and third diodes) 21 and 22 are connected in antiparallel to the switching elements 19 and 20, respectively (the high potential side terminal (collector) of the switching element and the cathode side terminal of the diode are connected). ). Further, a snubber capacitor 23 is connected in parallel to the switching element 20 (which may be the switching element 19).
  • diodes (fourth and fifth diodes) 25 and 27 are connected in antiparallel to the switching elements 24 and 26 (the high potential side terminal (collector) of the switching element and the cathode side terminal of the diode are connected to each other). Connected). A snubber capacitor 28 is connected in parallel to the switching element 26 (which may be the switching element 24).
  • a series connection body of the first resonance capacitor 6, the first inductor 7, and the feeding power detection unit 5 is connected to the connection line of the switching element 19 and the switching element 20 and the connection line of the switching element 24 and the switching element 26. Is done.
  • the second inductor 8 is disposed so as to face the first inductor 7 as the electric propulsion vehicle moves, for example.
  • a second resonant capacitor 9 is connected to the high potential side of the second inductor 8, and the low potential side of the second inductor 8 and the second resonant capacitor 9 include a second rectifier circuit 11 including a smoothing filter.
  • the received power detection unit 10 is connected to the high potential side of the second rectifier circuit 11, and the load (battery) 12 is connected to the low potential side of the received power detection unit 10 and the second rectifier circuit 11. .
  • the supply power detection unit 5 in the present embodiment includes a current detection unit 30, a voltage detection unit 31, and a power calculation unit 32.
  • the current detection unit 30 and the voltage detection unit 31 may be used when the power supply power can be estimated using either the current or the voltage.
  • the feed power detection unit 5 is connected in series to the series resonance circuit of the first inductor 7 and the first resonance capacitor 6, only one of the current and voltage is correlated. The power supply can be estimated by detection.
  • the received power detection unit 10 may have the same configuration as the power supply power detection unit 5.
  • the control circuit 13 receives a power command value from the control circuit 14 by wireless communication.
  • the control circuit 13 compares the supplied power detected by the supplied power detection unit 5 with the received power command value, and the switching elements 19 and 20 and the switching elements 24 and 26 of the inverter circuit 4 are obtained so that the power command value is obtained.
  • the switching element 16 of the power factor correction circuit 3 is driven.
  • a dedicated control IC may be used for controlling the switching element 16 of the power factor correction circuit 3.
  • the control circuit 14 determines a power command value according to the remaining voltage of the battery 12 detected by the received power detection unit 10 and transmits it to the control circuit 13 by wireless communication. Further, the received power is detected by the received power detection unit 10 during operation of the power supply apparatus, and the control circuit 14 changes the power command value to the control circuit 13 so that the load (battery) 12 is not overcurrent or overvoltage.
  • a battery for an electric propulsion vehicle is used as the load 12 of the first embodiment.
  • Battery charging is performed by supplying a voltage equal to or higher than the remaining voltage of the battery, but when the power supply voltage exceeds the remaining battery voltage, a charging current suddenly flows. This means that the load impedance as viewed from the power supply device varies greatly depending on the remaining battery voltage and the power supply voltage.
  • FIG. 3A is a schematic diagram showing an AC voltage waveform of the commercial power source 1
  • FIG. 3B is a schematic diagram showing an output voltage waveform of the DC power source, that is, an output voltage waveform of the first rectifier circuit 2. It is. This voltage is input to the power factor correction circuit 3, boosted, and then output to the smoothing capacitor 18.
  • FIG. 3C is a schematic diagram showing a waveform applied to the smoothing capacitor 18, that is, an output voltage waveform of the power factor correction circuit 3 and an input voltage waveform of the inverter circuit 4.
  • FIG. 3D is a schematic diagram showing a high-frequency current waveform generated in the first inductor 7
  • FIG. 3E is a schematic diagram showing a power waveform fed from the power feeding device to the power receiving device.
  • 3F is a schematic diagram illustrating an output current waveform of the second rectifier circuit 11, that is, an input current waveform of the load 2.
  • 3 (g) and 3 (h) are schematic diagrams showing an energization rate (duty ratio) and an operating frequency, respectively.
  • FIG. 4 shows voltage waveforms, current waveforms, etc. of each part of the non-contact charging system according to the present invention.
  • FIGS. 4 (a) to 4 (h) are respectively shown in FIGS. 3 (a) to 3 (h). It corresponds.
  • the commercial power source 1 shown in FIG. 4A is full-wave rectified by the first rectifier circuit 2 to form a DC power source as shown in the voltage waveform of FIG.
  • This DC power supply is supplied between the input terminals of the power factor correction circuit 3.
  • the diode 17 included in the power factor correction circuit 3 and the bridge diode of the first rectifier circuit 2 are turned on when the instantaneous value of the DC power supply voltage is smaller than the voltage of the smoothing capacitor 18. If not, the input current waveform is distorted and the power factor is significantly reduced. At that time, the control circuit 13 improves the power factor by turning the switching element 16 on and off.
  • the power factor correction circuit 3 has not only a power factor correction function but also a boosting function at the same time. For this reason, as shown in FIG.
  • the voltage of the smoothing capacitor 18 is the peak value of the input voltage of the power factor correction circuit 3 whose peak value is the peak value of the commercial power source 1, that is, the peak value of the DC power source. The voltage becomes higher and is supplied to the inverter circuit 4 through the smoothing capacitor 18.
  • FIGS. 3 (a) to 3 (c) and FIGS. 4 (a) to 4 (c) the commercial power supply in the power transmission system described in Patent Document 1 and the non-contact charging system according to the present invention. There is no significant difference between the AC voltage waveform of 1, the output voltage waveform of the first rectifier circuit 2, and the output voltage waveform of the power factor correction circuit 3.
  • the smoothed DC voltage output to both ends of the smoothing capacitor 18 connected between the output ends of the power factor correction circuit 3 shown in FIG. 4C is supplied to the inverter circuit 4.
  • the inverter circuit 4 is shown in FIG. 4D by the first resonant capacitor 6 and the first inductor 7 depending on whether the switching elements 19 and 20 are turned on / off and the switching elements 24 and 26 are turned on / off. Thus, a high-frequency current having a predetermined frequency is generated.
  • the on / off control of the switching elements 19 and 20 and the on / off control of the switching elements 24 and 26 are performed by the control circuit 13 applying an on signal to the gates of the switching elements 19, 20, 24 and 26. .
  • FIG. 7 and 8 show enlarged operation waveforms of the inverter circuit 4 at high input power and low input power, respectively.
  • (A), (c), and (d) are the switching elements 19 and 26 and the diode 21, respectively. , 27, the voltage of the switching elements 19, 26, and the gate voltage of the switching elements 19, 26, respectively, (b) and (e) flow in the switching elements 20, 24 and the diodes 22, 25. The current and the gate voltage of the switching elements 20 and 24 are shown.
  • (f) shows the current flowing through the first inductor 7, and the current flowing through the switching elements 19 and 26 and the diodes 21 and 27 flows during the Ton period in the figure, and the remainder of one cycle (in the figure) During the period of (T ⁇ Td ⁇ Ton), the current flowing through the switching elements 20 and 24 and the diodes 22 and 25 flows. During the dead time Td described later, the resonance current of the first inductor 7, the first resonance capacitor 6, and the snubber capacitors 23 and 28 flows.
  • the two switching elements 19 and 20 connected in series are exclusively energized, and the two switching elements 24 and 24 connected in series to the two switching elements 19 and 20 are connected in parallel. 26 is energized exclusively by shifting the drive signal phase of the switching elements 19 and 20.
  • the switching element 19 and the switching element 26 are repeatedly turned on and off in synchronization.
  • the switching element 20 and the switching element 24 are turned off, and the switching element 19 and the switching element 26 are turned on.
  • the switching element 20 and the switching element 24 are turned on, the switching element 20 and the switching element 24 are repeatedly turned on and off in synchronization.
  • the ON period of the switching elements 19 and 24 and the switching element 20 are set so that the switching element 19 and the switching element 20 are not turned on simultaneously, and so that the switching element 24 and the switching element 26 are not turned on simultaneously.
  • the dead time Td is set so as not to overlap.
  • the switching elements 19 and 26 are turned off from the on state, the snubber capacitor 23 is discharged with a gentle inclination due to resonance of the first inductor 7, the first resonance capacitor 6, and the snubber capacitor 23.
  • the switching elements 19, 26 realize a zero volt switching (ZVS) turn-off operation.
  • ZVS zero volt switching
  • the snubber capacitor 28 is discharged with a gentle slope due to resonance of the first inductor 7, the first resonant capacitor 6, and the snubber capacitor 28.
  • the elements 20 and 24 realize a ZVS turn-off operation.
  • the snubber capacitor 23 is charged and the snubber capacitor 28 is completely discharged, the diodes 21 and 27 are turned on, and an on signal is sent to the gates of the switching elements 19 and 26 during the period in which the diodes 21 and 27 are on.
  • the switching elements 19 and 26 and the switching elements 20 and 24 are alternately turned on / off by providing a dead time Td (for example, about 2 ⁇ s) so as not to short-circuit the smoothing capacitor 18.
  • Td for example, about 2 ⁇ s
  • the drive (operation) frequency of the switching elements 19, 20, 24, and 26 is made constant, and as shown in FIG. 4 (g), the energization rate (duty ratio).
  • the high frequency power is controlled by controlling.
  • the “energization rate” here means the switching element 19 with respect to the time required for one cycle of ON / OFF of the switching elements 19 and 26 (or the switching elements 20 and 24), as shown in FIGS. , 26 (or switching elements 20, 24).
  • the inverter circuit 4 has a voltage ripple of 120 Hz as shown in FIG.
  • a current ripple is generated in the current of the first inductor 7. Therefore, the feed power fluctuates as shown in FIG. 3E, and a 120-Hz current ripple occurs in the input current of the load 12 as shown in FIG.
  • the inverter circuit 4 when the input voltage including the voltage ripple shown in FIG. 4C is applied to the inverter circuit 4, the current (or the first current) of the first inductor 7 detected by the feed power detector 5.
  • the energization rates (duty ratios) of the switching elements 19, 20, 24, and 26 are controlled so that the magnetic field generated by the inductor 7 becomes substantially constant.
  • the electric current which flows through the 1st inductor 7, and the electric power feeding electric power by the side of an electric power feeder become substantially constant, as FIG.4 (d) and (e) show.
  • the control circuit 13 compares the power supply power detected by the power supply power detection unit 5 with the received power command value to obtain a power command value.
  • the switching elements 19 and 20 of the inverter circuit 4 the switching elements 24 and 26, and the switching element 16 of the power factor correction circuit 3 are driven.
  • the energization rate is set so that the power supply power increases when the energization rates of the switching elements 19 and 20 and the switching elements 24 and 26 are increased.
  • the basic energization rate is determined so that the power command value is obtained.
  • the control circuit 13 lowers the energization rate below the basic energization rate when the output voltage of the power factor correction circuit 3 is high, and sets the energization rate at the low voltage. Control is performed so that it is set higher than the rate (see FIG. 4G). As a result, the current flowing through the first inductor 7 and the feed power can be made substantially constant.
  • the basic energization rate is selected so that the supply power matches the power command value when the energization rate control is performed so that the supply power is substantially constant.
  • the basic energization rate is 50% and the output is maximum, and the basic energization rate is variable in the range of 0 to 50%. Therefore, when the feed power that becomes the power command value cannot be obtained by the energization rate control, the control circuit 13 changes the drive frequency. When the feed power is low, the drive frequency is set lower, and the control circuit 13 resets the basic energization rate. On the contrary, when the feed power is high, the drive frequency is set higher and the basic energization rate is also reset.
  • the energization rate is set to be higher at high input power than at low input power (for example, 50%, 40%, etc.
  • the control circuit 13 controls the switching elements 19, 20, 24, and 26, so that the current flowing through the first inductor 7 and the feeding power are made substantially constant. can do.
  • the control circuit 14 determines command values such as charging current, voltage, and power according to the remaining voltage of the battery detected by the received power detection unit 10 at the start of charging, and transmits the command value to the control circuit 13 by wireless communication. Even during charging, information such as charging current, voltage, and power is transmitted to the control circuit 13 by wireless communication, and the control circuit 13 performs control based on the received information such as charging current, voltage, and power.
  • the power transmission efficiency between the first inductor 7 and the second inductor 8 can be increased by causing the second inductor 8 and the second resonant capacitor 9 to resonate. This is because, when the impedance component due to the leakage inductance that cannot be magnetically coupled to the first inductor 7 among the second inductors 8 is canceled by the second resonance capacitor 9, the impedance on the secondary side is lowered and it becomes easy to transmit power. Can also explain. Even if the second resonant capacitor 9 is not provided, the present invention is not affected.
  • control circuit 13 drives and controls the power factor correction circuit 3 and the inverter circuit 4 so that the power command value and the detection result of the feed power detection unit 5 are matched by the above-described operation.
  • the switching elements 19, 20, 24, and 26 are controlled based on the current value detected by the power supply power detection unit 5, but the power supply voltage detection unit 5 detects the power supply voltage. By controlling the switching elements 19, 20, 24, and 26 so that the detected voltage value becomes substantially constant, the voltage applied to the first inductor 7 and the feeding power can be made substantially constant.
  • the driving frequency of the switching elements 19, 20, 24, and 26 is made constant, and the energization rate is controlled to control the high frequency power, but in the present embodiment, FIG. As shown in FIG. 4, the high-frequency power is controlled by controlling the drive frequency of the switching elements 19, 20, 24, and 26 while keeping the energization rate constant.
  • the driving frequency is set so that the feeding power increases when the driving frequency is lowered (the operation is performed at a frequency higher than the frequency at which the feeding power becomes maximum), and is detected by the feeding power detection unit 5.
  • the control circuit 13 is set so that the drive frequency is set high when the output voltage of the power factor correction circuit 3 is high and the drive frequency is set low when the output voltage is low (see FIG. 5H).
  • the control circuit 13 compares the power supply power detected by the power supply power detection unit 5 with the received power command value to obtain a power command value.
  • the switching elements 19 and 20 of the inverter circuit 4 the switching elements 24 and 26, and the switching element 16 of the power factor correction circuit 3 are driven.
  • the driving frequency is set so that the feeding power increases when the driving frequency of the switching elements 19 and 20 and the switching elements 24 and 26 is lowered (maximum feeding power).
  • the control circuit 13 determines the basic drive frequency so that the power command value is obtained.
  • the control circuit 13 sets the drive frequency higher than the basic frequency when the output voltage of the power factor correction circuit 3 is high, and sets the drive frequency higher than the basic frequency when the output voltage is low. Control is performed so that it is set low (see FIG. 5H). As a result, the current flowing through the first inductor 7 and the feed power can be made substantially constant.
  • the basic drive frequency is selected so that the feed power matches the power command value when such drive frequency control is performed to make the feed power substantially constant.
  • the energization rate is basically 50%. However, when the energization rate is set higher, the power supply becomes larger, while when the energization rate is set lower, the power supply is reduced. Yes. By changing this energization rate, the supplied power and the power command value can be made more consistent.
  • the current ripple in the load is generated when the output voltage of the power factor correction circuit 3, that is, the voltage of the electrolytic capacitor, changes as shown in FIG. Since the magnitude of this voltage increases as the feed power increases, in a charging system in which the power command value sent by wireless communication from the control circuit 14 varies as in this embodiment, the current ripple in the load Will also change depending on the power command value. For example, when the power command value increases, the voltage change width of the electrolytic capacitor increases and the load current ripple also increases.
  • the total power command value is The load current ripple is improved and the operation is performed so that the power supply becomes substantially constant.
  • the drive frequency is high when the output voltage of the power factor correction circuit 3 is high.
  • the control circuit 13 controls the drive frequency of the switching elements 19, 20, 24, and 26 so that the drive frequency is low when the voltage is low, the voltage ripple is reduced and the power supply voltage can be made substantially constant.
  • the high frequency power is controlled by controlling both the energization rate and the drive frequency of the switching elements 19, 20, 24, and 26.
  • control circuit 13 controls the switching elements 19, 20, 24, and 26 so as to reduce the current ripple, thereby reducing the current ripple and making the current flowing through the first inductor 7 substantially constant.
  • FIG. 9 is a circuit diagram of the non-contact charging system in the present embodiment. 9 is that the control circuit 13 is provided with an output voltage detector 33 that detects the output voltage of the smoothing capacitor 18 of the power factor correction circuit 3 (input voltage of the inverter circuit 4). It is different from the circuit diagram.
  • control circuit 13 controls the switching elements 19, 20, 24, and 26 based on the output voltage of the smoothing capacitor 18 detected by the output voltage detector 33 (energization rate control and / or / (Or frequency control), the feeding current or feeding voltage is controlled to a desired value.
  • the switching elements 19, 20, 24, and 26 are controlled as follows, as in the above-described first to third embodiments.
  • (I) Energization rate control (drive frequency is constant) In this control, the control circuit 13 switches the switching elements 19, 20, 24, and 26 so that the energization rate is small when the output voltage of the smoothing capacitor 18 detected by the output voltage detection unit 33 is high and the energization rate is large when the output voltage is low. By controlling the above, the current or voltage of the first inductor 7 and the feeding power are made substantially constant.
  • Energization rate control and drive frequency control In this control, the energization rate is small and the drive frequency is high when the output voltage of the smoothing capacitor 18 detected by the output voltage detector 33 is high, and the energization rate is large when the output voltage is low.
  • the control circuit 13 controls the switching elements 19, 20, 24, and 26 so that the drive frequency is lowered, so that the current or voltage of the first inductor 7 and the feeding power are made substantially constant.
  • the power feeding device of the non-contact charging system can not only reduce the current / voltage ripple of the power feeding device, but also reduce the number of parts of the power feeding device to reduce the size or cost of the power feeding device. Since the power loss can be reduced as much as possible, it is useful for power feeding to a power receiving device of an electric propulsion vehicle, for example.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne un dispositif d'alimentation électrique sans contact qui comprend : un circuit d'amélioration du facteur de puissance (3) qui produit une amélioration de facteur de puissance et génère une tension de C.C. ; un condensateur électrolytique (18) connecté à la borne de sortie du circuit d'amélioration de facteur de puissance (3) ; un circuit d'inverseur (4) qui possède une pluralité d'éléments de commutation (19, 20, 24, 26) et qui génère un signal de C.A. en utilisant la tension du condensateur électrolytique (18) comme source d'alimentation ; un premier condensateur à résonance (6) et un premier inducteur (7) connectés à la borne de sortie du circuit d'inverseur (4) ; et un circuit de commande de dispositif d'alimentation électrique (13). Par ailleurs, quand l'électricité est fournie à un dispositif récepteur de puissance, le premier inducteur (7) est configuré pour être opposé à un deuxième inducteur (8) du dispositif récepteur de puissance, et le circuit de commande du dispositif d'alimentation électrique (13) change le temps de passage de courant et/ou la fréquence d'attaque de la pluralité d'éléments de commutation (19, 20, 24, 26) en fonction de la sortie du circuit d'inverseur (4).
PCT/JP2011/001901 2011-01-06 2011-03-30 Dispositif d'alimentation électrique pour système de charge sans contact WO2012093423A1 (fr)

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JP2011001396 2011-01-06

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2014148144A1 (fr) * 2013-03-18 2014-09-25 株式会社Ihi Appareil d'alimentation électrique et système d'alimentation électrique sans contact
CN104981961A (zh) * 2013-02-20 2015-10-14 松下知识产权经营株式会社 非接触充电装置以及非接触充电方法
WO2016006066A1 (fr) * 2014-07-09 2016-01-14 日産自動車株式会社 Dispositif d'alimentation électrique sans contact
EP3352329A4 (fr) * 2015-09-17 2019-05-08 IHI Corporation Dispositif de transmission d'énergie et système d'alimentation électrique sans contact

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JPH11252810A (ja) * 1998-03-03 1999-09-17 Toyota Autom Loom Works Ltd バッテリ車の車載側充電装置
JP2009254031A (ja) * 2008-04-02 2009-10-29 Hitachi Plant Technologies Ltd 非接触給電装置
JP2010233354A (ja) * 2009-03-27 2010-10-14 Nissan Motor Co Ltd 給電装置
JP2010272412A (ja) * 2009-05-22 2010-12-02 Toyota Motor Corp ケーブル収納装置およびそれを備える車両

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JPH06178550A (ja) * 1992-12-02 1994-06-24 Fuji Electric Co Ltd Ｖｖｖｆインバータの電流制御装置
JPH11252810A (ja) * 1998-03-03 1999-09-17 Toyota Autom Loom Works Ltd バッテリ車の車載側充電装置
JP2009254031A (ja) * 2008-04-02 2009-10-29 Hitachi Plant Technologies Ltd 非接触給電装置
JP2010233354A (ja) * 2009-03-27 2010-10-14 Nissan Motor Co Ltd 給電装置
JP2010272412A (ja) * 2009-05-22 2010-12-02 Toyota Motor Corp ケーブル収納装置およびそれを備える車両

Cited By (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US9831712B2 (en) 2013-02-20 2017-11-28 Panasonic Intellectual Property Management Co., Ltd. Non-contact charging device and non-contact charging method
EP2961024A4 (fr) * 2013-02-20 2016-01-27 Panasonic Ip Man Co Ltd Dispositif de charge sans contact et procédé de charge sans contact
CN104981961A (zh) * 2013-02-20 2015-10-14 松下知识产权经营株式会社 非接触充电装置以及非接触充电方法
EP2961024A1 (fr) * 2013-02-20 2015-12-30 Panasonic Intellectual Property Management Co., Ltd. Dispositif de charge sans contact et procédé de charge sans contact
JPWO2014148144A1 (ja) * 2013-03-18 2017-02-16 株式会社Ihi 給電装置及び非接触給電システム
CN105052008A (zh) * 2013-03-18 2015-11-11 株式会社Ihi 供电装置以及非接触供电系统
JP5888468B2 (ja) * 2013-03-18 2016-03-22 株式会社Ihi 給電装置及び非接触給電システム
CN105052008B (zh) * 2013-03-18 2018-08-24 株式会社Ihi 供电装置以及非接触供电系统
WO2014148144A1 (fr) * 2013-03-18 2014-09-25 株式会社Ihi Appareil d'alimentation électrique et système d'alimentation électrique sans contact
EP2985868A4 (fr) * 2013-03-18 2017-01-11 IHI Corporation Appareil d'alimentation électrique et système d'alimentation électrique sans contact
US10298063B2 (en) 2013-03-18 2019-05-21 Ihi Corporation Power-supplying device and wireless power supply system
WO2016006066A1 (fr) * 2014-07-09 2016-01-14 日産自動車株式会社 Dispositif d'alimentation électrique sans contact
EP3352329A4 (fr) * 2015-09-17 2019-05-08 IHI Corporation Dispositif de transmission d'énergie et système d'alimentation électrique sans contact
US10498220B2 (en) 2015-09-17 2019-12-03 Ihi Corporation Power transmitter and wireless power transfer system

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