WO2008032362A1 - Convertisseur cc-cc - Google Patents

Convertisseur cc-cc Download PDF

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Publication number
WO2008032362A1
WO2008032362A1 PCT/JP2006/318029 JP2006318029W WO2008032362A1 WO 2008032362 A1 WO2008032362 A1 WO 2008032362A1 JP 2006318029 W JP2006318029 W JP 2006318029W WO 2008032362 A1 WO2008032362 A1 WO 2008032362A1
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WO
WIPO (PCT)
Prior art keywords
semiconductor switching
voltage side
terminal
capacitor
switching element
Prior art date
Application number
PCT/JP2006/318029
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English (en)
Japanese (ja)
Inventor
Takahiro Urakabe
Tatsuya Okuda
Original Assignee
Mitsubishi Electric Corporation
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Mitsubishi Electric Corporation filed Critical Mitsubishi Electric Corporation
Priority to PCT/JP2006/318029 priority Critical patent/WO2008032362A1/fr
Publication of WO2008032362A1 publication Critical patent/WO2008032362A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/4837—Flying capacitor converters

Definitions

  • the present invention relates to a DCZDC converter device that converts a DC voltage into a DC voltage that is stepped up or stepped down.
  • a conventional DCZDC converter device includes m (m is an integer of 2 or more) number of parallel connected switched capacitor transformers, and each transformer includes a capacitor and a plurality of switching transistors. Composed.
  • Each switched capacitor transformer has a switching signal that alternately switches between charging and discharging of the capacitor, and a clock signal whose phase is shifted by 2 ⁇ / (rad) according to a predetermined input voltage. It is configured to be driven by a signal to be in a state (see, for example, Patent Document 1).
  • Patent Document 1 Japanese Utility Model Publication No. 1 147685
  • the present invention has been made to solve the above-described problems, and an object thereof is to obtain a DCZDC converter device capable of increasing the amount of power to be transferred with a small and simple circuit configuration. It is said.
  • a DCZDC converter device includes a low voltage side DC power supply and a high voltage side DC power supply.
  • a capacitor and a plurality of semiconductor switching elements are provided between the power source and the capacitor, and charging and discharging of the capacitor are alternately switched by the switching operation of the semiconductor switching element.
  • an inductor is inserted in a path section where the charging path and discharging path of the capacitor overlap, and the capacitor and the inductor are connected in series when the capacitor is charged and discharged.
  • FIG. 1 is a diagram showing a main circuit configuration of a converter device according to a first embodiment of the present invention.
  • FIG. 2 is a diagram for explaining the operation of the converter device according to the first embodiment of the present invention.
  • FIG. 3 is a diagram illustrating the effect of the converter device according to the first embodiment of the present invention using a comparative example.
  • FIG. 4 is a diagram showing a main circuit configuration of a converter device according to another example of the first embodiment of the present invention.
  • FIG. 5 is a diagram for explaining the operation of the converter device according to the second embodiment of the present invention.
  • FIG. 6 shows a main circuit configuration of a converter device according to a third embodiment of the present invention.
  • FIG. 7 is a diagram showing a main circuit configuration of a converter device according to another example of the third embodiment of the present invention.
  • FIG. 8 shows a main circuit configuration of a converter device according to a fourth embodiment of the present invention.
  • FIG. 9 is a diagram showing a main circuit configuration of a converter device according to another example of the fourth embodiment of the present invention.
  • FIG. 10 is a diagram showing a main circuit configuration of a converter device according to a fifth embodiment of the present invention.
  • FIG. 11 is a diagram showing a main circuit configuration of a converter device according to a sixth embodiment of the present invention.
  • FIG. 12 is a diagram showing a main circuit configuration of a converter device according to another example of the sixth embodiment of the present invention.
  • FIG. 13 is a diagram for explaining the operation of the converter according to the sixth embodiment of the present invention.
  • Swla, Sw2a Switches as first and second semiconductor switching elements
  • Sw3a, Sw4a Switches as first and second semiconductor switching elements
  • SwlOO, Sw201 to Sw203, Sw301 to Sw303, Sw401 to Sw403 Switch as a semiconductor switching element
  • a DCZDC converter device (hereinafter referred to as a converter device) according to Embodiment 1 of the present invention will be described with reference to the drawings.
  • FIG. 1 is a diagram showing a main circuit configuration of a converter device according to Embodiment 1 of the present invention.
  • Converter block 1 includes four MOSFETs (hereinafter referred to as switches) Swl to Sw4, capacitors Ce, and inductors Lr as semiconductor switching elements.
  • switches MOSFETs (hereinafter referred to as switches) Swl to Sw4, capacitors Ce, and inductors Lr as semiconductor switching elements.
  • the drain terminal of the switch Swl as the first semiconductor switching element is connected to the positive terminal 3 of the high voltage side DC power supply.
  • the drain terminal is connected to the source terminal of the switch Swl, and the source terminal is connected to the positive terminal 2 of the low-voltage side DC power supply.
  • the source terminal of the switch Sw3 as the third semiconductor switching element is connected to the negative terminal 3a of the high voltage side DC power source and the negative terminal 2a of the low voltage side DC power source.
  • the source terminal is connected to the drain terminal of the switch Sw3, and the drain terminal is connected to the positive terminal 2 of the low-voltage DC power supply.
  • the capacitor Ce and the inductor Lr are connected in series, and are connected between the connection point of the switches Swl and Sw2 and the connection point of the switches Sw3 and Sw4.
  • Each switch Swl to Sw4 includes a gate drive signal generated by a control circuit unit (not shown).
  • a gate signal (Hereinafter referred to as a gate signal) is input, and an on-off operation is performed according to the voltage level of the gate signal.
  • the voltage between terminals 2 and 2a of the low-voltage DC power supply is VL
  • the voltage between terminals 3 and 3a of the high-voltage DC power supply is VH.
  • the smoothing capacitor CL and the capacitor Ce are connected in series, and the series body is connected in parallel with the smoothing capacitor CH. Since the smoothing capacitor and the capacitor Ce have a voltage VL, the voltage of the series body is 2VL. Since the terminal voltage VH on the high voltage side is smaller than 2VL, the energy shifts from the low voltage side to the high voltage side.
  • VHZVL operates in such a way that power is transferred bidirectionally in the relationship of approximately two.
  • switches Sw2 and Sw3 are simultaneously switched on and switches Swl and Sw4 are switched on alternately.
  • the gate signals of switches Sw2 and Sw3 and the gate signals of switches Swl and Sw4 have the same shape.
  • the switching of the switching operation switches between charging and discharging of the capacitor Ce to perform power transfer.However, since the inductor Lr is inserted in the section where the current path during charging and the current path during discharging overlap, Both current paths during discharge The 1S inductor Lr, capacitor Ce, and the resistance of the current flow path are connected in series. For this reason, the switching frequencies of the gate signals of the switches Sw2 and Sw3 and the gate signals of the switches Swl and Sw4 are made to coincide with the resonance frequency at which the inductor Lr and the capacitor Ce are in a series resonance state.
  • the capacitance value of the capacitor Ce is Ce
  • the inductance value of the inductor Lr is Lr
  • the resistance of the path through which the current flows that is, the on-resistance of the switch Sw2, Sw3 or the switch Swl, Sw4, the capacitor Ce
  • the resistance of the inductor Lr If the sum of the components is R, the period T of the gate signal can be expressed by the following equation (1).
  • FIG. Fig. 2 (a) shows the case of 2VL> VH
  • Fig. 2 (b) shows the case of 2VL> VH.
  • the current that flows from the positive terminal 2 of the low-voltage side DC power supply to the converter block 1 is IL
  • the current that flows from the converter block 1 to the positive terminal 3 of the high-voltage side DC power supply is IH
  • the current that flows to the capacitor Ce is Ice
  • the capacitor The Ce voltage is Vce.
  • the direction of the current and voltage arrows shown in Fig. 2 is positive.
  • the switches Sw2, Sw3 and the switches Swl, Sw4 are switched on and off at the timing when the current Ice flowing in the capacitor Ce becomes zero, and the current Ic e flowing in the capacitor Ce is as shown in FIG. It becomes a continuous sinusoidal current.
  • the current IL is a current waveform in which the current Ice is converted to an absolute value in either a positive or negative direction
  • the current IH is a current waveform obtained by taking out only the ON periods of the switches IL and SW4 of the current IL.
  • the voltage Vce of the capacitor Ce is a voltage that oscillates in a sinusoidal shape centered on the voltage VL.
  • the voltage shows a maximum value and a minimum value at the switching timing of each gate signal.
  • the voltage Vce of the capacitor Ce changes from VL + ⁇ to VL ⁇ at the time of energy transfer. If the resonance phenomenon is not used, only the amount of charge of (2VL -VH) is transferred! On the other hand, in this embodiment, the energy transfer is larger than (2V L-VH). It becomes possible.
  • the current Ice flowing through the capacitor Ce can be made into a continuous sinusoidal current, and is used per switching.
  • the amount of energy stored in the capacitor Ce can be increased. Therefore, it is possible to increase the amount of power transferred with a small and simple circuit configuration without increasing the capacitor capacity or increasing the switching frequency.
  • Fig. 3 (a) shows the relationship between the capacitance value Ce of the capacitor Ce and the amount of energy transferred per switching from the low voltage side to the high voltage side.
  • the driving frequency (gate signal frequency) of the embodiment (with inductor Lr) that uses the series resonance phenomenon of the inductor Lr and the capacitor Ce on the premise of switching when the current Ice flowing through the capacitor Ce becomes zero is Based on equation (1), the following force vj is used.
  • the embodiment according to the present invention transfers a large amount of power with a small capacitor capacity as compared with the comparative example (without inductor Lr).
  • the inductor Lr is connected in series with the capacitor Ce and connected between the connection point of the switches Swl and Sw2 and the connection point of the switches Sw3 and Sw4. As shown, only the capacitor Ce is connected between the connection point of the switches Swl and Sw2 and the connection point of the switches Sw3 and Sw4, and the inductor Lr is connected to the low-voltage side positive terminal 2 and the switches Swl and Sw2. It may be inserted between points. In this case as well, since the inductor Lr is inserted in the section where the current path during charging and the current path during discharging overlap, the series resonance phenomenon of the inductor Lr and the capacitor Ce is used as in the above embodiment. And the same effect can be obtained.
  • the inductor Lr when the inductor Lr is manufactured using a small magnetic material for miniaturization and allowing some magnetic saturation, the inductor Lr depends on the flowing current level (transition power level).
  • the inductance value changes.
  • Figure 5 (a) shows the relationship between the amount of power transferred depending on the amount of current flowing through inductor Lr, and the inductance and current values of inductor Lr. As shown in the figure, the inductance value decreases as the electric energy (current amount) increases.
  • the drive frequency is made variable, and the drive frequency is set to substantially match the resonance frequency that changes in accordance with the change in the inductance value.
  • the transition power region is divided into four, and the drive frequency is varied for each region.
  • 11 is the resonance frequency that varies with the amount of power transferred
  • 12 is the resonance frequency.
  • This is the drive frequency (set frequency) that is switched and set accordingly.
  • a storage unit (not shown) is provided, and four types of clock signals having different frequencies are stored in the storage unit in advance, a DC current value on the low voltage side is detected, and a storage unit is detected according to the current value. Calls the clock signal and uses it to generate the gate signal for each switch Swl to Sw4.
  • the drive frequency is variable, and the drive frequency is set so as to substantially match the resonance frequency even when the resonance frequency changes. Therefore, a small magnetic body allows some magnetic saturation. Inductor Lr can be used, and the circuit configuration can be made inexpensive and small.
  • the SC converter block 1 connected between the low voltage side (VL side) DC power source and the high voltage side (VH side) DC power source is connected to four switches Swl to Sw4 and capacitors.
  • Force composed of Ce and inductor Lr In this third embodiment, converter block 1 is connected to diodes Dil, Di2 as first and second diodes, and switches (MOSFETs) as first and second semiconductor switching elements. Consists of Sw3a, Sw4a, capacitor Ce and inductor.
  • FIG. 6 is a diagram showing a main circuit configuration of the converter device according to the third embodiment of the present invention.
  • switches Sw3a and Sw4a are used instead of the switches Sw3 and Sw4 shown in the first embodiment.
  • the force sword terminal is connected to the high-voltage side positive terminal 3 and the force sword terminal is connected to the anode terminal of the diode Dil.
  • a diode Di2 whose anode terminal is connected to the switch Sw4a is used. Only the capacitor Ce is connected between the connection point of the diodes Dil and Di2 and the connection point of the switches Sw3a and Sw4a.
  • the connection point of the diode Di2 and switch Sw4a is connected to the low-voltage side positive terminal 2 via the inductor Lr. Connect to.
  • FIG. 7 shows the case where the same position as in the first embodiment is acceptable.
  • the switching frequency of the gate signal of switch Sw3a and the gate signal of switch Sw4a By switching the switch Sw3a and switch Sw4a alternately, the power is transferred from the low voltage side to the high voltage side when 2VL> VH. .
  • the energy transfer from the low voltage side to the high voltage side is performed, and the same current and voltage waveforms shown in FIG. 2A of the first embodiment are obtained.
  • the diode Dil is turned on by the electromotive voltage of the inductor Lr and the voltage of the capacitor Ce while the switch Sw4a is turned on and a current flows toward the high-voltage side positive terminal 3.
  • the diode Di2 is switched by the switch Sw3a and the current flows from the low-voltage side positive terminal 2! /, While the voltage from the inductor Lr and the voltage difference between the low-voltage side positive terminal 2 and the capacitor Ce voltage Turns on. Both diodes Dil and Di2 are automatically turned off when the current direction is reversed.
  • the SC converter block 1 connected between the low voltage side (VL side) DC power source and the high voltage side (VH side) DC power source is connected to four switches Swl to Sw4 and capacitors. Force composed of Ce and inductor Lr In this Embodiment 4, the converter block 1 is connected to the switches (MOSFETs) Swla, Sw2a as the first and second semiconductor switching elements, and the diode Di3 as the first and second diodes. , Di4, capacitor Ce and inductor.
  • FIG. 8 shows a main circuit configuration of the converter device according to the fourth embodiment of the present invention.
  • switches Swla and Sw2a are used instead of the switches Swl and Sw2 shown in the first embodiment.
  • switches Sw3 and Sw4 shown in the first embodiment above instead of the switches Sw3 and Sw4 shown in the first embodiment above, in addition, a diode Di3 whose anode terminal is connected to the ground terminals 2a and 3a and a diode Di4 whose anode terminal is connected to the force sword terminal of the diode Di3 and whose force sword terminal is connected to the switch Sw2a are used.
  • capacitor Ce is connected between the connection point of the diodes Di3 and Di4 and the connection point of the switches Swla and Sw2a, and the connection point of the diode Di4 and switch Sw2a is connected to the low-voltage side positive terminal 2 via the inductor Lr. Connecting.
  • the position of the inductor Lr only needs to be connected in series with the capacitor Ce when the capacitor Ce is charged / discharged.
  • the diode Di3 is turned on by the electromotive voltage of the inductor Lr and the voltage of the capacitor Ce while the switch Sw2a is turned on and the current flows from the capacitor Ce to the low-voltage side positive electrode terminal 2.
  • the diode Di4 is connected to the voltage generated by the inductor Lr and the capacitor Ce voltage superimposed on the low-voltage side positive terminal 2 while the switch Swla is turned on and current flows from the high-voltage side positive terminal 3 to the low-voltage side. Turns on by voltage difference with voltage side terminal 3. Both diodes are automatically turned off when the current direction is reversed.
  • Embodiment 5 In Embodiments 1 to 4 above, a force in which one SC converter block 1 is connected between the low voltage side (VL side) DC power source and the high voltage side (VH side) DC power source. Connect multiple SC converter blocks like this in parallel.
  • FIG. 10 is a diagram showing a main circuit configuration of the converter device according to the fourth embodiment of the present invention.
  • SC cells la ⁇ : Ld having the same SC-type converter block force as the converter block 1 shown in the first embodiment are connected to the low voltage side (VL side) DC power source and the high power source. Connect in parallel with the pressure side (VH side) DC power supply.
  • smoothing capacitors CL and CH for smoothing the voltage are connected between the low voltage side terminals 2 and 2a and between the high voltage side terminals 3 and 3a. Low voltage side negative terminal 2a and high voltage side negative terminal 3a are grounded.
  • Each SC cell la ⁇ The reference clock signal for driving Ld is shifted by 2 ⁇ Z4 (rad).
  • the same operation can be performed by shifting the good reference clock signal by 2 ⁇ ⁇ (rad) by (n).
  • the larger the number of SC cells the greater the effect of reducing the ripple current of the smoothing capacitors CL and CH, and the size of the smoothing capacitors CL and CH can be reduced.
  • FIG. 11 is a diagram showing a main circuit configuration of the converter device according to the sixth embodiment of the present invention.
  • an SC converter device 10 is connected between a low voltage side (VL side) DC power source and a high voltage side (VH side) DC power source.
  • Smoothing capacitors CL and CH for smoothing the voltage are connected between the low voltage side terminals 2 and 2a and between the high voltage side terminals 3 and 3a.
  • the low voltage side negative terminal 2a and the high voltage side negative terminal 3a is grounded.
  • converter device 10 includes four switches Swl00, Sw203, Sw303, Sw404, capacitor Ce3, and inductor Lr3 in the same configuration as converter block 1 of the first embodiment.
  • the three switches Sw202, Sw302, Sw402, and the capacitor Ce2 are the same units as the unit composed of the three switches Sw203, Sw303, Sw404, the capacitor Ce3, and the inductor Lr3.
  • an inductor Lr2 three switches Sw201, Sw301, Sw401, a capacitor Cel, and an inductor Lrl.
  • the source terminal of the switch Sw201 is connected to the positive terminal 2 on the low voltage side
  • the source terminal of the switch Sw202 is connected to the drain terminal of the switch Sw201
  • the switch Sw203 is connected to the drain terminal of the switch Sw202. Similar to the later-described operation, it is possible to connect the source terminals of the switches Sw201 to Sw203 to the low-voltage side positive terminal 2 as in the converter device 10a shown in FIG.
  • Each switch Swl00, Sw201 to 203, Sw301 to 303, and Sw401 to 403 receives a gate signal generated by a control circuit unit (not shown), and performs an on / off operation according to the voltage level of the gate signal.
  • Figure 13 shows the gate signal of each switch and the voltage and current waveforms of each part.
  • VL, VH, IL, and IH are the voltages and currents for the same parts as in the first embodiment, and the currents flowing through the capacitors Cel to Ce3 and the voltages of the capacitors Cel to Ce3 are also shown. . Furthermore, the directions of the current and voltage arrows shown in FIG. 11 are positive.
  • the switches Swl00 and Sw401 to 403 are off when the switches Sw201 to 203 and Sw301 to 303 are on.
  • the bodies (Cel, Lrl), (Ce2, Lr2), and (Ce3, Lr3) are connected in parallel between both terminals 2 and 2a of the low-voltage DC power supply. The energy shifts from the high-voltage side force to the low-voltage side, and each capacitor Cel ⁇ Ce3 is discharged and the voltage becomes VL ⁇ .
  • the pair of capacitors Ce (Cel to Ce3) and the inductor Lr (Lrl to Lr3) are connected in series.
  • Multiple connected series bodies (Ce, Lr) (in this case, 3) are provided, and these series bodies (Ce, Lr) are simultaneously connected in parallel between both terminals 2 and 2a of the low-voltage DC power supply.
  • the first mode and the plurality of series bodies (Ce, Lr) are simultaneously connected in series to the low voltage side DC power supply (smoothing capacitor CL) and the series connected composite series body is connected to the high voltage side DC power supply.
  • each inductor Lr and each capacitor Ce is in a series resonance state has the inductance value of each Lr as Lr, If the capacitance value of each Ce is Ce, it can be expressed by the following formula (2).
  • the resonance period Tb in which each inductor Lr and each capacitor Ce is in a series resonance state is as follows.
  • the inductance value of each Lr is Lr and the capacitance value of each Ce is Ce, It can be expressed by the following formula (3).
  • Ta Tb
  • the two types of gate signals used in the first and second modes are simply rectangular with a duty ratio of 50% as in the first embodiment. It becomes a pulse signal.
  • the series resonance phenomenon of the inductor Lr and the capacitor Ce can be used to increase the amount of energy stored in the capacitor Ce used per switching. Therefore, it is possible to increase the amount of power transferred with a small and simple circuit configuration without increasing the capacitor capacity or increasing the switching frequency.
  • the above unit including a series body in which a capacitor Ce and an inductor Lr are connected in series and a plurality of switches is sufficient if the voltage ratio is an integer of 2 or more. By further increasing the power, it is possible to transfer power at a larger voltage ratio.
  • the same effect can be obtained even if another semiconductor switching element such as a power IGBT using a MOSFET is used as the semiconductor switching element.
  • the present invention can be applied to a booster circuit, a step-down circuit, or a step-up / step-down circuit that realizes energy transfer by switching charge / discharge of a capacitor by switching operation of a semiconductor switching element.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

La présente invention concerne un convertisseur CC-CC composé d'un condensateur et de transistors de commutation et qui possède une structure de circuit simple de petite taille, capable d'augmenter la puissance électrique à convertir. Un convertisseur CC-CC comprend un circuit en série d'un condensateur (Ce) et d'un inducteur (Lr) inséré dans une alimentation électrique CC basse tension (VL) et une alimentation électrique CC haute tension (VH), ainsi que des éléments de commutation à semi-conducteurs (Sw1 à Sw4). Un mode, dans lequel la conduction simultanée des commutateurs (Sw2, Sw3) et la conduction simultanée des commutateurs (Sw1, Sw4) sont alternativement commutées en utilisant, comme fréquence d'attaque, la fréquence de résonance à laquelle le condensateur (Ce) et l'inducteur (Lr) résonnent en série et où le circuit en série est relié à l'alimentation électrique CC basse tension (VL), et un mode, dans lequel le circuit en série est relié en série à l'alimentation électrique CC basse tension (VL) et où ce second circuit en série est relié en parallèle à l'alimentation électrique CC haute tension (VH), sont alternativement commutés, ce qui augmente la puissance convertie pour chaque commutation.
PCT/JP2006/318029 2006-09-12 2006-09-12 Convertisseur cc-cc WO2008032362A1 (fr)

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Cited By (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2011229247A (ja) * 2010-04-19 2011-11-10 Mitsubishi Electric Corp Ｄｃ／ｄｃ電圧変換装置
WO2012001828A1 (fr) * 2010-06-29 2012-01-05 三菱電機株式会社 Convertisseur d'énergie cc-cc
EP2819290A3 (fr) * 2013-06-26 2015-04-08 Industry Foundation of Chonnam National University Convertisseur CC/CC résonnant bidirectionnel avec le même potentiel électrique d'entrée et de sortie
US9543842B2 (en) 2011-06-23 2017-01-10 University Court Of The University Of Aberdeen Converter for transferring power between DC systems
EP3320607A4 (fr) * 2015-07-10 2019-03-06 Maxim Integrated Products, Inc. Systèmes et procédés de réduction de tension de commutation dans des alimentations de puissance à mode commuté
CN109639132A (zh) * 2018-12-19 2019-04-16 北京理工大学 一种谐振开关电容变换器
IT201900006719A1 (it) * 2019-05-10 2020-11-10 St Microelectronics Srl Convertitore elettronico
US11133672B1 (en) 2020-03-06 2021-09-28 Hamilton Sundstrand Corporation System and method for adding a high voltage DC source to a power bus

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JPS62123695A (ja) * 1985-11-25 1987-06-04 松下電工株式会社 電源装置
JPH04105552A (ja) * 1990-08-24 1992-04-07 Toyota Autom Loom Works Ltd Ｄｃ―ｄｃコンバータ
JP2000324851A (ja) * 1998-12-22 2000-11-24 Tdk Corp 部分共振ｐｗｍコンバータ
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JP2011229247A (ja) * 2010-04-19 2011-11-10 Mitsubishi Electric Corp Ｄｃ／ｄｃ電圧変換装置
WO2012001828A1 (fr) * 2010-06-29 2012-01-05 三菱電機株式会社 Convertisseur d'énergie cc-cc
JP2012016075A (ja) * 2010-06-29 2012-01-19 Mitsubishi Electric Corp Ｄｃ／ｄｃ電力変換装置
CN102959843A (zh) * 2010-06-29 2013-03-06 三菱电机株式会社 Dc/dc功率转换装置
EP2590306A1 (fr) * 2010-06-29 2013-05-08 Mitsubishi Electric Corporation Convertisseur d'énergie cc-cc
EP2590306A4 (fr) * 2010-06-29 2013-11-27 Mitsubishi Electric Corp Convertisseur d'énergie cc-cc
US9007040B2 (en) 2010-06-29 2015-04-14 Mitsubishi Electric Corporation DC-DC power conversion apparatus
US9543842B2 (en) 2011-06-23 2017-01-10 University Court Of The University Of Aberdeen Converter for transferring power between DC systems
EP2819290A3 (fr) * 2013-06-26 2015-04-08 Industry Foundation of Chonnam National University Convertisseur CC/CC résonnant bidirectionnel avec le même potentiel électrique d'entrée et de sortie
EP3320607A4 (fr) * 2015-07-10 2019-03-06 Maxim Integrated Products, Inc. Systèmes et procédés de réduction de tension de commutation dans des alimentations de puissance à mode commuté
CN109639132A (zh) * 2018-12-19 2019-04-16 北京理工大学 一种谐振开关电容变换器
IT201900006719A1 (it) * 2019-05-10 2020-11-10 St Microelectronics Srl Convertitore elettronico
US11223279B2 (en) 2019-05-10 2022-01-11 Stmicroelectronics S.R.L. Resonant switched transformer converter
US11133672B1 (en) 2020-03-06 2021-09-28 Hamilton Sundstrand Corporation System and method for adding a high voltage DC source to a power bus

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