Classifications

• • G—PHYSICS
  • G05—CONTROLLING; REGULATING
  • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
  • G05F3/00—Non-retroactive systems for regulating electric variables by using an uncontrolled element, or an uncontrolled combination of elements, such element or such combination having self-regulating properties
  • G05F3/02—Regulating voltage or current
  • G05F3/08—Regulating voltage or current wherein the variable is dc
  • G05F3/10—Regulating voltage or current wherein the variable is dc using uncontrolled devices with non-linear characteristics
  • G05F3/16—Regulating voltage or current wherein the variable is dc using uncontrolled devices with non-linear characteristics being semiconductor devices
  • G05F3/18—Regulating voltage or current wherein the variable is dc using uncontrolled devices with non-linear characteristics being semiconductor devices using Zener diodes
• • G—PHYSICS
  • G05—CONTROLLING; REGULATING
  • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
  • G05F3/00—Non-retroactive systems for regulating electric variables by using an uncontrolled element, or an uncontrolled combination of elements, such element or such combination having self-regulating properties
  • G05F3/02—Regulating voltage or current
  • G05F3/08—Regulating voltage or current wherein the variable is dc
  • G05F3/10—Regulating voltage or current wherein the variable is dc using uncontrolled devices with non-linear characteristics
  • G05F3/16—Regulating voltage or current wherein the variable is dc using uncontrolled devices with non-linear characteristics being semiconductor devices
  • G05F3/20—Regulating voltage or current wherein the variable is dc using uncontrolled devices with non-linear characteristics being semiconductor devices using diode- transistor combinations
  • G05F3/22—Regulating voltage or current wherein the variable is dc using uncontrolled devices with non-linear characteristics being semiconductor devices using diode- transistor combinations wherein the transistors are of the bipolar type only
  • G05F3/222—Regulating voltage or current wherein the variable is dc using uncontrolled devices with non-linear characteristics being semiconductor devices using diode- transistor combinations wherein the transistors are of the bipolar type only with compensation for device parameters, e.g. Early effect, gain, manufacturing process, or external variations, e.g. temperature, loading, supply voltage

Definitions

• the present invention relates to a voltage supply circuit having a starting voltage source, a continuous operating voltage source, which is realized by a voltage source oscillating after a start-up phase, and a storage capacitor, wherein the starting voltage source and the permanent operating voltage source are coupled in parallel with the storage capacitor. It also relates to a method for providing a supply voltage by means of such a power supply circuit.
• the present invention generally relates to the problem of providing a start-up suitable auxiliary voltage supply for logic circuits, in particular microcontroller, with minimal power consumption in stand-by mode.
• integrated solutions in driver circuits and ASICs are known from the prior art.
• complex circuits with operational amplifiers and current mirrors are usually used, which can not be built discretely with a few components.
• a discrete set up would be desirable to avoid custom ASICs and associated constraints in the sourcing sources.
• the object of the present invention is to further develop the aforementioned circuit arrangement such that it can be realized as a discrete, external circuit arrangement. It also exists It is to provide a corresponding method for providing a supply voltage available.
• the first-mentioned object is achieved by a power supply circuit having the features of patent claim 1, the second-mentioned task by a method having the features of patent claim 13.
• the present invention is based on the finding that the problems mentioned can be solved by using a circuit arrangement with a self-holding function. As a result, it is possible, in particular, to realize a voltage supply circuit which can be used as a discrete external solution for logic circuits, in particular controllers, which, due to the process, can only manage voltages up to their own supply voltage.
• a preferred embodiment is characterized in that the circuit arrangement with self-holding function is designed to provide an output voltage of 0 V in the startup phase, first below a predefinable threshold voltage at the storage capacitor at the output terminal, secondly from the predefinable threshold voltage at the storage capacitor at the output terminal, an output voltage with predefinable Amplitude provide, wherein the output voltage is smaller than the predetermined threshold voltage at the storage capacitor.
• the circuit arrangement with self-holding function is further designed such that in the start-up phase below a predetermined threshold voltage, the latching is disabled and from the predetermined threshold voltage latching is activated, there is the advantage that the power supply circuit according to the invention with dissolved Self-holding practically has no own power consumption.
• the self-hold circuit has a control device to control or regulate the output voltage.
• a further preferred embodiment is characterized in that an output current is provided at the output terminal, wherein the circuit arrangement is designed with self-holding function such that in the off phase after switching off the Treasurewetriebungsspringungsttle over a predetermined holding current threshold of the output current, the latching remains activated.
• an output current is provided at the output terminal, wherein the circuit arrangement with self-holding function is designed such that in the off phase after switching off the continuous operating voltage source below a predetermined holding current threshold of the output current, the latching is disabled.
• a self-latching restart is enabled when the current drawn by the circuitry powered from the power supply circuit drops below the holding current threshold, for example, a brownout.
• a brownout is the automatic, controlled shutdown of a microcontroller when falling below a threshold value in the input voltage to understand.
• the self-hold circuit includes an input terminal coupled to the storage capacitor and an output terminal coupled to the output terminal of the power supply circuit.
• the downstream load is coupled, which is preferably implemented as a microcontroller.
• the self-holding circuit further comprises first and second transistors, first, second, third and fourth resistors and first and second Zener diodes, the reference electrode of the first transistor being connected to the first transistor Input terminal, the control electrode of the first transistor with the first Zener diode, the first ohmic resistance is coupled between the reference electrode and the control electrode of the first transistor, wherein between the working electrode of the first transistor and the output terminal, the series circuit of fourth and second ohmic resistance is coupled, wherein the connection point between the fourth and the second ohmic resistance with the second Zener diode is coupled on the one hand and with the control electrode of the second transistor on the other hand, wherein the control electrode of the first transistor is coupled via the third ohmic resistor to the working electrode of the second transistor, and wherein the reference electrode of the second transistor is coupled to the output terminal.
• the predefinable threshold voltage can be predetermined by the first Zener diode.
• the holding current threshold of the output current is furthermore preferably predetermined by the first and the second ohmic resistance.
• a control or regulating device for controlling or regulating the output voltage can be realized in a simple manner by the second transistor and the second Zener diode.
• the maximum output current through the fourth ohmic resistance and the open-circuit gain of the second transistor can be predetermined.
• the self-current consumption can be dimensioned so low with activated latching that a stand-by operation is made possible solely from the starting voltage source at full output voltage at the output terminal of the power supply circuit.
• the self-holding is activated by exceeding the threshold voltage which can be predetermined by the first Zener diode.
• FIG. 1 shows a schematic representation of an embodiment of a voltage supply circuit according to the invention
• Fig. 3 shows the time course of various sizes of the circuit arrangement of the embodiment of Fig. 1 when deactivating the latching.
• Fig. 1 shows a schematic representation of an embodiment of a circuit arrangement according to the invention. It comprises an input circuit 10, which essentially serves to charge the capacitor C10 to supply the self-holding function holding arrangement 20.
• the input circuit 10 in this case comprises a starting voltage source E10 for supplying the circuit arrangement with self-holding function 20 via the capacitor C10 during a start-up phase, which is characterized in that the oscillating voltage source, which serves as a continuous operation voltage source E20, is not yet in operation.
• the resistor R10 which is arranged between the starting voltage source E10 and the capacitor C10, is preferably designed to be highly resistive.
• the start-up voltage source E10 is configured to provide a current of less than 300 ⁇ A while the steady-state voltage source E20 is configured to provide a current greater than 5 mA.
• the continuous operating voltage source E20 is in particular an oscillating voltage source which is connected to the Input terminals A1, A2 connected circuit, in particular logic circuit, which is supplied from the power supply circuit according to the invention.
• An example of an oscillating voltage source is the half-bridge center of an inverter with two switches in a half-bridge arrangement.
• the output current of the oscillating voltage source E20 is recharged in a capacitor C20, rectified by means of the diodes D21, D22 and then fed to the capacitor C10.
• the circuit arrangement with self-holding function 20 has an input terminal E, which is coupled to the storage capacitor C10, wherein its output is coupled to the output terminal A1, A2 of the power supply circuit according to the invention.
• the circuit arrangement with self-holding function 20 further comprises a first transistor T1 and a second transistor T2, a first ohmic resistor R1, a second ohmic resistor R2, a third ohmic resistor R3 and a fourth ohmic resistor R4 and a first Zener diode D1 and a second Zener diode D2 ,
• the reference electrode of the first transistor T1 is coupled to the input terminal E, the control electrode of the first transistor T1 to the first Zener diode D1, the first ohmic resistor R1 between the reference electrode and the control electrode of the first transistor T1.
• the series circuit of fourth ohmic resistor R4 and second resistor R2 is coupled, wherein the connection point between the fourth ohmic resistor R4 and the second ohmic resistor R2 with the second Zener diode D2 on the one hand and is coupled to the control electrode of the second transistor T2 on the other hand.
• the control electrode of the first transistor T1 is coupled via the third ohmic resistor R3 to the working electrode of the second transistor T2, wherein the reference electrode of the second transistor T2 is coupled to the output terminal A1, A2.
• U 3 is not allowed to increase synchronously with the voltage U i, since then already a current would be taken out of the capacitor C 10 and would not allow a rise on U DI there, this high voltage value being needed to drive etc. in the circuit connected to connection A1, A2.
• a typical value for UD I is more than 10 V, in particular for example 18 V. Accordingly, the capacitor C10 is charged to a higher voltage than is actually required by the circuit connected to the terminals A1, A2.
• a current flows I 30 , see Fig. 2c, which exceeds by the starting resistance R10 by a multiple.
• the nominal value I 30 of the current I 3 can be adjusted by the resistor R4 and the open-loop gain of the transistor T2.
• the capacitor C10 is therefore discharged.
• the circuit connected to the output terminal A1, A2 activates an oscillating voltage source E20, see FIG. 2d.
• the current of this voltage source E20 is transposed in the capacitor C20 and rectified by means of the diodes D21, D22 and supplied to the capacitor C10. This current takes over the supply of the circuit connected to the output terminal A1, A2 in continuous operation.
• Fig. 2a The phase described last is shown in Fig. 2a to detect the drop in voltage U to a value of approximately 10 V, at the end, see Fig. 2d * oscillating voltage source E20 with a time offset of At based on the maximum value of Voltage Ui begins to oscillate. Then the voltage Ui rises again.
• the circuit arrangement connected to the output terminal A1, A2 is supplied from the capacitor C10.
• the circuit arrangement In order to ensure a good takeover, ie an uninterrupted change from the supply from the source E10 to the supply from the source E20, the circuit arrangement must enable a sufficiently large voltage swing.
• the transistor T2 is kept conductive by a current from the base to the collector of the transistor T1, the resistor R4 and then via the base to the emitter of the transistor T2.
• the voltage U 3 remains at its nominal value U 30 , see FIG. 3b. This state continues until the voltage across the resistor R1, set by the dimensioning of the resistors R1 and R2, falls below the base-emitter threshold voltage of the transistor T1. As a result, the transistor T1 begins to block, thereby blocking the transistor T2, whereby the latch is released.
• Fig. 3c Two cases must be distinguished, see Fig. 3c: If the current I 3, for example, to 200 uA, the voltage Ui rises slowly, with recharge via the source E10, on. As a result, the voltage U 3 is still maintained at its nominal value U 30 . However, if the current I 3 decreases even further, for example, when reset to 10 ⁇ A, the latching is solved because the current is too low, thereby maintaining the conductive state of the transistor T1, see Fig. 3c and Fig. 3b. The voltage U 3 , see Fig. 3b, goes back to 0V. As a result, a new start, as described with reference to FIG. 2, again possible.

Priority Applications (4)

Applications Claiming Priority (1)

Publications (1)

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Citations (3)

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• 2006
  • 2006-07-28 CN CN2006800554881A patent/CN101501604B/zh not_active Expired - Fee Related
  • 2006-07-28 KR KR1020097004239A patent/KR101298565B1/ko not_active IP Right Cessation
  • 2006-07-28 EP EP06762883A patent/EP2047349A1/de not_active Withdrawn
  • 2006-07-28 WO PCT/EP2006/007502 patent/WO2008011905A1/de active Application Filing

Patent Citations (3)

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