WO2004105301A1 - Procedimiento de reducción de la varianza de la estimación de la relación señal a ruido de una señal con modulación diferencial en fase y cohenrente en amplitud - Google Patents
Procedimiento de reducción de la varianza de la estimación de la relación señal a ruido de una señal con modulación diferencial en fase y cohenrente en amplitud Download PDFInfo
- Publication number
- WO2004105301A1 WO2004105301A1 PCT/ES2004/000223 ES2004000223W WO2004105301A1 WO 2004105301 A1 WO2004105301 A1 WO 2004105301A1 ES 2004000223 W ES2004000223 W ES 2004000223W WO 2004105301 A1 WO2004105301 A1 WO 2004105301A1
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- WO
- WIPO (PCT)
- Prior art keywords
- amplitude
- signal
- phase
- variance
- noise
- Prior art date
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Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
- H04L27/20—Modulator circuits; Transmitter circuits
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
- H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
- H04L27/38—Demodulator circuits; Receiver circuits
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R29/00—Arrangements for measuring or indicating electric quantities not covered by groups G01R19/00 - G01R27/00
- G01R29/26—Measuring noise figure; Measuring signal-to-noise ratio
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L1/00—Arrangements for detecting or preventing errors in the information received
- H04L1/20—Arrangements for detecting or preventing errors in the information received using signal quality detector
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
Definitions
- the present invention refers to a method of reducing the variance of the estimation of the signal-to-noise ratio of a signal with differential phase modulation and coherent in breadth.
- the method of the invention is applicable to communications systems regardless of the physical medium they use for communication.
- This procedure makes it possible to reduce the variance of the estimates and match that variance between the optimal constellations of bits per odd and even symbol.
- the system can adapt to the maximum data transfer rate offered by the channel.
- DAPSK differential in amplitude and phase
- ADPSK modulation (differential phase modulation and amplitude coherent) is known in the state of the art as it appears in "Comparison and optimization of differentially encoded transmission on fading channels", L. Lampe and R. Fischer, Proceedings ISPLC '99;"Performance evaluation of non-coherent transmission over power lines", L. Lampe, R. Fischer and R. Schober, Proceedings ISPLC'OO;"Differential encoding strategies for transmission over fading channels", R. Fischer, L. Lampe and S.
- ADPSK modulation represents the best compromise between performance and receiver complexity for practical implementation.
- Another of the important factors to achieve that maximum data transfer rate is to minimize overhead (system control information necessary for a correct reception of the data and that is sent with them).
- This overhead is more important if transmission strategies are used based on the use of multiple carriers such as OFDM (orthogonal frequency division multiplexing) where symbol times are much longer and contain much more information than in a digital communication in which employs a single information carrier frequency.
- ADPSK modulation has two important requirements. The first is that, because some of the information is encoded in the phase increments, it is necessary to previously send a symbol that constitutes a phase reference for the receiver. Likewise, the rest of the information is encoded in the value of the amplitude of the received symbol. Therefore, the second requirement involves estimating the value of the amplitude of the response of the channel to correct its effect on the receiver.
- the real channels show some variation of their characteristics with the time that forces the receiver to track and update that estimate. initial. In addition, this temporal variation also requires a continuous update of the SNR estimate.
- this procedure allows the insertion of data symbols in the frame so that users to whom the transmitter data is not directed, and who do not know the constellation with which they are modulated, can monitor the channel and follow its variations both of amplitude as SNR. Therefore, to optimize the transfer of data in a multi-user communication, it is necessary to estimate the SNR perceived by the receiver. This estimate can only be made when the constellation in which the received data is modulated is known to the receiver. In addition, the period during which the SNR is estimated may comprise modulated symbols with different constellations.
- the problem to be solved is to estimate the SNR in the receiver of a signal with ADPSK modulation during a period that includes the reception of a certain number of data symbols with the possibility that they are modulated using different constellations.
- various techniques are presented to estimate the SNR of a signal with coherent phase modulation (PSK). It also indicates how to extend these techniques to a QAM modulation. In both cases it is not taken into account that the constellation may change during the estimation time.
- the average power of the transmitted signal can be known if the constellation is normalized in power and the effect of the receiving channel is equalized. Then, to estimate the SNR in the receiver it is only necessary to estimate the noise power in the constellation received. That noise power estimate is easily made by averaging the noise power samples. Thus, the problem is to calculate those samples in the receiver. But another added problem is the differential character of the phase in ADPSK modulation; In this case the constellation received is the constellation formed by the amplitudes and phase increments received. If the value of the samples of the noise power is obtained by calculating the squared module of the noise vector given by the error in amplitude and by the error in the phase increase, without any modification, it is observed that the estimate presents a greater variance in the constellations of bits by odd symbol.
- This effect is not admissible because the period during which the SNR is estimated may comprise modulated symbols with different constellations in an optimal multi-user communications system.
- This communications system also includes transmissions intended for multiple users (multicast) or all (broadcast), in addition to transmissions to a single user (unicast).
- the proposed method of the invention presents a method of estimating the SNR of a signal with ADPSK modulation that matches the variances of the estimate in constellations with odd and even bits per symbol, further reducing the variance of said estimate for all cases.
- the invention consists in a method of reducing the variance of the estimation of the signal to noise ratio of a signal with differential modulation in phase and coherent in amplitude.
- This procedure is applicable to the bidirectional communication of multiple user equipment in which a differential phase modulation and coherent in amplitude is used, which requires the sending of a phase reference symbol prior to the sending of information, and where a estimation of the signal-to-noise ratio in order to employ a modulation with the maximum number of bits per symbol, maintaining the probability of bit error in reception within given ranges.
- the process of the invention is characterized in that, starting from the amplitude error and the error in the phase increment corresponding to the constellation point received, a translation of said errors is made to the corresponding point of the first constellation ring as if it had been this is the one transmitted and without any modification, and then the squared module of the error vector is calculated.
- This feature allows to calculate the noise samples, reduce the variance of the values obtained and match this variance between the optimal constellations of bits per odd and even symbol.
- an average of the squared module of the noise samples can be performed to estimate the average value of the noise power, the number of samples to average a configurable system value.
- the amplitude and phase increase are detected and then these values are subtracted from the amplitude and phase increase received, or vice versa, that is, they are subtracted from the amplitude and phase increase received, the amplitude and the phase increase detected respectively; that is, a first way to calculate the noise samples is done in blind mode, without knowing the symbol transmitted in the calculation of amplitude and phase increase errors.
- Another way of obtaining the squared module of the noise vector consists in subtracting respectively the amplitude and phase increment of the previously transmitted symbols received in reception, the amplitude and the phase increment received, or vice versa, that is, they are subtracted from the amplitude and phase increment received, the amplitude and phase increment of previously transmitted and known symbols in reception respectively; that is, noise samples are calculated using a sequence of symbols previously known in reception for the calculation of amplitude and phase increase errors.
- the invention envisages combining the above estimates, so that the receiving equipment that estimates the signal-to-noise ratio combines estimates in blind mode and estimates with known sequence of symbols.
- the samples of the noise power to be averaged may belong to different constellations. Therefore, to correct the bias of the estimator, due to the differential nature of the modulation and of different value in each constellation, multiply each of the samples of the noise power that are averaged by The corresponding value.
- FIGURES Figure 1 Represents a constellation formed by the amplitudes and phase increments of a 6-bit ADPSK constellation per symbol.
- Figure 2. Schematically represents the magnitudes involved in the calculation of a sample of the noise power.
- Figure 3 Schematically represents the magnitudes involved in the calculation of a sample of the noise power and its translation to the first ring.
- Figure 4. Represents an example of a block diagram of a receiver that implements the method of the invention. DESCRIPTION OF AN EXAMPLE OF REALIZATION OF THE
- FIG. 1 presents an example in which the constellation is formed by the equalized amplitude and the phase increase of the received signal for a 6-bit constellation per symbol with an SNR of 27.9 decibels (dB) and a frequency error 5 parts per million (ppm). Continuous radial lines represent the optimal decision thresholds for phase increments.
- the points received are grouped in clouds of elliptical shaped points whose shape is more pronounced when the amplitude of the rings is greater, because of the differential character of the modulation.
- These point clouds are centered at each of the constellation points and are due to the noise that is added to the signal. But, as you can see, point clouds are not centered between the optimal thresholds, but rather a certain number of radians displaced. This fixed displacement is determined by the frequency error in the receiver.
- the SNR estimator should only estimate the noise power suffered by the receiver. For this, an average of N samples of noise power in different symbols is made:
- a k is the amplitude detected
- a k is the amplitude received and equalized to compensate for the attenuation of the channel
- a ⁇ k is the phase increase detected
- a ⁇ k the phase increase received.
- the noise power sample is obtained by calculating the squared module of the vector (2):
- the objective is to make the samples independent of the noise power of the ring to which the detected point belongs.
- the new noise power sample can be calculated as:
- r is the amplitude of the first ring of the corresponding constellation.
- the average of N samples is performed to calculate the noise power in the same way:
- Figure 4 shows an example of a block diagram of a receiver that implements the method of the invention presented. The starting data needed by the block that calculates the noise power samples
- phase errors (4) and amplitude (1) can be done in two ways. The first is to calculate these errors from the detection of the amplitude (19), and the phase increase (20), received; that is, the sequence of symbols sent by the transmitter is unknown.
- This mode is called blind estimation and is affected by detection errors, which prevents estimating the S ⁇ R when they occur; since the calculated errors will be smaller in magnitude to those that have actually occurred and the estimate of the S ⁇ R will be greater than the one that really affects the system.
- the second way to calculate phase and amplitude errors is based on sequence knowledge. transmitted, so these errors will correspond exactly to those produced by not mediating any detection in the process. In this exemplary embodiment, both are carried out, thus by means of a block (21) the amplitude values A k (23), and phase increment A incremento k (24), transmitted are generated. There must be an equal block in the transmitter for the transmission and reception sequences to be the same.
- the receiver will not always know the constellation with which the data he receives is modulated. You will only know it in a unicast communication when it is the destination of the transmitted data or when a multicast communication is made that includes it in the group of recipients or in a broadcast; That is why the N samples of the noise power that are averaged can belong to different constellations.
- a signal (15) indicates that the constellation is known and that the noise power samples can be calculated.
- the block (12) must apply this correction factor K, to the samples of the noise power to correct the biased nature of the estimator, by:
- the number of bits per symbol (14), is used to determine the value of r, (6), and of the correction factor K to be used in the calculation. This correction must be made sample by sample since these samples can belong to different constellations. As an average of the samples is made, a memory (13) is necessary to store the partial value of the sum presented above.
- the operation performed by block (12) is as follows:
- block (12) generates a signal (16) indicating that there is an estimate of available noise power.
- a signal (22) again indicates the estimation mode, blind or with known sequence, which will determine the number of samples N, to accumulate.
- the signal (16) indicates it, the memory is read and the value is divided by the corresponding N value.
- the estimation mode with known sequence is more reliable than the blind mode, but has the disadvantage that it does not allow data to be sent to the receivers.
- it is necessary to monitor the S ⁇ R of the channel so that the system can adapt the number of bits per symbol to be used.
- an estimate is made with a known sequence. Then new estimates are made with known sequence with a periodicity of seconds . These estimates can produce blind mode estimates (depending on data traffic) that are used to determine if there has been a sharp change in the channel. If the change in the channel causes a significant worsening of the actual SNR, it will be necessary to perform an estimate with a known sequence to avoid the error that occurs in the blind estimate described above.
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- Engineering & Computer Science (AREA)
- Computer Networks & Wireless Communication (AREA)
- Signal Processing (AREA)
- Physics & Mathematics (AREA)
- General Physics & Mathematics (AREA)
- Quality & Reliability (AREA)
- Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
- Radio Transmission System (AREA)
Abstract
Description
Claims
Priority Applications (10)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
MXPA05012716A MXPA05012716A (es) | 2003-05-26 | 2004-05-19 | Procedimiento de reduccion de la varianza de la estimacion de la relacion senal a ruido de una senal con modulacion diferencial en fase y coherente en amplitud. |
CA002527332A CA2527332A1 (en) | 2003-05-26 | 2004-05-19 | Method of reducing the variance of a signal-to-noise ratio estimate for a signal with differential phase and coherent amplitude modulation |
EP04733827.2A EP1633072B1 (en) | 2003-05-26 | 2004-05-19 | Method of reducing the variance of a signal-to-noise ratio estimate for a signal with differential phase and coherent amplitude modulation |
BRPI0410719-5A BRPI0410719A (pt) | 2003-05-26 | 2004-05-19 | método para reduzir a variação de uma avaliação de relação sinal/ruìdo para um sinal com modulação de fase diferencial e amplitude coerente |
AU2004240362A AU2004240362A1 (en) | 2003-05-26 | 2004-05-19 | Method of reducing the variance of a signal-to-noise ratio estimate for a signal with differential phase and coherent amplitude modulation |
EA200501864A EA009251B1 (ru) | 2003-05-26 | 2004-05-19 | Способ уменьшения разброса результатов оценки отношения сигнал-шум для сигнала с относительной фазовой и когерентной амплитудной модуляцией |
KR1020057022640A KR101078440B1 (ko) | 2003-05-26 | 2004-05-19 | 차동 위상 및 코히어런트 진폭 변조로 신호의 신호 대잡음비 추정치의 분산을 감소시키는 방법 |
JP2006530296A JP4714806B2 (ja) | 2003-05-26 | 2004-05-19 | 差動位相及びコヒーレント振幅変調を有する信号のための信号対雑音比推定の分散を低減する方法 |
US11/284,799 US7433428B2 (en) | 2003-05-26 | 2005-11-22 | Method of reducing the variance of the signal-to-noise rate estimated for a signal with amplitude differential phase-shift keying modulation |
IL172141A IL172141A (en) | 2003-05-26 | 2005-11-23 | Method of reducing the variance of a signal-to-noise ratio estimate for a signal with differential phase and coherent amplitude modulation |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
ES200301229A ES2221568B2 (es) | 2003-05-26 | 2003-05-26 | Procedimiento de reduccion de la varianza de la estimacion de la relacion señal a ruido de una señal con modulacion diferencial en fase y coherente en amplitud. |
ESP200301229 | 2003-05-26 |
Related Child Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US11/284,799 Continuation US7433428B2 (en) | 2003-05-26 | 2005-11-22 | Method of reducing the variance of the signal-to-noise rate estimated for a signal with amplitude differential phase-shift keying modulation |
Publications (1)
Publication Number | Publication Date |
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WO2004105301A1 true WO2004105301A1 (es) | 2004-12-02 |
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PCT/ES2004/000223 WO2004105301A1 (es) | 2003-05-26 | 2004-05-19 | Procedimiento de reducción de la varianza de la estimación de la relación señal a ruido de una señal con modulación diferencial en fase y cohenrente en amplitud |
Country Status (14)
Country | Link |
---|---|
US (1) | US7433428B2 (es) |
EP (1) | EP1633072B1 (es) |
JP (1) | JP4714806B2 (es) |
KR (1) | KR101078440B1 (es) |
CN (1) | CN100531024C (es) |
AU (1) | AU2004240362A1 (es) |
BR (1) | BRPI0410719A (es) |
CA (1) | CA2527332A1 (es) |
EA (1) | EA009251B1 (es) |
ES (1) | ES2221568B2 (es) |
IL (1) | IL172141A (es) |
MX (1) | MXPA05012716A (es) |
TW (1) | TWI279097B (es) |
WO (1) | WO2004105301A1 (es) |
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
KR100930016B1 (ko) | 2005-02-14 | 2009-12-07 | 인터디지탈 테크날러지 코포레이션 | 슬라이딩 윈도우 블록 선형 이퀄라이저를 갖춘 진보된수신기 |
Families Citing this family (9)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
ES2221568B2 (es) | 2003-05-26 | 2005-07-16 | Diseño De Sistemas En Silicio, S.A. | Procedimiento de reduccion de la varianza de la estimacion de la relacion señal a ruido de una señal con modulacion diferencial en fase y coherente en amplitud. |
US7414581B2 (en) | 2006-01-06 | 2008-08-19 | Honeywell International Inc. | Method for improved signal to noise ratio estimation |
US8238481B2 (en) * | 2008-07-02 | 2012-08-07 | Qualcomm Incorporated | Blind channel estimation for PSK and D-PSK modulated multicarrier communication systems |
GB2548293B (en) * | 2012-05-30 | 2018-01-17 | Imagination Tech Ltd | Noise variance estimation and interference detection |
US8878620B2 (en) * | 2012-08-24 | 2014-11-04 | Tektronix, Inc. | Phase coherent playback in and arbitrary waveform generator |
CN103095636B (zh) * | 2012-12-07 | 2015-06-03 | 桂林电子科技大学 | 差分球调制方法 |
CN104917706B (zh) * | 2014-03-10 | 2018-08-10 | 联想(北京)有限公司 | 一种信噪比估计方法及电子设备 |
RU2598693C1 (ru) * | 2015-03-25 | 2016-09-27 | ООО "Топкон Позишионинг Системс" | Способ и устройство для оценки текущего отношения сигнал-шум |
KR101595830B1 (ko) * | 2015-09-21 | 2016-02-24 | 대한민국 | 단파 통신 두절의 판단을 위한 단파 신호 모니터링 방법 및 장치 |
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US20040105396A1 (en) * | 2002-11-08 | 2004-06-03 | Thales | Method and modem for phase synchronization and tracking |
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US5809074A (en) * | 1996-11-08 | 1998-09-15 | Lucent Technologies Inc. | Technique for improving the blind convergence of an adaptive equalizer using a transition algorithm |
EP0993147A3 (en) * | 1998-09-30 | 2004-01-14 | Mitsubishi Materials Corporation | Radio server system |
JP3776716B2 (ja) * | 2000-11-17 | 2006-05-17 | 株式会社東芝 | 直交周波数分割多重伝送信号受信装置 |
US6735264B2 (en) * | 2001-08-31 | 2004-05-11 | Rainmaker Technologies, Inc. | Compensation for non-linear distortion in a modem receiver |
US7756421B2 (en) * | 2002-10-03 | 2010-07-13 | Ciena Corporation | Electrical domain compensation of non-linear effects in an optical communications system |
ES2221568B2 (es) | 2003-05-26 | 2005-07-16 | Diseño De Sistemas En Silicio, S.A. | Procedimiento de reduccion de la varianza de la estimacion de la relacion señal a ruido de una señal con modulacion diferencial en fase y coherente en amplitud. |
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2003
- 2003-05-26 ES ES200301229A patent/ES2221568B2/es not_active Expired - Fee Related
-
2004
- 2004-05-19 WO PCT/ES2004/000223 patent/WO2004105301A1/es active Application Filing
- 2004-05-19 AU AU2004240362A patent/AU2004240362A1/en not_active Abandoned
- 2004-05-19 CA CA002527332A patent/CA2527332A1/en not_active Abandoned
- 2004-05-19 MX MXPA05012716A patent/MXPA05012716A/es active IP Right Grant
- 2004-05-19 CN CNB2004800214062A patent/CN100531024C/zh not_active Expired - Lifetime
- 2004-05-19 JP JP2006530296A patent/JP4714806B2/ja not_active Expired - Fee Related
- 2004-05-19 KR KR1020057022640A patent/KR101078440B1/ko not_active IP Right Cessation
- 2004-05-19 EP EP04733827.2A patent/EP1633072B1/en not_active Expired - Lifetime
- 2004-05-19 BR BRPI0410719-5A patent/BRPI0410719A/pt not_active IP Right Cessation
- 2004-05-19 EA EA200501864A patent/EA009251B1/ru not_active IP Right Cessation
- 2004-05-26 TW TW093114932A patent/TWI279097B/zh not_active IP Right Cessation
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2005
- 2005-11-22 US US11/284,799 patent/US7433428B2/en not_active Expired - Fee Related
- 2005-11-23 IL IL172141A patent/IL172141A/en not_active IP Right Cessation
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---|---|---|---|---|
KR100930016B1 (ko) | 2005-02-14 | 2009-12-07 | 인터디지탈 테크날러지 코포레이션 | 슬라이딩 윈도우 블록 선형 이퀄라이저를 갖춘 진보된수신기 |
Also Published As
Publication number | Publication date |
---|---|
KR101078440B1 (ko) | 2011-11-01 |
CN100531024C (zh) | 2009-08-19 |
EP1633072B1 (en) | 2017-10-25 |
EP1633072A1 (en) | 2006-03-08 |
AU2004240362A1 (en) | 2004-12-02 |
US20060159201A1 (en) | 2006-07-20 |
ES2221568B2 (es) | 2005-07-16 |
CA2527332A1 (en) | 2004-12-02 |
EA009251B1 (ru) | 2007-12-28 |
TW200507490A (en) | 2005-02-16 |
MXPA05012716A (es) | 2006-02-08 |
IL172141A (en) | 2011-04-28 |
ES2221568A1 (es) | 2004-12-16 |
KR20060059883A (ko) | 2006-06-02 |
JP4714806B2 (ja) | 2011-06-29 |
US7433428B2 (en) | 2008-10-07 |
BRPI0410719A (pt) | 2006-06-20 |
JP2007501579A (ja) | 2007-01-25 |
IL172141A0 (en) | 2006-04-10 |
EA200501864A1 (ru) | 2006-06-30 |
TWI279097B (en) | 2007-04-11 |
CN1830172A (zh) | 2006-09-06 |
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