WO2004077662A1 - Dispositif d'amplification de puissance pour systeme de communication - Google Patents

Dispositif d'amplification de puissance pour systeme de communication Download PDF

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Publication number
WO2004077662A1
WO2004077662A1 PCT/CN2003/000144 CN0300144W WO2004077662A1 WO 2004077662 A1 WO2004077662 A1 WO 2004077662A1 CN 0300144 W CN0300144 W CN 0300144W WO 2004077662 A1 WO2004077662 A1 WO 2004077662A1
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WO
WIPO (PCT)
Prior art keywords
power
signal
amplifier
gain factor
amplifying device
Prior art date
Application number
PCT/CN2003/000144
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English (en)
Inventor
James Peroulas
Original Assignee
Huawei Technologies Co., Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Huawei Technologies Co., Ltd filed Critical Huawei Technologies Co., Ltd
Priority to AU2003213984A priority Critical patent/AU2003213984A1/en
Priority to CNB038246678A priority patent/CN100474762C/zh
Priority to PCT/CN2003/000144 priority patent/WO2004077662A1/fr
Publication of WO2004077662A1 publication Critical patent/WO2004077662A1/fr

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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/60—Amplifiers in which coupling networks have distributed constants, e.g. with waveguide resonators
    • H03F3/602—Combinations of several amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0294—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers using vector summing of two or more constant amplitude phase-modulated signals

Definitions

  • the invention relates to a signal transmission system, and more particularly to a power amplifying device for a communication system.
  • the final step in a communication system involves the amplification of a low power signal to the power level that is required by the transmission medium.
  • the source information signal may have a power level of about 1 milliwatt whereas the radio channel may require a transmit power ten thousand times greater at about 10 watts.
  • the process of amplifying such a low power signal to a high power level is called power amplification and is accomplished by using a power amplifier or PA.
  • the power amplifier has some very difficult requirements. It must accurately amplify the source signal, it must not distort the source signal, it must not transmit energy outside the frequency range of the source signal, it must act on the entire bandwidth of the source signal, and it must do all of the above in a very efficient manner. For a fixed architecture and process technology, the classical tradeoffs have been between bandwidth, efficiency, and linearity. Improving one parameter necessarily reduces the performance of the other parameters .
  • Modern modulation schemes such as QAM do not allow any tricks to be used and the power amplification problem can no longer be avoided.
  • Modern transmitters must accept wide bandwidth signals where the information is carried both in the amplitude and in the phase of the transmitted signal .
  • LINC architecture which stands for Linear amplification using Nonlinear Components. This architecture also goes by the names "Outphasing" and "Chireix” .
  • the two digital component signals Si (n) and s 2 (n) each have the property that for all values of n, their magnitude is always constant. No matter what the digital source signal s (n) looks like, no matter what the power of the digital signal s (n) is, the magnitude (and hence the power) of the digital component signals s 1 (n) and s 2 (n) will always be exactly the same.
  • the digital source signal s (n) which contains both amplitude and phase variations, has been decomposed into two signals that have only phase variations.
  • the following equations describe the signal decomposition operation and assume that the digital source signal s (n) is constrained so that its magnitude is less than or equal to 1.
  • the two digital component signals s (n) and s 2 (n) are converted into two analog signals S ⁇ . (t) and s 2 (t) by means of a first D/A converter 11 and a second D/A converter 12.
  • the two analog signals s x (t) and s 2 (t) are modulated to a desired carrier frequency f c by means of a modulator 13.
  • the .modulated signals are respectively amplified by a first power amplifier 15 and a second power amplifier 16.
  • the amplified signals x x (t) and x 2 (t) are combined by a signal combiner 17 to obtain an output signal x(t) to be transmitted through an antenna.
  • this architecture has received attention is that although it requires two power amplifiers, the power amplifiers in this architecture are much easier to construct than a single power amplifier because the signals going into these power amplifiers have characteristics that are easier to amplify. Specifically, the signals going into the power amplifiers are constant magnitude signals that can be amplified using simple, cheap amplifiers, such as, but not limited to, Class C amplifiers. This architecture has only limited real world use because it is very sensitive to gain and phase imbalances between the two amplifiers.
  • Fig.2a shows an example, the X-axis ranges from -fs/2 to +fs/2, where fs is the sampling rate of the D/A converters and is also equal to the sampling rate of the digital source signal s (n) as well as the two component signals s x (n) and s 2 (n) .
  • the Y-axis, standing for x( ⁇ ), is measured in dB and is useful for relative measurements, i.e., since the passband is at 0 dB, one can say that the noise energy begins to appear 30 dB below the passband.
  • the graph in Fig.2b is the result of zooming in on the passband of the graph in Fig.2a.
  • the X-axis in Fig.2b ranges from approximately -0.025fs/2 to approximately 0.3fs/2..
  • the two graphs in Fig.2a and Fig.2b are the result of plotting the same data, but on different scales. -
  • a 0.25 dB gain imbalance causes out of band noise to begin to appear about 30 dB below the passband.
  • the noise introduced does not scale with the input power. For example, in the above scheme with a full power source signal, the out of band emissions are 30 dB below the passband. If the source power is reduced by 12 dB (for example) , the out of band emissions will not go down by 12 dB. They will stay at a fixed absolute power level. Therefore, the out of band emissions will be 18 dB below the passband.
  • Fig.3a shows the relationship of a source signal, an intermediate signal (a combined signal of the two analog signals S ⁇ (t)+s 2 (t)) and an output signal x(t) of the conventional power amplifying device for a communication system where the digital source signal is a full power source signal.
  • Fig.3b shows the relationship of a source signal, an intermediate signal (a combined signal of the two analog signals S ⁇ (t)+s 2 (t)) and an output signal x(t) of the conventional power amplifying device for a communication system where the digital source signal is a weak source signal.
  • the two rippled lines indicate the introduced output noise.
  • the introduced output noise is always added at an absolute power level regardless of the input power level .
  • the noise produced by the amplifier imbalance is relative to the power of the analog signals s x (t) and s 2 (t).
  • the power of these signals is constant, and hence the noise caused by the amplifier imbalance is also going to be constant. It does not depend on the strength of the input signal .
  • the requirements on the out of band noise are not just the dBc requirement for transmission. The requirement is actually the dBc requirement plus the expected dynamic range of the output signal. If the average power of the output signal is expected to vary by 20 dB and the out of band emission requirements are 30 dBc, then the noise introduced by the amplifier imbalances must be 50 dBc below the maximum output power .
  • the sensitivity to gain imbalance has usually been solved either with a complex network to compensate for the amplifier imbalance. Or with a complex measurement device to measure the performance of every component to make sure that only devices with a similar performance are used.
  • Another problem with this architecture is that the two amplifiers are always operating at full power. For instance, if 20 watts are needed at the antenna, then each amplifier will produce 10 watts and all the energy will be sent to the antenna. However, if only 1 watt is needed, each amplifier will still produce 10 watts of output. 1 watt will be sent out of the antenna and 19 watts will be wasted and dissipated as heat in the combiner.
  • the object of the invention is to solve the above- mentioned problems in the prior art by providing a power amplifying device for a communication system, in which no complex network is needed to compensate for amplifier imbalance, no complex measurement device is required to measure the absolute performance of every power amplifier, the power consumption of the power amplifiers can be reduced, lighter power cables can be used, smaller/fewer backup batteries are needed, and a smaller heat sink can be used.
  • the power amplifying device for a communication system comprises a decomposer for decomposing a digital source signal into a first digital component signal and a second digital component signal; a first D/A converter for converting the first digital component signal into a first analog signal; a second D/A converter for converting the second digital component signal into a second analog signal; a first power amplifier for amplifying the first analog ,- signal to obtain a first amplified signal; a second power amplifier for amplifying the second analog signal to obtain a second amplified signal; a signal combiner for combining the first amplified signal and the second amplified signal to obtain an output signal to be transmitted through an antenna.
  • the power amplifying device for a communication system further comprises a power detection & gain factor calculation device and a third amplifier for amplifying the digital signal to be decomposed by said decomposer; said power detection & gain factor calculation device detects the power value of said digital signal, adjusts the gain factor of the third amplifier and the gain factor of the first power amplifier and the second power amplifier based on the detected power value of said digital signal.
  • this invention involves adding a circuit that measures the average power of the digital source signal and calculates two gain factors, adding a gain device before the decomposer, and adding gain control on the two power amplifiers.
  • the power detection & gain factor calculation device detects that the power of the digital source signal is low, it will increase the gain of the signal going into the decomposer so that at all times, the decomposer is receiving a full power signal.
  • the first and the second amplifiers on the other hand, will have their gain factor reduced by the same amount that the gain of the signal going into the decomposer was increased, so that the overall gain factor of the system is constant.
  • the amplifiers will always be producing a signal that will use the full power of both the amplifiers.
  • the noise added by the amplifiers will always be relative to a full power signal, regardless of the power of the input signal. Since full power is not always needed at the output, the gain factor of the power amplifiers will be adjusted to lower both the signal power and the noise power to the desired transmit power level . This way, the requirements on the balance between the amplifiers are reduced.
  • the requirements on amplifier balancing are still only 30 dB.
  • the amplifier balancing will take care of the adjacent channel noise and the power detection and gain factor calculation device will take care of increasing and reducing both the signal power and the noise power.
  • a complex network is not needed to compensate for amplifier imbalance. Neither is a complex measurement device required to measure the absolute performance of every power amplifier.
  • the gain factor of the amplifiers can be adjusted by changing their DC supply voltage. This will also reduce their power consumption. For example, if only 1 watt is needed at the antenna, then the DC supply of the power amplifiers will be reduced so that they only produce 1 watt of power in total . In the conventional architecture, if only 1 watt was needed, the power amplifiers would still produce 9 watts of power.
  • Fig.l is a schematic drawing of a conventional power amplifying device for a communication system
  • Fig.2a and Fig.2b are graphs showing the out of band noise introduced due to gain imbalance of the two power amplifiers in the conventional power amplifying device for a communication system
  • Fig.3a shows the relationship of a source signal, the intermediate signal and the output signal of the conventional power amplifying device for a communication system where the digital source signal is a full power source signal
  • Fig.3b shows the relationship of a source signal, the intermediate signal and the output signal of the conventional power amplifying device for a communication system where the digital source signal is a weak power source signal
  • Fig. is a schematic drawing of a power amplifying device for a communication system according to the invention
  • Fig.5 (a) -Fig.5 (d) show the relationship of a source signal, the intermediate signal, the out of band noise introduced due to gain imbalance and the output signal of the power amplifying device for; a communication system according to the invention where the digital source signal is a weak power source signal .
  • the digital source signal of the power amplifying device for a communication system is a full power input signal.
  • the peak power of the digital source signal is assumed to be 0 dB, and the peak to average ratio is assumed to be 10 dB, the largest average value of the input power will be -10 dB .
  • the gain of the amplifiers is chosen so that the output power in watts is equal to the desired level of output power. For instance, if the desired output power is 10 watts or 40 dBm, this amount of power will be produced when the input signal power is at -10 dB.
  • the power amplifying device for a communication system comprises a third amplifier 22 for amplifying the digital source signal s (n) and outputting an amplified digital source signal to a decomposer 10 as its input signal.
  • the decomposer 10 decomposes the amplified digital source signal into a first digital component signal Sx (n) and a second digital component signal s 2 (n) .
  • a first D/A converter 11 converts the first digital component signal s (n) into a first analog signal s x (t) .
  • a second D/A converter 12 converts the second digital component signal s 2 (n) into a second analog signal s 2 (t) .
  • a modulator 13 modulates respectively the first analog signal S ⁇ (t) and the second analog signal s 2 (t) to become a first modulated signal m x (t) and a second modulated signal m 2 (t) each having a desired carrier frequency f c .
  • a first power amplifier 15 amplifies the first modulated signal ⁇ (t) to obtain a first amplified signal x x (t) .
  • a second power amplifier 16 amplifies the second modulated signal m 2 (t) to obtain a second amplified signal x 2 (t) .
  • a signal combiner 17 combines the first amplified signal x x (t) and the second amplified signal x 2 (t) to obtain an output signal x(t) to be transmitted.
  • the modulator 13 is optional . Even if the desired carrier frequency f c is zero, the power amplifying device for a communication system will work. In other words, the modulation operation does not affect any of the properties of the power amplifying device, which are equally valid for a carrier frequency of 0Hz as they are valid for a carrier frequency of 2 GHz, for example.
  • the power amplifying device for a communication system further comprises a power detection & gain factor calculation device 20.
  • the power detection & gain factor calculation device 20 detects the average power of the digital source signal s (n) , adjusts the gain factor g x of the third amplifier 22 and the gain factor g 2 of the first power amplifier 15 and the second power amplifier 16 based on the detected average power of the digital source signal s (n) .
  • the measurement of the average power of the digital source signal s (n) is used to adjust the gain factors g 1 and g 2 to make sure that the amplified digital source signal going into the decomposer 10 always has a power level of -10 dB.
  • the gain factor g x of the third amplifier 22 will be so set that the amplified digital source signal has a power level of -10 dB.
  • the gain factor g 2 of the first power amplifier 15 and the second power amplifier 16 is used to scale the average power of the output signal x(t) so that it is at the desired setting.
  • the gain factor g 2 will be set to a suitable value so that the overall gain will -be constant.
  • the power amplifying device for a communication system further comprises two reconstruction filters (not shown) , one of which is connected between the first D/A converter 11 and the modulator 13, and the other of which is connected between the second D/A converter 12 and the modulator 13. Any time that a digital to analog conversion happens, what is produced is the desired output spectrum, and images of that spectrum that keep repeating every fs .
  • the reconstruction filters are used to filter out the images that are not wanted.
  • the digital source signal s (n) could be a multi-carrier signal or a single carrier signal .
  • the modulation of the digital source signal s (n) could be anything (GSM, CDMA, OFDMA, etc)
  • One example is to examine the source signal itself, and estimate the power of the source signal, i.e., one can calculate abs(s(n) 2 ) for every input sample and then average these values over a certain averaging period. This averaging operation can be performed, for example, either with an alpha filter, or by directly summing N number of abs(s(n) 2 ) values and then dividing by N.
  • Another method is to use some information about how the signal itself was generated. For instance, if it is known that s (n) is the result of adding three signals, each with a power level of X, therefore, one can deduce that the power of s (n) is 3X. This is a very real solution in a CDMA system, since the signal s (n) is actually composed of the sum of hundreds of sequences, and we know the power of each of those sequences. This method would require different signals be sent into the power estimation module. The source signal s (n) is not needed for this method,.
  • g n is the nominal gain factor of the two power amplifiers when the source signal is at full power, i.e., if the source signal is at full power, g x will be 1 and g 2 will be g n to produce a signal on the output that is at the required power level. If the source signal is not at full power, g 2 will be equal to S/M*g n .
  • Fig.5 (a) -Fig.5 (d) show the relationship of a source signal, the intermediate signal, the out of band noise introduced due to gain imbalance and the output signal of the power amplifying device for a communication system according to the invention where the digital source signal is a weak power source signal .
  • the intermediate analog signal formed by combining the first analog signal s x (t) and the second analog signal s 2 (t) is scaled up due to the amplifying effect of the third amplifier 22. If the gain factor g x of the third amplifier is set as required, the signal going into the decomposer 10 is always at full scale.
  • the power amplifiers will always be reconstructing a full scale signal, and hence the output out of band spectral emissions will be relative to the input signal power.
  • the output signal x(t) being sent to the antenna is determined by the common gain factor g 2 of the first and the second power amplifiers 15 and 16.
  • the gain factor g 2 of the first power amplifier 15 is set to g n and the second power amplifier 16 is equal to g n
  • the output signal x(t) would be that as shown in Fig.5(c) and the SNR after the first and the second power amplifiers is still very high, as if the input signal was at full power.
  • the digital source signal does not have to be centered around zero frequency. It can be centered around an intermediate frequency (so-called IF frequency) .
  • this invention can and will be used in the field of radio communications, but it is not limited to this use.
  • This invention can be used with other transmission media such as media that carries an optical signal, or even a cable that carries an RF signal .
  • the invention will work for all modulations schemes including, but not limited to CDMA, OFDMA, FM, QAM, DQPSK, and future modulation schemes .
  • the invention will work whether the source signal s (n) is composed of a single signal, or if it is a multi-carrier signal composed of several carriers .

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Amplifiers (AREA)
  • Transmitters (AREA)

Abstract

L'invention concerne un dispositif d'amplification de puissance pour un système de communication. Il comprend un décomposeur, deux convertisseurs N/A, deux amplificateurs de puissance et un combineur de signaux. Il comprend également un autre amplificateur de puissance avant le décomposeur et un dispositif de détection de puissance et de calcul de facteurs de gain lequel mesure la puissance moyenne du signal source du dispositif d'amplification de puissance et règle les facteurs de gain des trois amplificateurs de puissance conséquemment. Avec ce dispositif d'amplification de puissance, un réseau complexe n'est pas nécessaire pour compenser le déséquilibre des amplificateurs de même qu'un dispositif de mesure complexe n'est pas nécessaire pour mesurer les performances absolues de chaque composant. Avec cette invention des câbles de puissance plus légers peuvent être utilisés, moins de batteries de secours et de dissipateurs thermiques sont nécessaires. De même, les facteurs de gain des amplificateurs peuvent être réglés par changement de leur tension d'alimentation CC. Ceci permet de réduire leur consommation d'énergie.
PCT/CN2003/000144 2003-02-25 2003-02-25 Dispositif d'amplification de puissance pour systeme de communication WO2004077662A1 (fr)

Priority Applications (3)

Application Number Priority Date Filing Date Title
AU2003213984A AU2003213984A1 (en) 2003-02-25 2003-02-25 Power amplifying device for communication system
CNB038246678A CN100474762C (zh) 2003-02-25 2003-02-25 用于通信系统的功率放大器
PCT/CN2003/000144 WO2004077662A1 (fr) 2003-02-25 2003-02-25 Dispositif d'amplification de puissance pour systeme de communication

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/CN2003/000144 WO2004077662A1 (fr) 2003-02-25 2003-02-25 Dispositif d'amplification de puissance pour systeme de communication

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WO2004077662A1 true WO2004077662A1 (fr) 2004-09-10

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AU (1) AU2003213984A1 (fr)
WO (1) WO2004077662A1 (fr)

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WO2007003703A1 (fr) * 2005-06-30 2007-01-11 Nokia Siemens Networks Oy Retard emetteur et reglage de phase
EP1881597A1 (fr) 2006-07-21 2008-01-23 MediaTek Inc. Transmetteur LINC à plusieurs niveaux
CN100434520C (zh) * 2006-03-07 2008-11-19 湖北大学 聚肽型转染试剂
WO2009123568A1 (fr) * 2008-03-31 2009-10-08 Agency For Science, Technology & Research Émetteur linéaire à haut rendement
EP2214307A1 (fr) * 2007-09-27 2010-08-04 Kyocera Corporation Circuit d'amplification de puissance et émetteur et dispositif de communication sans fil utilisant ce circuit
US7826553B2 (en) 2006-07-21 2010-11-02 Mediatek Inc. Multilevel LINC transmitter
US7957700B2 (en) 2005-06-30 2011-06-07 Nokia Corporation Transmitter delay and phase adjustment
JP2015533065A (ja) * 2012-10-30 2015-11-16 イーティーエー デバイシズ， インコーポレイテッド 伝送機アーキテクチャおよび関連方法
US10038412B2 (en) 2015-01-12 2018-07-31 Huawei Technologies Co., Ltd. Signal amplification processing method and apparatus
US10164577B2 (en) 2012-10-30 2018-12-25 Eta Devices, Inc. Linearization circuits and methods for multilevel power amplifier systems

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CN103219958B (zh) * 2013-04-27 2016-11-09 成都九洲电子信息系统股份有限公司 超高频双频段功率放大电路
CN104346594A (zh) * 2013-08-09 2015-02-11 航天信息股份有限公司 Rfid读写器的功放装置及其信号处理方法
US9813169B2 (en) * 2015-11-19 2017-11-07 Texas Instruments Incorporated Precision measurement of transmit power using loopback calibration in an RF transceiver
CN110324009A (zh) * 2019-06-20 2019-10-11 电子科技大学 一种具有滤波功能的分布式电源调制放大器

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Cited By (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2007003703A1 (fr) * 2005-06-30 2007-01-11 Nokia Siemens Networks Oy Retard emetteur et reglage de phase
US7957700B2 (en) 2005-06-30 2011-06-07 Nokia Corporation Transmitter delay and phase adjustment
CN100434520C (zh) * 2006-03-07 2008-11-19 湖北大学 聚肽型转染试剂
EP1881597A1 (fr) 2006-07-21 2008-01-23 MediaTek Inc. Transmetteur LINC à plusieurs niveaux
US7826553B2 (en) 2006-07-21 2010-11-02 Mediatek Inc. Multilevel LINC transmitter
US8463202B2 (en) 2007-09-27 2013-06-11 Kyocera Corporation Power amplifying circuit, and transmitter and wireless communication device using the same
EP2214307A1 (fr) * 2007-09-27 2010-08-04 Kyocera Corporation Circuit d'amplification de puissance et émetteur et dispositif de communication sans fil utilisant ce circuit
EP2214307A4 (fr) * 2007-09-27 2010-12-01 Kyocera Corp Circuit d'amplification de puissance et émetteur et dispositif de communication sans fil utilisant ce circuit
WO2009123568A1 (fr) * 2008-03-31 2009-10-08 Agency For Science, Technology & Research Émetteur linéaire à haut rendement
JP2015533065A (ja) * 2012-10-30 2015-11-16 イーティーエー デバイシズ， インコーポレイテッド 伝送機アーキテクチャおよび関連方法
US10038461B2 (en) 2012-10-30 2018-07-31 Eta Devices, Inc. RF amplifier having a transition shaping filter
US10164577B2 (en) 2012-10-30 2018-12-25 Eta Devices, Inc. Linearization circuits and methods for multilevel power amplifier systems
US10658981B2 (en) 2012-10-30 2020-05-19 Eta Devices, Inc. Linearization circuits and methods for multilevel power amplifier systems
US10038412B2 (en) 2015-01-12 2018-07-31 Huawei Technologies Co., Ltd. Signal amplification processing method and apparatus

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CN1695297A (zh) 2005-11-09
AU2003213984A1 (en) 2004-09-17
CN100474762C (zh) 2009-04-01

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