WO2000018000A1 - Regulateur de tension - Google Patents

Regulateur de tension Download PDF

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Publication number
WO2000018000A1
WO2000018000A1 PCT/JP1999/003211 JP9903211W WO0018000A1 WO 2000018000 A1 WO2000018000 A1 WO 2000018000A1 JP 9903211 W JP9903211 W JP 9903211W WO 0018000 A1 WO0018000 A1 WO 0018000A1
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WO
WIPO (PCT)
Prior art keywords
motor
variable
signal
voltage
iron loss
Prior art date
Application number
PCT/JP1999/003211
Other languages
English (en)
Japanese (ja)
Inventor
Toshihiro Kamata
Original Assignee
Solidway Incorporated
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Solidway Incorporated filed Critical Solidway Incorporated
Publication of WO2000018000A1 publication Critical patent/WO2000018000A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters

Definitions

  • the present invention relates to a voltage control device for the purpose of power-saving (hereinafter, referred to as energy-saving) operation of an induction motor (hereinafter, referred to as a motor).
  • energy-saving hereinafter, referred to as energy-saving
  • a motor induction motor
  • a device as shown in Fig. 7 has been conventionally proposed as an energy-saving control inverter.
  • AC power from an AC power supply 50 is converted into DC power by a converter 51, and then a pulsating component is removed by a smoothing capacitor 52.
  • This smoothed DC power is supplied to a PWM inverter 53 composed of a semiconductor switch such as a transistor or GTO.
  • the PWM receiver 53 is controlled by a pulse width modulated signal from the PWM generator 54.
  • 3 ⁇ 41 generator 54 drives PWM inverter 53 based on frequency command f and control voltage V r, converts DC input to variable voltage and variable frequency AC output, Drive at speed.
  • the PWM generator 54 includes a power calculation unit 56 and a voltage calculation unit 57 in its control unit, and the power calculation unit 56 calculates the power P from the output voltage VI and the output current I 1. Then, the voltage calculator 57 calculates Vr that maximizes the efficiency from the power P and the frequency f. ?
  • the generator 54 controls the PWM circuit 53 so that the motor 55 receives this frequency ⁇ and the optimum voltage V r. Supply.
  • the motor 55 can be operated at the maximum efficiency regardless of the supply frequency and the load.
  • Fig. 10 shows a highland circle diagram obtained from a simple equivalent circuit of a motor. This shows the current vector when the line segment OP1 is not loaded and the line segment 0P3 when the shaft is constrained.
  • the vertical axis is the same as the vector direction of the supply voltage. That is, the amount on the vertical axis is proportional to the motor supply power.
  • the radius of the circle diagram is determined by the supply voltage.
  • the motor is operated at the point P 1 at which the motor is most efficient in the conventional technology.
  • the supply voltage should be raised quickly to increase the radius of the circle diagram.In actual equipment, this is called hunting.
  • the supply voltage change has a delay time element, so it is not possible to instantaneously supply the appropriate voltage corresponding to a sudden increase in load torque, and the point beyond P1 to PM To point P2.
  • the motor slips more and eventually falls into operation at point P3.
  • a higher supply voltage is required than at point P1 due to the added load torque, the input power of the motor will be lower than P1, so the supply voltage will be lower than the supply voltage at P1. It operates to supply pressure, and energy-saving operation cannot be performed, and the motor stops stalling.
  • the minimum of the radius of the circle diagram that is, the lower limit of the supply voltage, is determined so that PM becomes larger than the input power at the time of the torque larger than the rated torque. Therefore, even at light load, the optimum supply voltage could not be supplied due to the restriction of the lower limit voltage, and the ideal energy saving effect could not be achieved.
  • the copper loss generated in the motor during operation changes in proportion to the square of the load current, and fluctuates depending on the voltage fluctuation rate. Since the voltage is inversely proportional to the frequency at the same voltage, the load current, voltage fluctuation rate, or frequency is always detected, and the iron loss and copper loss are always equalized. It was difficult to control the motive supply voltage.
  • the magnitudes of iron loss and copper loss depend on the resistance of the primary and secondary windings of the motor, the excitation conductance, the excitation susceptance, and the leakage reactance. Since it differs depending on the type, it was difficult to provide a device that can control the already installed motor so that iron loss and copper loss have the same value. In particular, in the prior art, constants such as the motor capacity must be set every time the connected motor changes.
  • the present invention has been proposed in order to solve the problems of the prior art as described above, and its purpose is to control the electric motor by changing the supply voltage.
  • the present invention eliminates the limitation of the lower limit voltage for preventing stall stop, which has been a problem in the prior art, to achieve an ideal energy saving effect, and to eliminate the constant setting required for each motor. It is characterized by the following.
  • Another object of the present invention is to use a computer such as a microcomputer to drive a motor with a simpler configuration and always matching the iron loss and the copper loss as described above. It is to provide a voltage control device. Disclosure of the invention
  • the present invention provides a variable conductance 13 and a variable susceptance 14 which are set according to the excitation conductance and the excitation susceptance of a motor, and the resistance values of a primary winding and a secondary winding of the motor. It has a variable resistor 15 that is set according to.
  • a means for calculating a copper loss by processing a signal e proportional to the fundamental wave instantaneous voltage supplied to the motor based on the variable conductance; and a signal e proportional to the fundamental wave instantaneous voltage supplied to the motor.
  • FIG. 8 shows a simplified equivalent circuit of the motor.
  • I is the primary current
  • IL is the load current
  • 10 is the exciting current
  • E is the primary voltage of the motor
  • R1 is the primary winding resistance
  • R2 is the secondary winding resistance
  • X is the leakage reactance
  • S is the motor slip
  • gO is the excitation conductance
  • bO is the excitation susceptance.
  • Iron loss is caused by the excitation conductance gO
  • copper loss is caused by the primary winding resistance and the secondary winding resistance R 1 + R 2. If the iron loss is P i, the number
  • Excitation conductance gO, excitation susceptance bO, primary winding resistance Rl, and secondary winding resistance R2 have constant values, and take different values depending on motor capacity. The ratio of each constant is almost constant regardless of the motor capacity, and general values are also known. Therefore, the iron loss can be obtained from the above equation (1).
  • the load current IL can be obtained by determining the primary current I and the excitation current I 0, and gO and bO can be obtained by measurement as described above, or a general value can be obtained. Because it is known, the exciting current I 0 can be easily obtained from the primary voltage E. As can be seen from the relationship between the vector diagrams of the respective currents in FIG. 9, the load current IL can be obtained, and the copper loss Pc can be obtained from the above equation (2).
  • the present invention compares the iron loss and the copper loss thus obtained with a comparator, A control signal is obtained and input to control means such as an inverter driven by the PWM generator, and the control means controls the supply voltage of the motor. That is, when the copper loss Pc is larger than the iron loss Pi, the voltage control signal increases, and the motor supply voltage increases accordingly. On the other hand, when the copper loss P c is smaller than the iron loss P i, the voltage control signal decreases, and accordingly, the motor supply voltage also decreases. As a result, the optimal voltage at which the copper loss and the iron loss match is supplied to the motor, and the loss of the motor is minimized, enabling energy-saving operation.
  • the copper loss P c at the point P 1 is proportional to the square of the length of the line segment P 0 P 1
  • the copper loss at the point P 2 is represented by the line segments P 0 P 2 and P 3.
  • FIG. 1 is a circuit diagram showing a first embodiment of a voltage control device according to the present invention.
  • FIG. 2 is a block diagram showing a second embodiment of the voltage control device according to the present invention.
  • FIG. 3 is a flowchart showing the first half of the operation of the voltage control device according to the second embodiment of the present invention.
  • FIG. 4 is a flowchart showing the latter half of the operation of the voltage control device according to the second embodiment of the present invention.
  • FIG. 5 is a graph showing an example of the iron loss voltage compensation table.
  • FIG. 6 is a graph showing supply voltage and loss characteristics.
  • FIG. 7 is a circuit diagram showing energy saving control of a conventional electric motor.
  • FIG. 8 is a simplified equivalent circuit diagram of an induction motor.
  • FIG. 9 is a current vector diagram of the electric motor.
  • FIG. 10 is a highland circle diagram of the electric motor. BEST MODE FOR CARRYING OUT THE INVENTION
  • FIG. 1 shows an example in which the present invention is applied to an inverter device.
  • 1 is a rectifier that converts AC power to DC power
  • 2 is a capacitor for smoothing DC
  • 3 is an inverter that switches the DC power and converts it to AC power.
  • the device 3 crosses the main circuit of the inverter device.
  • the inverter 3 is driven by the PWM generator 6, and the voltage E supplied to the motor 5 is determined by the voltage charged in the DC smoothing capacitor 2 and the signal PWM generated by the PWM generator 6.
  • the PWM generator 6 generates a PWM signal PWM determined by the frequency setting signal FRQ and the voltage setting signal VLEVE, and a signal e proportional to the instantaneous fundamental voltage supplied to the motor.
  • the motor supply voltage E is proportional to the voltage setting signal VL EVE L
  • the frequency f is proportional to the frequency setting signal F RQ. That is, when the voltage setting signal VL EVE L increases, the motor supply voltage E increases in proportion thereto, and the amplitude of the output signal e from the PWM generator 6 also increases in proportion.
  • a multiplier 7 On the output side of the voltage output signal e of the PWM generator 6, a multiplier 7 having input terminals a and b and an integrating circuit 8 are connected.
  • the voltage signal e is directly input to the input terminal b of the multiplier 7, and the voltage signal e is input to the input terminal a of the multiplier 7 via the variable conductance 13.
  • An average value circuit 9 is connected to the output side of the multiplier 7, and the output side of the average value circuit 9 is connected to the input terminal a on the iron loss side of the comparator 12.
  • the output side of the integration circuit 8 is connected to the input side of the first adder 16 via a variable susceptance 14.
  • the other input side of the first adder 16 is connected to the output side of the variable conductance 13.
  • the output of the first adder 16 is connected to the negative input terminal of the second adder.
  • the positive side input terminal of the second adder 17 is connected to a current detector 4 for detecting an output current of the inverting device 3.
  • a 2 multiplier 11 To the output side of the second adder, a 2 multiplier 11, an average value circuit 10 and a variable resistor 15 are connected in order, and the output side of the variable resistor 15 is connected to the copper loss of the comparator 12 Connected to the input terminal b on the side.
  • the AC power supplied from the AC power supply is converted into DC power by the rectifier 1, and the DC power smoothed by the smoothing capacitor 2 is supplied to the inverter 3 and converted into AC power. Is converted.
  • the inverter 3 applies a predetermined frequency f and voltage E to the motor 5 based on the frequency command FRQ and the voltage setting signal VL EVE L from the control PWM generator 6 connected thereto. Supply.
  • the voltage setting signal VLEVEL is determined such that the copper loss Pc and the iron loss Pi of the motor match.
  • the excitation conductance gO, excitation susceptance bO, and the resistance values R1 and R2 of the primary and secondary windings, which determine the copper loss Pc and iron loss Pi of the motor The value is set to a predetermined value according to the motor to which the device is to be attached.
  • general values are known for the excitation conductance gO and the excitation susceptance bO, so input these values or measure these values for the motor to be attached, and measure the values.
  • the resistance value R 1 + R 2 of the variable resistor 15 may be obtained by actually measuring the motor to which the present device is attached, or may be set according to the design value of the motor.
  • the voltage signal e is extracted from the PWM generator 6 in a state where the excitation conductance gO, the excitation susceptance bO, and the winding resistance R1 + R2 are set according to the motor to which the device is mounted. Then, the b terminal of the multiplier 7, the variable conductance 13 and the integrating circuit 8 are applied. Further, the output current (motor current) of the reverse converter 3 detected by the current detector 4 is applied to the plus terminal of the second adder. Then, as shown in FIG. 1, i 0, i gO, i bO, i, and i L flow through each part of the apparatus, and these are I 0, I gO, I bO, I, This is the instantaneous value of IL.
  • the set point of the variable conductance 13 is set to g Assuming that it is a constant of 0, igO is obtained by dividing the signal e by the variable conductance 13. Then, this igO is input to the b terminal of the multiplier 7 and is multiplied by the signal e also input to the a terminal to obtain e ⁇ igO.
  • ibO is a current flowing through the inductance component (variable susceptance 14), and the phase of the signal e is delayed by 90 °. Therefore, first, the phase of the signal e is delayed by 90 °.
  • i bO is obtained as a result of voltage division by the variable susceptance 14.
  • the first adder 16 adds i g0 from the variable conductance 13 and i bO from the variable susceptance 14 to obtain i 0.
  • the second adder 17 adds the instantaneous value i of the output current I detected by the current detector 4 and i ⁇ 0 obtained by the first adder 16 to obtain the instantaneous value i L of IL. .
  • (i L) 2 is obtained by the squaring multiplier 11 based on the i L obtained as described above, and the (i L) 2 AVE That is, (IL) ⁇ is obtained.
  • the setting point of the variable resistor 15 is regarded as a constant of R 1 + R 2, from (IL) 2 to (IL) 2 (R 1 + R 2), that is, the copper loss P c is obtained.
  • the calculated copper loss Pc and iron loss Pi are compared by the comparator 12 to obtain the voltage adjustment level VLEVEL and input to the PWM generator 6. That is, when P c> P i, the voltage adjustment level V L EV E L increases, and the motor supply voltage increases. Conversely, when Pc ⁇ Pi, the motor supply voltage decreases.
  • the comparator 12 is provided with a delay element 12a for stabilizing the operation.
  • the means for controlling the motor supply voltage according to the comparison result of the comparator is an inverter device, and the inverter device has the inverter 3 controlled by the PWM generator.
  • the control of the supply voltage and frequency to the motor can be easily performed, and there is an advantage of high practicality.
  • the inverter device of the present invention in addition to a device that inputs AC power and outputs AC power, a device that inputs DC power and outputs AC power can also be used. Further, the present invention can be applied not only to the PWM inverter but also to a voltage control device using another inverter or a motor control device using a power supply voltage control method without using an inverter.
  • FIG. 2 shows a second embodiment of the present invention.
  • iron loss and loss are reduced by performing data processing using a microcomputer or the like instead of the elements such as the integration circuit, adder, and multiplier used in the first embodiment. It controls the PWM inverter to be the same.
  • each function of the embodiment is implemented by a predetermined procedure (program) controlling the computer.
  • Each “means” or “unit” in the present specification is a conceptual one corresponding to each function of the embodiment, and does not necessarily correspond one-to-one to a specific software / software routine.
  • the same hardware element may constitute different parts in some cases.
  • a computer may be one part when executing one instruction and another part when executing another instruction.
  • one part may be realized by only one instruction, or may be realized by many instructions. Therefore, in this specification, the embodiments will be described below assuming virtual circuit blocks (parts) having the functions of the embodiments.
  • each step of each procedure in the present embodiment may be executed in a different order, may be executed at the same time, or may be executed in a different order, as long as it does not violate its nature.
  • the present invention when the present invention is realized as software for a computer, the software is recorded on a recording medium such as a magnetic or optical medium, and is stored in an individual design.
  • a recording medium such as a magnetic or optical medium
  • One of the embodiments of the present invention is that reading by a person and execution by the own computer are also possible.
  • the microcomputer includes a CPU 21, a main memory 22, a storage device such as a RAM and a ROM 23, a keyboard for inputting data and commands, an input device 24 such as a mouse and a touch sensor 24, and an output device such as a display or a printer. It has an I / O section 26 for exchanging data with hardware such as a device 25, a PWM generator 6, and an inverse converter 3, and the optimum voltage calculation means 30 is implemented on this microcomputer. It is implemented as a program to be executed.
  • the optimum voltage calculating means 30 compares the copper loss value P c calculated by these with the copper loss calculating section 31 and the iron loss calculating section 32 and the iron loss value P i, and outputs the result to the PWM generator 6 according to the result.
  • a loss comparison unit 33 that outputs the voltage setting signal VLE VEL is provided.
  • the copper loss calculation unit 31 includes a calculation unit 31 a of the instantaneous value current i L, a square integration unit 31 b of the instantaneous value current i L, an averaging unit 31 c, and a resistance multiplication unit 31 d. Have.
  • the iron loss calculating unit 32 includes an instantaneous power calculation unit 32a for iron loss, an instantaneous power integrating unit 32b, an average processing unit 32c, and a data reference unit 32d. Further, the optimum voltage calculating means 30 includes a sampling count section 34 for determining that the copper loss calculating section 31 and the iron loss calculating section 32 have calculated and integrated the instantaneous value of one AC cycle. ing.
  • the storage device 23 stores the excitation conductance gO and the excitation susceptance b0 whose values are known in advance by a general motor or the like, and fault compensation data.
  • the iron loss compensation data is a table showing the change of the iron loss Pi due to the motor supply voltage E and the supply voltage, and the force proportional to the 1.6th power to the 1.8th power of the voltage E It is a table with a table.
  • FIG. 5 is a graph showing an example of this table, and is a curve obtained by taking an average of 1.6 to 1.8 power and setting it to 1.7 power.
  • the voltage and compensation value data can be stored in the ROM of the computer or can be created by a broken line circuit of the analog circuit.
  • the resistance value R 1 + R 2 of the primary winding and the secondary winding of the motor is input from the input device 24 and stored in the storage device 23.
  • the excitation conductance gO and the excitation susceptance bO in addition to previously storing general values in the storage device 23 composed of a ROM or the like, values specific to the motor to which the present device is attached are also input to the input device. You can also enter from 24.
  • the microcomputer inputs the instantaneous voltage i supplied to the motor 5 through, for example, the I / O unit 26 as, for example, the output of the PWM generator 6, and sets this as a voltage control signal e.
  • Step 2 Read voltage control signal e '
  • the instantaneous value current i L calculator 31a in FIG. 2 executes the copper loss calculation steps of Steps 3 to 7.
  • the excitation conductance gO and the excitation susceptance bO whose values are known in advance by a general motor or the like are read from the storage device 23.
  • These values are the instantaneous value i gO of the current flowing through the excitation conductance gO and the instantaneous value i bO of the current flowing through the excitation susceptance bO.
  • Step 5 Copper loss calculation step
  • the instantaneous values ig O and ib O of these currents are added to determine the instantaneous value i 0 of the exciting current.
  • the instantaneous value i of the motor current is detected by the current detector 4, and i ⁇ i 0 is calculated based on the instantaneous value i 0 of the exciting current, and is set as the instantaneous value current i.
  • P i A is the integrated value of the instantaneous power of iron loss, and is data for the purpose of calculating iron loss P i by averaging later when one cycle of AC is completed.
  • the square integrating unit 3 1 b of the instantaneous value current on the basis of the instantaneous value current i L obtained in step 7 to calculate the (i L) 2, IL "is added to 1 A.
  • IA instantaneous value collector Is the integrated value of the square of the flow i L, and is averaged at the end of one AC cycle later (
  • the sampling count unit 34 performs the determination of whether or not sampling for one cycle of AC has been completed (determination of YES or N0 in step 10) and the counting of the number of samplings N. If has not been completed, the process returns to step 1 to repeat the process of calculating the instantaneous power P i A of the iron loss and the square value (i L) ⁇ of the instantaneous value current and adding them to the integrated value. On the other hand, after one cycle of the AC is completed, the process proceeds to step 12 shown in FIG.
  • the averaging unit 32c of the iron loss calculation unit 32 averaged the integrated value of the instantaneous power of the iron loss by the number of counts! 5 Calculate i A ZN.
  • the actual iron loss depends on the supply voltage of the motor. Since it changes, the average value of the instantaneous power of iron loss obtained by the above calculation cannot be used as it is. Therefore, in the present embodiment, the iron loss compensation data corresponding to the motor supply voltage E stored in the storage device 23 is read by the data reference unit 32d, and the compensation data is multiplied by P i AZN. Data P i is obtained by approximating P i AZN to the iron loss of the actual motor.
  • the averaging processing unit 3 1 c copper loss calculation unit 31 calculates the IL 2 A resulting et a in the manner described above by dividing by the sampling count Bok number N, calculates the IL 2 A / N Get the averaged (IL) 2 .
  • the loss comparison unit 23 calculates the copper loss Pc—the iron loss Pi, and if the value is positive, outputs a signal for increasing the output voltage level of the voltage setting signal VLEVEL to the PWM generator 6, If the value is negative, a signal to decrease the output voltage level of the voltage setting signal VLELEL is output.
  • the rate of rise and fall of the output voltage level may be a fixed rate or a function of Pc-Pi.
  • the motor supply voltage by the inverter 3 can be controlled to the optimum voltage by the PWM generator 6.
  • Table 1 shows the measured numbers of commercially available motors.
  • each constant is expressed as a ratio when R 1 + R 2 is set to 1.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)

Abstract

La présente invention concerne un régulateur de tension dont la conductance variable (13) et la susceptance variable sont déterminées en fonction de la conductance à l'excitation et de la susceptance à l'excitation d'un moteur électrique, et dont la résistance variable (15) est déterminée en fonction de la résistance du primaire et du secondaire du moteur électrique. Le régulateur est pourvu d'organes permettant de calculer la perte dans le cuivre par traitement d'un signal (e) proportionnel à la tension de l'onde fondamentale fournir au moteur électrique sur la base de la conductance variable, et d'organes permettant de calculer la perte dans le fer par traitement du signal (e) proportionnel à la tension instantanée (i) de l'intensité moteur sur la base de la conductance variable, de la susceptance variable, et de la résistance variable. On compare la perte dans le cuivre avec la perte dans le fer puis on fait une régulation de la tension d'alimentation du moteur électrique de façon que la perte dans le cuivre vienne égaler la perte dans le fer. Cela permet un fonctionnement du moteur électrique, économe en énergie.
PCT/JP1999/003211 1998-09-18 1999-06-16 Regulateur de tension WO2000018000A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP10/265345 1998-09-18
JP10265345A JP3043717B2 (ja) 1998-09-18 1998-09-18 電圧制御装置

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WO2000018000A1 true WO2000018000A1 (fr) 2000-03-30

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Cited By (1)

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Publication number Priority date Publication date Assignee Title
CN107276491A (zh) * 2017-06-19 2017-10-20 黄南虎 一种基于三相异步电机的电压控制装置

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Publication number Priority date Publication date Assignee Title
JP5884160B2 (ja) * 2011-12-07 2016-03-15 Ｊｆｅスチール株式会社 ハイブリッド自動車用モータの性能解析方法

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JPH06261597A (ja) * 1993-03-08 1994-09-16 Alex Denshi Kogyo Kk 誘導電動機用電力制御装置
JPH09233879A (ja) * 1996-02-20 1997-09-05 Hiroshi Ko モ−タ−の省電力制御法
JPH09262000A (ja) * 1996-03-26 1997-10-03 Mitsubishi Electric Corp 誘導電動機の制御装置

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH06261597A (ja) * 1993-03-08 1994-09-16 Alex Denshi Kogyo Kk 誘導電動機用電力制御装置
JPH09233879A (ja) * 1996-02-20 1997-09-05 Hiroshi Ko モ−タ−の省電力制御法
JPH09262000A (ja) * 1996-03-26 1997-10-03 Mitsubishi Electric Corp 誘導電動機の制御装置

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Title
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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107276491A (zh) * 2017-06-19 2017-10-20 黄南虎 一种基于三相异步电机的电压控制装置

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