WO1990004895A2 - Procede de codage d'informations - Google Patents

Procede de codage d'informations Download PDF

Info

Publication number
WO1990004895A2
WO1990004895A2 PCT/EP1989/001244 EP8901244W WO9004895A2 WO 1990004895 A2 WO1990004895 A2 WO 1990004895A2 EP 8901244 W EP8901244 W EP 8901244W WO 9004895 A2 WO9004895 A2 WO 9004895A2
Authority
WO
WIPO (PCT)
Prior art keywords
code
signal
pulses
phase
signals
Prior art date
Application number
PCT/EP1989/001244
Other languages
German (de)
English (en)
Other versions
WO1990004895A3 (fr
Inventor
Josef Dirr
Original Assignee
Josef Dirr
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Priority claimed from DE19883835630 external-priority patent/DE3835630A1/de
Application filed by Josef Dirr filed Critical Josef Dirr
Publication of WO1990004895A2 publication Critical patent/WO1990004895A2/fr
Publication of WO1990004895A3 publication Critical patent/WO1990004895A3/fr

Links

Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N11/00—Colour television systems
    • H04N11/04—Colour television systems using pulse code modulation
    • H04N11/042—Codec means
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J3/00—Time-division multiplex systems
    • H04J3/16—Time-division multiplex systems in which the time allocation to individual channels within a transmission cycle is variable, e.g. to accommodate varying complexity of signals, to vary number of channels transmitted
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J3/00—Time-division multiplex systems
    • H04J3/16—Time-division multiplex systems in which the time allocation to individual channels within a transmission cycle is variable, e.g. to accommodate varying complexity of signals, to vary number of channels transmitted
    • H04J3/1676—Time-division multiplex with pulse-position, pulse-interval, or pulse-width modulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
    • H04L27/24—Half-wave signalling systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N7/00—Television systems
    • H04N7/12—Systems in which the television signal is transmitted via one channel or a plurality of parallel channels, the bandwidth of each channel being less than the bandwidth of the television signal

Definitions

  • the present invention relates to a method for coding information.
  • Et al it shows how to achieve digital and / or analog coding of information from one, two or more channels and / or a frequency or bandwidth reduction and / or an increase in transmission security.
  • frequency and time-division multiplexing methods such as e.g. the carrier frequency technology and the pulse code modulation are known.
  • a disadvantage of these methods is that they require large bandwidths and a lot of effort.
  • the object of the present invention is to transmit the information of one, two or more channels with less bandwidth and to transmit the information of two or more channels over a channel with less bandwidth than would be required for the sum of the individual channels.
  • This is done by synchronously or Code elements of the different channels arranged in quasi-synchronous order are to be arranged in parallel, and all are combined and transmitted to form one code word.
  • This is done by e.g. the PAM pulses in PDM, PPM and PFM pulses in sinusoidal half periods.
  • Period impulses or Code elements are converted that are sent in an uninterrupted sequence of positive and negative half-periods.
  • the half period or Period duration is a measure of the PDM-PPM and PFM impulses.
  • the invention can e.g. are used to combine telex, teletex, fax, digital voice data channels.
  • the invention can also be used to advantage in the case of shared connections and selector switches.
  • the invention shows possibilities of advantageous coding of new television techniques to improve C-MAC, D-MAC, D2-MAC etc. Furthermore, it can also be used in the further development of the HDTV method. All of these new television methods are very limited in their possibilities due to a lack of bandwidth. Furthermore, the invention discloses an advantageous phase coding of the color tone in television. It is not the phase shift which is coded in the alternating current and which is a measure of the hue that is transmitted, but rather the phase shift of the sample values which is subsequently transmitted into the period of the coding alternating current, the amplitude encoding the saturation vector.
  • the invention shows applications for duplex traffic with an alternating current of an equenzrequency. This is based on the principle of adding two alternating currents that are 90 degrees out of phase, in which the amplitudes of the half-waves represent the information and then do not cancel each other out in oncoming traffic.
  • applications for double quadrature amplitude modulation are shown, in which the 4 encoding alternating currents are summed up twice and which have a phase position of 0.90, 90.180 degrees and a phase position of 45 and 135 degrees with the second summation.
  • patents and published documents also apply as prior art: patents US 4,794,621, 4,675,721, 4,731,798 Canada 1214277, European laid-open documents 0110427, 0197529, 0239959, 0284019, German disclosures DE 3629706.2, 3514664.8, 3719670.7, 3802088.2, 3805263.6.
  • FIG. 10,11 and 13 representation of a double QAM and vector diagram of a higher-quality coding
  • FIG. 14 Vector diagram of a double QAM
  • Fig. 15 Overview for the generation of phase and amplitude stages
  • FIG. 22,23 Overview of a television transmitter and receiver Fig. 25, 26, 27 duplex traffic via lines and radio with only one alternating current with phase adjustment
  • Fig. 68,69 A phase encoding for color television signals
  • Fig.72 principle arrangement for the transmission of television signals, phase-coded.
  • Fig. 82 Circuit diagram for the accommodation of an information channel between 2 television channels
  • Rectangular pulses with a frequency of 1 MHz are switched on on the transmitting side S. Is, as shown in Fig.3c, in the transmission path
  • the frequency sequence of the alternating current decreases or increases in the case of phase jumps, the frequency change corresponds to a phase jump.
  • FIG. 2 represents a ⁇ phase keying of a conventional type. This shows that with every phase change there is a frequency change, but not in a continuous manner. It is therefore difficult to determine the size of the phase jump from the period on the receiving side.
  • each phase jump can be broken down into stages. This is shown schematically in FIG. In / this is T / 2 the half period of a pulse and corresponds to 180 °. This angle is divided into 36 steps of 5 degrees each. Should a phase jump of 40 degrees occurs, the half period T / 2 is shortened 4 times by 5 degrees and of course the other half period as well. The half period compared to the reference pulse is then T1 / 2. After the phase jump you can either leave this frequency or switch back to the frequency T / 2 by providing a phase jump of 5 degrees in the opposite direction. Compared to the reference phase, there would still be a phase shift of 30 degrees. 6, the times of the reference phase and 4 times the periods of the periods shortened by 2x5 degrees are shown 4 times. A comparison after the 4th period shows the difference of 40 degrees compared to the reference phase.
  • the periodendans are subdivided into 72 levels, namely with phase jump levels of 5 degrees.
  • 72x10 720 measuring pulses for the period and 360 measuring pulses for the half-period.
  • the second half period is then controlled via the encoder Cod. If phase jump steps of 5 degrees are provided, 350 measuring pulses are required for the half-period if the change is to be leading and 370 for a lagging phase change.
  • Counter Z in FIG. 7 must therefore have at least 370 outputs.
  • the mass pulse frequency therefore depends on the coding frequency.
  • the control alternating current for the measuring pulses is generated in the oscillator Osc. You can use it to control the counter directly via gate G1, or you can also generate pulses by means of a Schmitt trigger or another circuit and then switch counter Z with these pulses. You can also change the pulse duration by changing the oscillator frequency.
  • the output Z2 on the counter Z is assumed to mark 370 measuring pulses, ie the lagging phase shift, then the encoder
  • Gate G2 placed that then when reaching the counter output Z 2, then z. the same potential at the other input of G2, the potential at the output of G2 changes, e.g. from h to 1.
  • this has the result that positive potential + is applied to output J.
  • the Codie rer Cod is connected to the electronic relay ER.
  • connection A controls the ER so that output minus potential - is applied to output J.
  • Bipolar square-wave pulses can therefore be taken from the output of ER.
  • the counter Z is switched 10 times to Z2.
  • the counter is switched back via gate G4, R. It is possible to set the pulse duration, the number of stages and the size of the stages by changing the number of outputs on counter Z and / or by changing the oscillator frequency These variants are controlled via the encoder Cod.
  • the oscillation frequency can be switched via fA, the number of stages and, if necessary, the phase angle change and the stage size and the amplitudes of the rectangular pulses J via A via connections g2, g3,. In the example, 2 sizes + / (A) +, - / (A) - are provided.
  • the rectangular pulses J are then connected to a low-pass filter analogous to FIG. 3 and given via a transformer U, for example on the transmission path, possibly with the interposition of a filter Fi.
  • Quadrature amplitude modulation requires AC currents that are 90 degrees out of phase with each other.
  • 8 shows a maintenance principle for generating such phase-shifted alternating currents of the same frequency.
  • the counter Z is controlled by an alternating current which is generated in the oscillator Osz and is guided via the gate G, at the other input of which there is a starting potential B.
  • 4 square-wave pulses are to be generated which act against one another If the counter Z has 100 outputs, then at 25.50., 75. and
  • Rectangular pulses are generated. There are still means in the ER relays that always reverse the potential in the case of bipolar rectangular pulses and remove the potential in the case of unipolar rectangular pulses during a run.
  • the rectangular pulses are then designated J in FIG. sent via the filters Fi1 to Fi4.
  • the resulting alternating current has a phase shift of 90 degrees compared to that generated by the next output.
  • the outputs can also be switched by 90
  • a filter FiO is also connected to the electronic relay ER1, e.g. only passes the 3rd harmonic of the square pulse, so that here you get 3 times the frequency of the square pulses. The phase shift is then transferred to the 3rd harmonic.
  • Fig.7 you can also generate different amplitude levels at the same time. Only 2 are identified in the circuit.
  • FIG. 9 another possibility is to generate different amplitude levels.
  • the alternating current generated, for example, in FIG. 7 is fed to a limiter in which the control pulses are generated.
  • the characteristic states are via the connection code fed, which make a switch to the amplitude size determined by the code and that in the encoder Cod.
  • the switch to a different amplitude size always takes place during the Hull passage.
  • the magnitude of the amplitudes is determined by the resistors R1 to R4, which are arranged in AC circuits.
  • Electronic relays I to IVes which are controlled by the encoder Cod, switch on the various resistors in the AC circuits. At output A you get 4 different amplitudes.
  • the two characteristic states of the two alternating currents are designated u1 / uo and v1 / vo. If both are added together, the four sum vectors I, IV and II, III are obtained. You can see that vectors II and III are no longer on the 45 degree line. This makes evaluation a little more difficult.
  • 4 options are sufficient, all of which are at 45 degrees. Dinie can lay, designated in Fig.11 with (ll) and (IIl). The four possibilities are shown in FIG. 13, 00, 11, 10, 01. If all 4 possibilities are on the 45 degree vector, as shown in Fig. 11, they can be coded by 4 different large amplitudes, ie with a sinusoidal alternating current. Such a possibility is shown in FIG.
  • a multi-value quaternary code such as the 4 PSK or 4 QAM is sufficient. These codes are spread over a period.
  • the positive and negative half-wave are of equal size, it is then the over a DC current freedom.
  • the poositive and negative half-wave can be used as an additional criterion. You can then distribute the 4 amplitude characteristics, 2 on the positive and 2 on the negative half-wave. These can have the same size, for example in Fig. 11, I + IV
  • the present invention shows a further possibility of reducing the frequency, in particular binary-coded information.
  • a channel K is recorded with a binary code 1, 0,1,1, ... If the frequency of the channel is to be reduced to 2 channels with half the frequency, then 2 serial binary values of the channel must be arranged.
  • K can be distributed in parallel to channels Kv1 and Kv2, e.g. the 4 values 1, 0.1, 1 of the channel K, the value 1 on Kv1, the value 0 on Kv2, the value 1 again
  • a total alternating current and simple coding alternating current can also be added, provided that a 90 degree phase shift is required. This creates 8 possible combinations.
  • FIG. 1 Kv1, Kv2, Kv3, Kv4.
  • 16 combinations are necessary.
  • a period is required for coding in each case if phase shifts are provided according to the present invention.
  • the coding is carried out by 30 degree phase differences and by 3 and 4 amplitude levels. If you still want greater security, you can still divide the 4 amplitude levels BPh. Steps can still be accommodated on the zero line.
  • the predetermined coding point is then determined in the encoder for the respective combination and transmitted to the phase and amplitude of the coding alternating current.
  • the phase is defined in FIG. 7, if necessary, one can also use this to set the Am encode plitude, and in Figure 9 you can then encode the required amplitudes. The overview for this is shown in FIG.
  • the coding point is determined based on the combination of four.
  • the phase encoder generates the half waves. Periods with the appropriate phase and the amplitude encoder generates the associated amplitudes.
  • a phase encoder can look analogous to Figure 7 and an amplitude encoder analogous to Figure 9.
  • a phase jump always means a change in the period. This change, i.e.
  • any phase can be maintained with the circuit of FIG , d. H. maintain the frequency that arose during the phase change.
  • the phase changes are always made in the present case at the zero crossing.
  • a reference phase BPh can be seen in FIG. 16, from which a phase shift is carried out 2x30 degrees ahead and behind.
  • FIG. 16 shows a generation of the phase jumps of FIG. 16 according to the principle of FIG. 7.
  • the angle of 360 degrees is characterized by 3600 pulses. If there is only an amplitude change with the reference phase, the counter is always from 0 switched through to 360 degrees. The control takes place via the encoder code, which was already described in Fig. 7. The change in amplitude takes place as shown in FIG. 7 or in FIG. 9. If the phase jump Ph1 is to take place in FIG. 16, then switching to the output 195 has to be carried out every half cycle if a DC current freedom is required. A reference phase is not necessary for the evaluation because, as long as there is no further phase change, the clear phase is determined by the period.
  • the period is 330 degrees, ie there is always a changeover at the output 165 always related to the period. If, for example, the phase shift was related to the half-period in the latter case, a switch-back would have to take place at output 150. Other methods of generating phase jumps can be used exactly as well.
  • phase jumps are evaluated by measuring the period durations by means of an excessive control speed of counter elements, e.g. in European patent application 86104693.6.
  • a reference phase is required for each evaluation of FIG. 14.
  • the amplitude points 1 to 4 are immediately on the reference phase, while the other 12 coding points are arranged to lead and lag the reference phase.
  • the signals are assumed to be those of a television system.
  • the reference phase is then determined during the blanking time and control signals are simultaneously transmitted. Only the amplitude values on the reference phase are used. From the transmission path ÜW, the signals are fed to the input set EST (Fig. 12). Once they go to a delimiter B and once to a code evaluation CA. In the limiter, the positive and negative half-waves are converted to Jp and Jn pulses. In the comparison device VE, the phase of the
  • FIG. 12a shows the leading and the reference phase pulse Jv, Jn, JB, which are compared with the reference phase pulse JBn determined from a coding.
  • the 3 possible phase values leading or reference phase are given for code evaluation.
  • the amplitude values are determined in this and, in conjunction with the leading or reference phase, the coding points are then determined and transmitted via S for further use.
  • the coding of the reference phase in the blanking time can, for example, be such that 4 times the point 2 and 4 times the point 4 are sent on the reference phase.
  • the evaluation of these takes place in the reference phase evaluation BA. From this a reference phase pulse JBn is then given to the comparison device.
  • FIG. 5 channels K1 to K5 are intended to be code-multiplexed: Way will be transferred.
  • Way will be transferred.
  • binary coded information of these 5 channels. is first stored in memory Sp.
  • Fig. 20 e.g. the steps of the binary characters are shown and already synchronized.
  • To encode are 5 steps arranged in parallel respectively.
  • the steps of S1 are 1-1-0-1-0. 5 bits are required for coding these 64 combinations.
  • these are coded with the amplitudes of the half-waves of an alternating current with the characteristic states of large and small amplitude values and with a leading and a lagging phase jump of 36 degrees, as shown in FIG. 19.
  • the binary values are fed from the memory Sp in FIG. 18 to the encoder Cod and are converted into a corresponding code in the latter.
  • the corresponding standing steps are assigned to the channels again according to the code.
  • FIG. 21 shows a further application of the invention for the coding and transmission of the signals in color television.
  • the luminance signal is tapped at 6 MHz.
  • This principle has already been disclosed in published patent application P 32 23 312.
  • the colors red and blue should each be picked up with 1.2 Mnz, ie each red and blue tap hits 5 luminance taps.
  • the luminance taps are designated l, ll, III, lV, V. These samples are coded with 8 bits, in the example binary coded. With tap III, the taps for red and blue must also be made.
  • the red and blue samples are binary coded with 6 bits in the example.
  • the code for the color samples red and blue is sent at the same time.
  • Fig.21a are the binary codes of all signals to be transmitted are recorded.
  • the 8 bits 1-8 of the luminance samples are arranged in parallel.
  • the sound and other signals and the 6 bits of the blue signal are then arranged in series under 9.10 digital sound and other signals T + So, the 6 bits of the red signal and again the sound and other signals under 11.12.
  • T + So the 6 bits of the red signal and again the sound and other signals under 11.12.
  • the control element StO controls the TV camera FK also supplies the other control signals such as blanking and synchronization signals A + S.
  • the red-green and blue signals are fed to the Y-matrix YM and red and blue at the same time to the color processing FA.
  • a capacitor K is provided which taps the luminance signal Y, the color signals r + b1 and the sound and other signals .
  • a criterion for color processing is given via connection 3a. In this tap, the red and blue signals are tapped and both values are stored in capacitors C1 and C2.
  • the FA is also fed a Y value from the Y matrix which is present at the third tap, so that the color difference signals ry and by er are obtained at tap 6a and 6b holds. -You can also only tap the color separation signals.
  • the sound and other signals are fed via 6c and 6d to the concentrator via the TSo module. All values are fed from the concentrator to a memory Sp. From the memory, the signals are fed to an analog / digital converter in a timely manner, for example as described in Fig. 21a. This is encoded in accordance with Fig. 21b.
  • a switchover to the concentrator K1 takes place via U.
  • the code word can be sent a few times with only zeros.
  • Other signals So can also be sent during the blanking time.
  • the beginning of a line can also be marked with a null code. While the line is through the sequence and the number of half-waves given a synchronization. In the present code, a nominal frequency of 15 MHz is required. If you only want to use an amplitude code, 2 alternating currents with 18 MHz each are required, which could then be phase-shifted by 90 degrees and transmitted together. It is only a question of economy and safety which method is used here. In the example, the leading or lagging phase jump is determined by the period, so no reference phase is then required. Of course, multistage amplitude codes and / or phase codes can be used to reduce the frequency.
  • the PAM signal can be applied to the T input, which is then tapped off frequently within the 8 kHz time.
  • tap 6c / 6d A partial overview of a television receiver is shown in FIG. Via the HF oscillator and mixer and the
  • Amplifier V the signals are fed to the demodulator DM.
  • the signals as shown in FIG. 21b are recovered and fed to the decoder DC.
  • the color signals are passed on in the sequence of the matrix Ma.
  • the Y signal is also connected to this.
  • the color difference signals RY.GY and BY are obtained, which, like UY, are sent to the television sets.
  • the D ecoder DC then also supplies the blanking and synchronization signals AS, the sound and other signals. 24 shows an example in which the code for code multiplexing is obtained from several alternating currents.
  • the characteristics to be transmitted consist of rectangular pulses with a frequency of 1000 Hz, as shown in FIG. 24b.
  • each channel can be supplied with multiple channels of low bit frequency in a time-division manner.
  • the same number of bits could be achieved in exactly the same way with two alternating currents at 2000 Hz and another two alternating currents at 3000 Hz, each of which would have to be 90 degrees out of phase with respect to one another so that they could be added during transmission.
  • duplex operation can be carried out with the same alternating current.
  • the countercoding alternating current is 90 degrees out of phase.
  • the code can be digital, a binary code according to the patent DE 30 10 938 or else analog according to the Canadian patent 1 214 277. With half-waves as code elements, the frequency is 32 KHz for digital coding and 4 KHZ for analog coding.
  • S1 is the microphone and E2 is the handset of one participant and S2 and E1 of the other participant.
  • S1 there is still an encoder in which the coding alternating current is obtained from the speech.
  • the coding alternating current goes from S1 via a fork G, the connection resp.
  • Connection line RL to fork G of the opposite party and to handset E1.
  • the coding alternating current from S1 is the synchronizing alternating current. From E1 this becomes branched off to S2 via a phase shifter at 90 degrees, in which it may be amplified. If S2 speaks, a coding alternating current that is 90 degrees out of phase is sent via G, RL, G to E2, decoded there and transmitted to the listener as speech. If, for example, there is a short spoken voice, an addition alternating current arises on the transmission path RL. An extinction is not caused. This principle can also be provided for duplex traffic in data transmission. Further related examples are disclosed in laid-open specification 3802088.
  • the transmission alternating current is also provided here as a coding alternating current. Pre-stage modulation is advantageously used.
  • the transmission alternating current is generated in the oscillator 0sz1.
  • the basic signal is converted into an alternating current digital code in the Amalog digital converter A1 / D1. It is even easier to provide an arrangement according to FIG. 7 as an oscillator and encoder.
  • the electronic pelais is then controlled by the encoder in such a way that large and small rectangular pulses are present at the output J, which are then in the
  • Low pass TP can be formed into a sinusoidal alternating current.
  • the encoding alternating current then reaches the output stage ⁇ and the transmitting antenna via amplifiers (not shown).
  • a branch circuit can also be provided in the output stage by phase-shifting the harmonics by 180 degrees, which are then fed back to the main current circuit for compensation.
  • the useful signals are fed to an amplifier V via a fixed tuning circuit and then switched on to the digital-to-analog converter D2 / A2.
  • the analog signal is! Damn forwarded for example via a mediation.
  • the alternating transmission current is also branched off to a phase shifter of 90 degrees Ph and then switched on to the oscillator Osz2. The oscillator is synchronized with this.
  • the transmitter is then operated in the opposite direction via the converter A3 / D3, the amplifier (not shown) and the output amplifier E.
  • Receiver E1 is held exactly like receiver E2, only the phase shifter is not required.
  • a phase shifter based on the principle of FIG. 7 is shown in FIG. 27. This also provides compensation for small frequency fluctuations.
  • a counter Z is provided with 1000 outputs. During a half wave of the alternating transmission current, the counter runs through these 1000 outputs.
  • the control pulses Js are generated in an oscillator, not shown. With a 90 degree phase shift, a half-wave encounters a phase shift of 45 degrees, which corresponds to 250 outputs.
  • the transmission alternating current half-waves coming from the amplifier V are fed to a limiter, so that rectangular pulses Jp and Jn are produced at the output of the same. These pulses are connected to the control element St. The control pulses Js and the start indicator Be are also applied to this. The control element is switched so that only whole Jp resp. Jn impulses take effect on the counter. If the counter has reached the output 1000 during a pulse Jp, the gate Gll comes into the working position. A Jn pulse is connected to the gate G12 and, after the end of the Jp pulse, the potential is briefly switched on by the delay of the monostable element mG4.
  • G12 takes effect and applies potential to one output of G13, 1 potential has already been applied from Gll to the other input of G13.
  • Such potential is also applied to the gates G8, G9 and G10 that, in cooperation with the assigned outputs 1000, 999, 1001, they control one of the monostable elements mGl, mG2 or mG3. Since the Jp pulse controlled the counter up to 1000, the gates G9 and mG2 now took effect. If the counter is now controlled with the next Jn pulse on the output 250, then the gate G6 becomes effective, which controls the electronic relay ER, which generates a rectangular pulse according to FIG. 7, which is formed into a half-wave in the low pass. For the Jn pulse, the gates G15 G14 and the monostable element mG5 are arranged for the output marking. The monostable element mG2 holds e.g. to the exit 260.
  • G6 then returns to the starting position.
  • the electronic relay remains until the next marking of the output 250 in the this position. If only frequency 999 is reached due to a frequency fluctuation, then gate G8 is marked instead of G9 and mG1 and G5 are activated when output 249 is reached. If output 1001 is reached, G10 and mG3 are activated and gate G7 when output 251 is reached. Such frequency fluctuations are also passed on to the 90 degree phase-shifted alternating current.
  • the control element is shown in detail in FIG. 27a.
  • the pulses Jn and also the start signal are connected to the gate G3. If both are present, G3 takes effect and brings the bistable member bG into the working position, which now applies working potential to the gate G1. Only now can the Jp pulse take effect.
  • the control pulses Js now reach the counter via the gate G2, which is only a potential reversal gate. The other processes on the counter have already been described.
  • the negative half-wave can either be generated by the Jn pulse, or the passage of the positive half-wave is repeated, the respectively marked outputs being stored.
  • the code used in the invention can. preferably be an amplitude and / or phase code, e.g. such is shown in Fig. 16. With a pure amplitude code you can also use 2 alternating code currents; Provide frequency, one of which is then shifted in phase by 90 degrees during the transmission and is subsequently added to the other.
  • FIG. 28 shows 5 alternating coding currents with a binary code, the characteristic states being a large and a small amplitude value of the respective half-wave.
  • the frequencies are 8, 12, 16, 20 and 24 kHz.
  • each tap is then converted into an 8-bit code in the analog / digital converter A / D and is then, as shown in FIG. 21a, sent with the following 5 luminance code words.
  • Fig. 21a e.g. with 1 / 9,10,11,12 and V / 9, 10, 11, 12.
  • the taps during the picture change time must e.g. be determined by a time measurement.
  • the coding then also takes place during the picture change time.
  • Any code such as the AMI or HDB3 code, can of course be used for the code multiplex.
  • an amplitude code is often used in which the code elements from the half-waves or Periods of a sinusoidal alternating current with the characteristic states small and large amplitude value exist.
  • One code element corresponds to one bit. If, for example, 12 bits are required for the composite signal and audio signal, 12 half-waves are required.
  • the coding can be carried out synchronously with the taps, since the length of the code words does not change. However, if a phase code is If a phase code is additionally provided, the period duration also changes with each phase change, so that with a periodic tap and with phase changes being rectified, the signal taps are no longer in synchronism with the code.
  • a code element has 6 different levels and 2 digits the code word, as a result. 6 to 2 combinations are possible, i.e. 36 combinations. With 32 combinations you get 5 bits.
  • the PAM for the sound is generated in the TSO element and in each case e.g. placed in half rows at 6c.
  • the connections 6c and 6d are not required if the sound and the other signals are placed in the blanking time, so that the concentrator K 1 then takes over these tasks.
  • Figs. 21, 22 and 23 it should be shown how, for example, code multiplex can also be used for television.
  • the transmission frequency can of course be significantly reduced if more amplitudes and / or phase stages are provided. It is also possible to combine it with different supports, as provided for example in patent application P 3229 139.6 Fig. 9, or with different current paths.
  • Fig. 28 with 8 KHz a 64 Koit voice channel can be transmitted, with a binary code. 2 digits are each marked by the two half-waves of an 8 KHz alternating current, 2 further digits by the 2 half-waves of an alternating current, which is 90 degrees out of phase. These two alternating currents are summed and transmitted as one alternating current via the one current path.
  • decoding is carried out on the receiving side.
  • the coding can also be duobinary.
  • Another method in particular analog signals such as speech, tones, the lumianance signal in television, the color signals in television, telecontrol values, to be transmitted frequency-modulated and with less bandwidth, consists of the size of the PAM pulses in FDM with the help of pulse duration modulation PDM
  • AC pulses e.g. can be converted according to the method of FIG.
  • the pulses are then resp.
  • Periods of an alternating current are formed, the.
  • Periods or Half-periods of the half-waves or Periods equal to the length of the PDM pulses.
  • the spectrum of the frequency-modulated oscillation used to date contains a large number of side oscillations above and below the carrier, so that a very wide band is required for the transmission.
  • the bandwidth required is larger than twice the frequency swing.
  • predominantly digital ones can be used
  • Switching means are used so that inexpensive production is possible
  • Consequences are converted into pulse durations with the help of the Aquidestanz process, or the information is immediately included
  • Pulse durations are then converted into rectangular pulses in connection with the pauses between the pulse durations and subsequently with the aid of filters to sinusoidal coding alternating currents.
  • the pulse durations and pauses are reshaped with the help of counter elements in connection with electronic components
  • Half period or Period of the coding alternating current If the pulse duration is small, the frequency of the half-wave is Period when the coding alternating current is high, the pulse duration is long, see above is the frequency of the half wave or Period when coding alternating current is small.
  • the evaluation is carried out, for example, by measuring the half or Periods. So there is frequency and phase modulation at the same time.
  • the pulse duration pulse in Fig. 32PD1, PD2 and the pause between the pulse durations (Fig32, -P) - the pulse duration and the pause correspond e.g. each the distance between two taps, denoted by tp in Fig. 30 - fed to an electronic relay, in which bipolar rectangular pulses are then generated. Filters are then used to generate the frequency-modulated coding alternating current.
  • FIG. 7 it is shown how with the aid of a counter Z in connection with the frequency of the indexing or Measimpulse generated in the oscillator Osc, the time of a pulse is determined.
  • the respective output of the counter marks the time.
  • This is then provided in connection with gates for the control of an electronic relay ER. This then generates bipolar rectangular pulses.
  • the function is as follows.
  • the advance or Measuring pulses generated for the counter Z reach gate Z.1 via gate G.1 as long as the start character at B is present.
  • the outputs Z1 and Z2 of the counter are required. These outputs are at gates G2 and G3.
  • the encoder sets the g3 h potential so that when output Z1 is reached, a potential change takes place at the output of G3, which causes the electronic relay ER to trigger the rectangular pulse to end. If this was a positive impulse, the next impulse becomes negative. The counter is then switched back in this position.
  • gate G4 is provided at output z2.
  • the oscillator frequency can also be increased or decreased via fA, so that different times could be marked with the respective outputs, for example.
  • a connection A also goes from the encoder Cod to ER, with which one can control different pulse sizes J.
  • the square-wave pulses are applied to the line as a sinusoidal coding alternating current via a low-pass filter TP, the transformer U and filter Fi.
  • the half- Period of the encoding alternating current is the same as that of the rectangular pulse.
  • FIG. E The principle of converting the square-wave pulses into a sinusoidal alternating current is shown in FIG. E.g. Rectangular pulses with the frequency 1 MHz with a low pass 5.5 MHz band-limited, so you get, as shown in Fig.3c, still fairly steep edges.
  • Fig.3b a low pass of 3.5 MHz was used: you can see that the slope has already decreased noticeably.
  • a low pass of 1.5 MHz is switched on, the receiver has a sinusoidal alternating current.
  • the periods are the same as those of the rectangular pulses, i.e. one can, respectively, the period durations as a measure of the frequencies. Take phases.
  • this principle was used when converting the rectangular pulses J into an encoding alternating current with the help of the low-pass filter TP.
  • Fig. 4 shows rectangular pulses of different periods, expressed by the frequencies f, f1 and f2. These rectangular pulses have different phase shifts relative to one another, different frequencies. It can be seen from this that by changing the periods, phase jumps or Can cause frequency jumps, so that you also get a frequency modulation. Such a phase or Frequency step by step. This ensures that the bandwidth becomes small. As can be seen from FIG. 6, a total phase shift of 40 degrees is obtained with phase jumps of 5 degrees each 180 degrees with 4 phase jump steps.
  • FIG. 30 shows PAM-coded pulses from a signal Inf. These are converted into pulse duration pulses using an equidistance method, as shown in FIG. 30b.
  • the distance between the PAM pulses (Pig30atP) corresponds to a pulse duration PD and a pause P, as in FIG.
  • Pulse duration modulation can also be saw tooth process. In the Fig. 31 and 32 this procedure is shown.
  • the pulse durations are rectangular pulses PD1, PD2 ....
  • the symmetrical PDM and the bipolar PDM are known. (see also book
  • the pulses are generated, for example, according to Fig. 30 or 32, and fed to the gate Gl via G5.
  • the measuring pulses Jm for example 100 kHz frequency, are located at the other input of the gate Gl. As long as there is a PD pulse at Gl, the measuring pulses Jm are effective at the output. Via the potential reversal gate G2, the measuring pulses reach the counter Z, which is controlled with these pulses.
  • the number of outputs on the counter corresponds, for example, to the distance between 2 PAM pulses, in Fig. 30a tp.
  • the tap frequency is 10 KHz, then the counter would have 100,000 outputs.
  • the frequency swing is determined by the largest and smallest amplitude value of the information Inf, denoted by gw and kw in FIG. 30a.
  • the outputs A of the counter Z lead to gates G3 and the outputs of the gates to gates G4.
  • the respective PD pulse that blocks gate G4 is located at the other input of gate G4 (only when the PD pulse is no longer present can the output potential also become effective via G3 at G4.
  • ER now receives a potential change indicator via G4 for the next rectangular pulse, the beginning of the rectangular pulse is marked by the respective PD pulse, the next rectangular pulse is determined by the pause P (Fig. 30b, P). From ER a potential is applied to gate 5 via P, and thus to the gate Gl the measuring pulses Jm become transparent again.
  • the counter z is now switched to the output of gate G6.
  • G6 becomes effective and the counter is switched back to the starting position via R.
  • Rectangular pulses RJ are then at the output of ER the size of the half-periods such as that of the PD pulses and the pauses P.
  • the rectangular pulses become (sinusoidal half-waves fmo, so the information is frequency-modulated.
  • the half perio of the useful signal modulation frequencies then move between the half-periods on the counter with kw and gw marked.
  • the pulse dansers can change by half.
  • the PAM pulses are then one period behind on the receiving side.
  • the redundancy of the pauses in Fig. 35 can be avoided if, for example, the PAM pulses are saved and the next EAM pulse is called up after each PD coding. However, synchronization is then required at the receiver.
  • the tap frequency would have to be synchronized from time to time.
  • 36 shows the basic circuit of such a circuit on the transmission side.
  • the PAM pulses are stored in the memory Sp.
  • the ER receives the next pulse via AR. In preparation, the next pulse was saved as a PDM pulse in memory Sp1.
  • the counter Z is now controlled via the control element St and set to a corresponding output. ER also brought the counter back to the starting position via R.
  • the control impulses Jm are also on the control unit.
  • a PAM pulse is also sent from the memory Sp to the duration modulator and stored in it as a PDM pulse until the Sp1 memory is free again. It is advisable to provide 2 Sp1 memories, which are then alternately connected to the control unit after each call of ER.
  • a pulse end criterion is given to ER via counter Z, G1, G2.
  • the square-wave pulse PD generated by ER is reversed to the next, the counter is switched back via R and the call of the next most PDM pulse ice initiated.
  • the rectangular pulses RJ are passed on via a filter. Half waves with the half-period durations of the PDM pulses then arise at the output of the filter, as are shown in FIG. 37.
  • the PD pulses and possibly pauses of Figs. 30b and 32 directly control the electronic relay ER.
  • a polarity reversal occurs after each square-wave pulse.
  • the ER relay can also be controlled in Fig. 38.
  • a polarity reversal is only required after each pulse.
  • the beginnings of the PD pulses are only marked via PDS if a continuous transmission of PD pulses is to take place. In the case of a pulse / pause transmission, the start and end of a pulse are marked anyway.
  • the respective pulse must be coded equally by a positive and negative half-wave. This can e.g.
  • a division into 2 half pulses can also be achieved using the symmetrical PDM.
  • the PDM pulses of FIGS. 32 and 32a can also be connected directly to a filter Fi according to FIG. 38. In order not to allow the bandwidth to be increased, it is then expedient, as shown in FIG Place information in the sawtooth voltages so that the difference in length or The width of the pulses does not become too large.
  • the PD pulses according to Fig. 30b can also be applied directly to the ER switching means. After each pulse, a polarity reversal or no potential must then be applied to the rectangular pulses. The rectangular pulses would then be unipolar.
  • Channel a + b are modulated in quadrature amplitude and channels c + d are modulated in quadrature amplitude, whereby the channels have a phase angle of 0 °, 90 °, 90 ° and 180 ° and their total alternating currents have a phase angle of 45 ° and 135 °, and that the two total alternating currents again modulate quadrature amplitudes the evaluation is more difficult, as can also be seen from FIG. 11 (vectors 1, 11 and III arise with a single QAM).
  • Fig. 40 shows the binary values of the 4 channels again.
  • Fig. 41 2 rows of Fig. 40 are to be combined into 8 bits.
  • 6 MHz is the frequency of the alternating currents; 18 MHz is then required for the coding.
  • FIG. 41 uses a duobinary coding corresponding to FIG. 62 with the half-waves as code learning distance, one would gain some bandwidth compared to FIG. 39, but the frequency would be 3 times as high.
  • you combine the rows 1, 2, 3 and 4, 5, 6, i.e. 12 bits together for this duobinary code a 3-step code word with 8 digits is required for a row 1, 2, 3.
  • Fig. 45 shows a 4-level code element, with 4 digits this gives 256 possibilities. Coding according to Fig. 41 would result in a frequency reduction to 36 MHz. 63 shows a 6-stage code element. In order to code 3 rows of Fig. 40 serially, i.e. 12 bits, 5 digits would be required. So 30 MHz would still be required. In addition to the 3 amplitude levels, there are two phase levels. Periods provided. Fig. 46 shows 3 amplitudes and 3 phase steps. If 2 rows with 12 bits each are formed on the arrangement of Fig. 40, 3 digits are required for each row, 6 digits for both rows, ie it is one Frequency of 13 MHz necessary.
  • Fig. 43 the color television signals are arranged in a different way.
  • 8 bits for a Y tap are 4-bit serial, the colors red or blue 3-bit serial in the row III + IV.
  • the 4th bit in rows 3 and 4 is intended for sound and other purposes.
  • the color red or blue comes with every 2nd Y signal, i.e. these are constantly changing.
  • the vertical rows 1/2 and 3/4, as shown in Fig. 44 are combined, coding results in a more favorable ratio. With 4 stages, 3 digits are required, a frequency of 18 MHz is then required. If rows 1/2 and 3/4 are arranged in parallel, i.e. 16 bits, 4 digits are required for coding according to Fig. 46, i.e. 12 MHz frequency.
  • the double QAM of FIG. 39 can be transmitted frequency-modulated in order to have even more security during the transmission.
  • the total alternating current has only small frequency changes, so that, as can be seen from Fig. 64, the frequency-modulated oscillation can be transmitted in a narrow band.
  • the half-period T / 2 becomes very small when the frequency is increased, that is to say the frequency increases sharply. With a modulation frequency Mf and an amplitude u, the half-period T / 2 is shorter, with double amplitude 2u the half-period is shorter, while with an additional double frequency M2f, the half-period is significantly reduced.
  • Fig. 47 shows an overview of a television transmitter in which the codes explained in FIGS. 40, 41, 43 and 44 are used.
  • the analog tapped signals come from the multiplexer (not shown) into the
  • Analog-rich ASp and from there 'the samples are passed on to one or more analog / digital converters.
  • the digitized signals are then stored in the digital memory DSp and subsequently fed to the folder. In this they become according to Fig. 40, 41, 43 or 44
  • the SebdeewechseIstrom comes via the receiving antenna E in the stages tuning circuit / amplifier, mixer / Oszillaotr Mi / Osc, via the intermediate frequency amplifier.
  • the input is connected like an overlay receiver for radio reception - the code change current is available at the output of the demodulator. This is switched into the decoder.
  • the signals tapped in the transmission multiplexer are received here again, like the Y, r-y, b-y. Sound and other signals S and the various circuits supplied.
  • FIG. 50 and 51 show analog encodings of the color television signals.
  • An alternating current of the same frequency is provided as a code alternating current in FIG.
  • the half-wave amplitudes are the code elements.
  • the tap sequence is y, r, y, bl, y, T + S etc.
  • the transmission of these analog coded signals takes place on the basis of frequency modulation, so that a narrow band - only one frequency Fig. 64 - and also a transmission security is obtained.
  • An analog code is also provided in Fig. 51. It is a phase encoding.
  • the analog code is given by different half-period lengths.
  • the amplitudes of the half-waves are always the same size, it is a kind of frequency and phase modulation.
  • the individual signals are aries arranged in series, in the example y, r, y, bl, y, T + S.
  • the transmission takes place at a tap frequency of the Y_ signal at 6 MHz at 6 MHz. If all signals are multiplexed, including the r, bl and T + S. Signals, a tap frequency of 12 MHz is required.
  • Half-periods set.
  • the respective amplitude value is given to the ER relay of FIG. 36 in which a square-wave pulse with low or high voltage is then generated.
  • the amplitude code elements can e.g. multiple channels, v / ie sound stereo, etc.
  • the 4 half-wave elements are assigned to 4 different channels.
  • FIG. 59 An evaluation of the PDM, PPM or PFM pulses encoded with the half-periods is shown in FIG. 59. This is done again with the help of sawtooth tension.
  • the generator of the sawtooth voltage is switched on, after the half wave at the next zero crossing, the sawtooth voltage is briefly connected to a capacitor, for example by means of a field effect transistor, and stored in the capacitor.
  • the half-period T / 2 is then equal to the voltage value T / 2 or, analogously, the magnitude of the voltage value.
  • the half-period of 1 corresponds to the voltage value u1, that of 2 corresponds to that of u2, etc.
  • the voltage u1, u2, u3 must be tapped on the receiving side at the same frequency and converted to the voice alternating current .
  • the stored values u1, u2, u3, ... must be redistributed with the same frequency of the time-multiplexed tap.
  • the original information can be produced, for example, in the way by forming the evaluated code u1, u2, .. after the channel allocation in a step-like manner and passing this step signal over a low pass. Such reform are known and are therefore not dealt with in more detail.
  • PPM pulses can also be decoded in the same way as in FIG. 59 the PDM pulses. This is shown in FIG. 60.
  • the distance T / 2 of the pulses is converted into PAM pulses again using the sawtooth method and stored.
  • the distance T / 2 then corresponds to the voltage u1 etc.
  • the evaluated signals must be distributed synchronously on the reception side.
  • the Austas.tzeit synchr ⁇ nisierirapulse must be sent so that the sampling frequency on the receiving side, the distribution frequency can be determined according to the transmission side.
  • the sum of the largest half-periods per line that may occur must not exceed 54 us, this is the time that is provided for a line with a 4: 3 aspect ratio.
  • the half-periods in the transmitter may also have to be measured.
  • there must also be a fill code in the line code which contains, for example, the smallest or largest periods in a specific sequence. Of course, other fill codes can also be provided.
  • the blanking time must also be provided as a fill code.
  • Fig. 61 the smallest and largest half-periods k and g are shown. Such can e.g. are sent alternately.
  • the multiplexer Mu combines the channels 1 to n in terms of pulse amplitude, which is well known. These PAM samples are stored in the memory Sp, called up by the PDM and, as already described, fed to the counter via a control unit St, to which the control pulses Jm are connected. The other switching operations are the same as e.g. described in Fig. 36. After the pulse detector modulator PDM, the pulses can also be processed directly in accordance with FIG. 38. On the receiving side, of course, synchronization and distribution must take place in accordance with the tap frequency of the multiplexer.
  • FIG. 57 Another possibility of multiple use of a current path is shown in FIG.
  • To the Codiet alternating currents To be able to separate in terms of frequency, control pulses are used such that the frequency ranges of the alternating code currents are at such a distance that a correct evaluation is possible, for example by means of a filter in the receiving station.
  • Z1 is the one converter with the control pulses Jm1 and Z2 the other converter.
  • Fig. 58 shows the frequency position of the two channels.
  • T / 21 and T / 2II are the lowest frequencies of the two channels.
  • the respective angular stroke f2 brings the frequency range of channel T / 21 closer.
  • I el is still a distance from Ab. This can be chosen so that inexpensive udders can be used.
  • Half waves with the characteristic states of large and small amplitude values are provided.
  • a bit can then be encoded with a half wave.
  • FIG. 66 A possibility is recorded in FIG. 66 of how a message can be transmitted digitally in narrowband fashion without modulators.
  • Each code element is assigned a plurality of periods of an alternating current of a frequency, which are determined by the time Og, that is to say a predetermined number of periods.
  • the coding is assumed to be binary. With each change of state, i.e.
  • the transition takes place continuously, marked with Ü in Fig. 66.
  • the amplitudes for zero have the large Ak and for the characteristic state 1 the Great Ag. If the same values come in succession, the amplitude size is not changed. With 5 identical values one would send a period number of Og with the same amplitude five times.
  • the coding of information according to FIGS. 53, 54 and 66 results in very narrow frequency bands. This can also be used in television technology. So you could possibly put more channels between the individual television channels. An example of this is shown in FIGS. 42 and 82.
  • the carrier BTz is provided for this in FIG.
  • the carrier is also taken along for modulation. It is thus coded according to, for example, FIG. 66.
  • the carrier is also respectively in the image channel gap.
  • the carriers are provided for the sound information.
  • VHF it is necessary, for example, to provide a series resonance circuit for the next higher television channel. Suction curve.
  • the resonance resistance is only as large as the terlust resistance.
  • the Nyquist flank is hardly affected.
  • FIG. 1 A basic circuit diagram of the accommodation of an information channel between two television channels is shown in FIG.
  • the image signal B luminance signal
  • Color carrier oscillationF and the blanking and synchronizing signals AS are added to the PBAS signal in the adding stage.
  • the CVBS signal is then fed to a modulator Mo with the carrier frequency of 38.9 MHz via an amplifier stage.
  • the amplitude-modulated signal is then fed to the residual sideband filter, so that the lower sideband is partially suppressed, as is known.
  • the series resonant circuit is arranged in the circuit.
  • the resonance frequency here is 37.9 MHz.
  • the resonance curve is designated RR in FIG. 42.
  • several channels are combined time-multiplexed on a PAM basis (K1-X) and fed to the encoder. In this there is also a PAM / PCM converter, which converts the serial incoming PAM pulses of channels K1-X into a binary, duobinary or other code.
  • An oscillator feeds the encoder with the carrier frequency of 195.25 MHz.
  • This alternating current is then modulated with the PCM pulses analogously to a code from FIG. 66.
  • the modulated carrier is then fed to a decoupler E, to which the modulated sound carrier is also connected. Both signals are then possibly via an amplifier of a crossover W, to which the carrier of the composite signal is connected, in the example 189.25 MHz.
  • the sound carrier has a frequency of 194.75 MHz. All carriers are thus guided to the common antenna via the switch.
  • the series resonance circuit for the additional channel of 195.25 MHz is thus arranged in the television channel with the transmission frequency of 196.25 MHz.
  • a television channel can also be accommodated in the additional channel.
  • the digital code of Fig. 66 can also be modified as an analog / digital code.
  • 68 and 69 show a method for coding the color beard signals red and blue.
  • the color characteristic values are tapped at a predetermined frequency and modulated on each carrier, which are 90 degrees out of phase with respect to one another.
  • the carriers have at least twice the tap frequency. These are summed up.
  • the total alternating current contains the position of the color vector in the color circle due to the phase shift compared to a comparison alternating current. This bubble shift is caused by the period. Residual period compared to the comparison alternating current. Storage of these values is necessary for a double carrier frequency up to half the number of taps in a line, and for three times the carrier frequency 1/3 of the taps in a line.
  • the values of the phase shift are transferred to the half or Period duration of an alternating current included. With cable transmission one can maintain the
  • the carriers have 3 times the tap frequency.
  • 68a shows the sampling pulses P1, P2, P3, .. of the color difference signal BY. These are drawn in step-like dashed lines - expanded. A step-like expansion is brought about by a capacitor storage with a certain time constant.
  • 68b shows the taps P1,2,3, .. of the color difference signal RY with the step-like extension.
  • 68c and d show the two carrier alternating currents with the modulated staircase-shaped signals. The two modulated carriers are now added. A total alternating current is then obtained as shown in FIG. 68e.
  • the amplitude corresponds to the size of the color vector, this is a measure of the saturation of the color and the phase shift in relation to a comparison phase then corresponds to the color tone in the color wheel. This is already the case with the NTSC systems and PaL are known and will therefore not be discussed in more detail.
  • the output resp. Comparison phase V g is in the
  • Fig. 68f shown.
  • the phase shift therefore always remains in the example during the 3 periods of the carrier Su.
  • the half-period cannot be measured, which is why at least 3 periods are provided in the example until the next phase change.
  • a coding half-period is composed of 2 constant periods KP and the actual coding phase shift Ph, which is almost a period at 359 degrees phase shift.
  • the individual processes of transferring the phase shift to the period are shown in FIG. 69. For this, 3 color circles are shown with the phase shifts 60, 120 and 240 °.
  • the start of measurement is designated in the Mg, 68g and in Fig.
  • the burst would have a phase angle of 0 ° as shown in dear Fig. 69d.
  • a 3urst is not necessary in the example because the transmission is determined by the absolute period value. It is advisable to code the beginning of the serial arrangement of the code elements for each line.
  • the half-period i.e. the pulse that controls the ER relay in Fig. 75, begins with Be in Fig. 68 f and lasts for the two periods and also the size of the phase shift Ph.
  • the phase shift is 60 ° a phase shift of 300 ° was measured.
  • the total pulse is then equal to the two periods + the length of 300 °.
  • This pulse is amplified, for example, by ER relays and then converted to a sinusoidal coding alternating current using a filter, as has already been described many times.
  • the length of the half-periods in a television line thus becomes smaller than the distances between the sum of the step signals and the color difference signals. Therefore, the sum of the half-periods must also be measured and, if necessary, a filling half-period must be inserted if one is appropriate assigns the duration of 3 periods of the comparison alternating current.
  • the alternating currents shown in FIGS. 69a, b, c me are total alternating currents Su. In Fig. 69b the color angle is 120 °, the measurement is 240 ° and in Fig. 69c the color angle is 240 °, the measurement is 120 °.
  • the measured period is added to the two constant periods KP. In the examples, the saturations are 100% respectively.
  • 69d shows the phase comparison alternating current.
  • the period of a period of the total alternating current b maintain the phase angle of 360 degrees. To get even more accuracy, you can provide 180 degrees for a period by making an additional mark. If the phase shift is up to 180 degrees, a phase shift over 180 degrees is measured, as can be seen from FIGS. 69a and b. Here it is only necessary to measure the phase shift of the positive half period. Since only the period is required for coding the pixel size in the half-periods, an amplitude code can be used to code that the angle is more than 180 °. When transferring, you can then transfer twice the value of the angle. In Fig.
  • the angular size dw can then become twice as large.
  • the amplitude code must then be evaluated in the receiving station and the additional 180 ° angle taken into account.
  • the color and pixel coding can be transmitted in parallel in a manner similar to that disclosed in FIG. 58 or in series as shown in FIGS. 70 and 71.
  • the pixel tap is twice as fast as that of the color signals. Since the code alternating current is to take place in an uninterrupted sequence of positive and negative half-periods, there is no synchronism between tapping and coding. A more or less large storage is therefore necessary on both the transmitting and the receiving side.
  • the pixel and color signal assignment must be made exactly at the tap frequency of the transmission side.
  • 69a is coded by the amplitude size, which is stored like the period.
  • Fig. 70 A possible arrangement for the transmission is shown in Fig. 70.
  • the required frequency is determined by the number of image taps and color type tap number determined. If 832 pixels are to be tapped in a line and (a half period is required for each pixel, then 416 periods are required for the pixels. For the color coding, 1 half period must be provided for every 2 pixels, that is, 213 periods for a line. For example, these 629 periods are assigned one Time of 52 ⁇ s available. The frequency and the smallest frequency of the coding alternating current is then predetermined. The blanking interval of 12 ⁇ s is given the same frequency.
  • the coding half-periods are always smaller than the calculated ones, filling half-periods must be provided which are expedient for the greatest period A different code can of course also be provided for these.
  • the pixel half-periods always have the same amplitude size, while for the color half-periods the color vector is coded with the amplitude magnitude, that is to say the saturation is coded
  • Pixel half-period n are provided, can be provided as coding for the filling half-periods.
  • the storage of the amplitude size of the color or Saturation vectors can take place by means of a capacitor which is connected to the coding alternating current Su via a diode.
  • the pixel half-periods B (Y) can also be overlaid with a binary or duobinary amplitude code, with which the speech and other signals are then digitally encoded, as already described in FIGS. 52, 55.
  • a pixel coding is also assigned a binary coding for a phase angle of the hue greater than 180 °.
  • Fig. 69a for example, it is found that the counting half-period dw is positive, so that the negative half-wave no longer needs to be measured. These 180 ° are determined by this coding B + 180 °. The value dw becomes twice as large during transmission, so that the accuracy increases.
  • the further pixel half-period B + T / S is overlaid with a binary or duobinary amplitude code, with which the digitized speech and other control signals are then encoded.
  • the half-period F includes the hue angle in the half-period duration and the color or analog in the amplitude size.
  • Saturation vector. 72 shows the principle of an interconnection of the
  • Half periods are shown with the amplitude code.
  • An electronic relay again supplies square-wave pulses RJ. The period of these rectangular pulses is marked with Ph.
  • memories are provided in which the pixel taps may already have been stored in half-periods.
  • a memory is provided for storing the color angle KP + Ph.
  • the amplitudes of the rectangular pulses are supplied to the electronic relay ER in the folder Or in synchronism with the half-periods.
  • the analog amplitude size of the color vector is retrieved from the memory via FA.
  • T + S the digitized sound and other signal amplitudes are called up from a memory and sent to the electronic relay in the order e.g. of Fig. 70 fed.
  • Such an electronic relay with several amplitude stages is shown in FIG.
  • the square-wave pulses with the corresponding period durations and amplitude stages are then at the output of ER. These are then converted into a sinusoidal alternating current in the filter Fi.
  • the direct measurement of the phase angle is also possible.
  • the zero crossings from BE Fig. 68g must then be counted with the sum current, so that e.g. can determine the zero crossing M in Fig. 69b. From this point, the measurement is carried out up to Ph0 °.
  • Ph in Fig. 68g could then e.g. spread over 90 ° of the phase shift.
  • the 3 remaining 90 degree angles would then have to be coded with 180 °, similarly to FIG. 71.
  • the coding alternating currents of FIGS. 70, 71 are modulated onto the transmitting alternating current and transmitted.
  • the receiver is then switched in principle as shown in Fig. 23.
  • the input signals are routed via the tuning circuit / amplifier HF mixer / oscillator via the intermediate frequency amplifier V to the demodulator DM.
  • the demodulated alternating coding current for example according to FIG. 70, is fed to the decoder DC.
  • the distribution of the image and color values (FIG. 70, 71) must take place in accordance with the image point and color difference signal taps.
  • alternating current at the sampling frequency during the blanking time, which is then used for the synchronization of the im Receiver provided as a distributor synchronized alternating current.
  • the amplitudes of this synchronizing alternating current of the blanking time can also be provided for binary or duobinary coding.
  • the pixel values can be evaluated, for example, according to Fig. 59.
  • the evaluation of the color mode element with the half-period values and the amplitude quantities, which if necessary is converted into a length similar to that shown in Fig. 74a, is best carried out on a computational basis.
  • the sound (stereo) and other signals that are PCM-coded can be demodulated in a known manner.
  • Fig. 67a shows the pixel taps BAb and the color difference signal taps FAb and, in addition, how to use them e.g. with serial transmission (Fig. 70) the coding alternating current can be assigned (Cod).
  • Fig. 79 shows a particularly useful coding method.
  • Code elements that take the form of a period or a
  • Binary value 0 and a relatively large one e.g. twice that
  • Fig. 79 is shown.
  • the nine-digit binary number to be coded are generated by the successive half-waves of a sine wave
  • Fig. 79 shows.
  • the sixth, seventh, eighth and ninth bits of the nine-digit binary number are represented by the successive half-waves of a sine wave of the period P / 2, as curve c in FIG. 79 shows.
  • Sinusoids in curves A, B and C are all shown in the first period P1 to simplify the illustration with the same amplitude that encoded
  • Binary number would consist of nine ones.
  • the curve 00 shows the value 00 in the period P2 and the value 10 in the period P3.
  • the oscillation trains corresponding to curves a, b and c that are created during coding are superimposed on one another and can then be transmitted over a single line.
  • the vibrations a, b, c are separated by filters and can then be decoded in a known manner, e.g. B. by measuring the duration of each half period, as described in US Patent 4,794,621.
  • each coding period P the different coding oscillations a, b, c etc. must always have the same phase position. You can also work with duobinary amplitude levels, so that 3
  • phase-shifted, superimposed coding alternating current of this type are then 3 18 combinations available.
  • a duobinary coding is e.g. B. used in the European D-MAC system.
  • each coding oscillation a, b, c etc. can be further increased by giving each coding oscillation a, b, c etc. a second phase-shifted by 90 degrees
  • Fig.7.7 is a circuit arrangement according to the invention
  • a color television signal which contains a luminance signal L, color signals I and Q, synchronization signals, if necessary, additional signals S and sound signals T.
  • the luminance signal is tapped at a predetermined frequency and fed to an analog / digital converter A / D, which
  • the color signals I and Q are tapped simultaneously with a frequency that is equal to half
  • the buffered signals are alternately switched via a switch U4. to an analog-to-digital converter A / D, which converts the samples into 6-bit code characters.
  • the synchronization signals and possibly other signals S are synchronization signals and possibly other signals S.
  • the audio signals T which are stereo signals, different languages etc. can act alternately or simultaneously with predetermined ones Tapped frequency, buffered in a buffer ZSp and fed via a switch U5 to an analog-to-digital converter A / D, the z. B. 8 or 16-bit code characters generated, which are also in the memory SP. be fed.
  • An encoder Cod is coupled to the memory Sp, of which the eight at a time, that is to say in parallel
  • Code elements of the I or Q signal can be called up via changeover switches U1 to U3 and a code element of the S or T signal, as shown in FIG. shown in column I.
  • a conventional radio frequency transmitter M is then modulated with the successive code characters, see columns I to IV etc. in FIG. 78, and the modulated radio frequency oscillation is emitted via an antenna S.
  • the high frequency oscillation is on the receiving side
  • the code words are demodulated in the decoder Dcod.
  • the eight bits of the respective samples of the luminance signal L are then simultaneously available on a group 1/8 of eight output connections; in a group
  • Buffer Sp1 are buffered and at an output 12 the S / T bits, which are in a memory
  • the luminance signal bits are converted into an analog luminance signal L in a digital / analog converter D / A.
  • D / A a digital / analog converter
  • the color signal bits are buffered and if six bits of an I and a Q signal sample are available, the now complete color signal code characters are converted by a digital-to-analog converter
  • the S / T bits are stored in the buffer memory Sp2 and, if complete code characters are available, in a digital-to-analog converter D / A into corresponding ones
  • Analog signals are implemented which, if required, can be buffered again in an intermediate memory Sp4 or processed directly. During the blanking period, the transmitter M can switch others via a switch U6
  • Code signals X are supplied, which are available on the receiving side at an output AT of the decoder DCod and are fed to a corresponding utilization
  • Fig. 83 shows a simple 4 PSK phase shift keying.
  • the nominal frequency is f corresponding to a nominal period of 360 °.
  • the generation is carried out analogously to the arrangements of FIGS. 7 and 8. This arrangement replaces the coding previously used according to Fig.2. Such phase jumps are generally described in FIG.
  • FIG. 80 Various period durations are shown in FIG. 80. If the evaluation is carried out by dimension, it is expedient to determine clearly measurable period duration differences, as has happened at 0 °, a °, b ° and 90 °. The distances between 1, b, a and 2 should also be pretty much the same. In Fig. 81 there are phase differences of over 90 °. intended. One disadvantage is that the frequency changes become very large. In the case of cable transmission, it is advisable to ensure that there is no DC current, and the coding is carried out with the same positive and negative half-wave.
  • FIG. 19b A particularly advantageous coding for code-multiplexed information transmission is shown in FIG. 19b.
  • Half-waves of an alternating current are provided as code elements, in an uninterrupted sequence of positive and negative half waves.
  • An amplitude code with 3 characteristic states, i.e. a duobinary code, is provided.
  • a period then has 2 digits.
  • a second coding alternating current of the same frequency, but which is 90 ° out of phase is provided. You get 4 digits from each period. From the two coding alternating currents, 3 to 4 combinations are obtained from each period, these are 81 combinations.
  • both coding alternating currents will be added and transmitted as only one total alternating current.

Landscapes

  • Engineering & Computer Science (AREA)
  • Signal Processing (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Multimedia (AREA)
  • Dc Digital Transmission (AREA)
  • Materials For Photolithography (AREA)
  • Time-Division Multiplex Systems (AREA)
  • Selective Calling Equipment (AREA)

Abstract

Selon des procédés connus de codage d'informations, on procède à une condensation des canaux par multiplexage temporel ou de fréquences, à un coût élevé, ce qui requiert une large bande passante. Selon l'invention, les codets sériellement agencés sont parallèlement ordonnés, un à un, puis sont tous réunis en un mot de code. La sécurité de la transmission est assurée par la conversion des informations en impulsions à modulation en durée et par le codage de ces impulsions en termes de durée de demi-périodes ou de périodes, qui sont alors transmises sous forme d'une séquence ininterrompue de demi-périodes positives et négatives.
PCT/EP1989/001244 1988-10-19 1989-10-18 Procede de codage d'informations WO1990004895A2 (fr)

Applications Claiming Priority (6)

Application Number Priority Date Filing Date Title
DEP3835630.9 1988-10-19
DE19883835630 DE3835630A1 (de) 1988-08-23 1988-10-19 Verfahren zur erzeugung einer frequenzmodulation
DE3904942 1989-02-17
DEP3904942.6 1989-02-17
DEP3909079.5 1989-03-20
DE3909079 1989-03-20

Publications (2)

Publication Number Publication Date
WO1990004895A2 true WO1990004895A2 (fr) 1990-05-03
WO1990004895A3 WO1990004895A3 (fr) 1990-07-12

Family

ID=27198399

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/EP1989/001244 WO1990004895A2 (fr) 1988-10-19 1989-10-18 Procede de codage d'informations

Country Status (3)

Country Link
AU (1) AU4429689A (fr)
CA (1) CA2001071A1 (fr)
WO (1) WO1990004895A2 (fr)

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE4025026A1 (de) * 1989-12-07 1991-06-13 Dirr Josef Verfahren zur codierung von information
WO1993004572A2 (fr) * 1992-02-24 1993-03-18 Josef Dirr Codage d'images et d'originaux, par exemple pour telecopieurs et televiseurs en couleurs
US5587797A (en) * 1992-11-06 1996-12-24 Dirr; Josef Process for encoding and transmitting information

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2015695A1 (fr) * 1968-08-15 1970-04-30 Ibm
US4066841A (en) * 1974-01-25 1978-01-03 Serck Industries Limited Data transmitting systems
US4345323A (en) * 1980-01-07 1982-08-17 Amp Incorporated Pulse duration digital multiplexing system
DE3802088A1 (de) * 1987-01-26 1988-08-04 Dirr Josef Verfahren fuer die uebertragung analoger und/oder digitaler information, insbesondere unter zwischenschaltung einer, 2er oder mehrerer vermittlungen in fernmeldeanlagen insbesondere
EP0284019A2 (fr) * 1987-03-23 1988-09-28 Josef Dirr Procédé de génération de variations de la fréquence et/ou de la phase de courants alternatifs, utilisé notamment pour la modulation d'amplitude en quadrature (QAM) et pour la prise d'échantillons
EP0329158A2 (fr) * 1988-02-19 1989-08-23 Josef Dirr Procédé pour le codage numérique et/ou analogique de l'information d'un, de deux ou de plusieurs canaux et/ou la réduction de fréquence ou de bande passante et/ou l'augmentation de la sécurité de transmission

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2015695A1 (fr) * 1968-08-15 1970-04-30 Ibm
US4066841A (en) * 1974-01-25 1978-01-03 Serck Industries Limited Data transmitting systems
US4345323A (en) * 1980-01-07 1982-08-17 Amp Incorporated Pulse duration digital multiplexing system
DE3802088A1 (de) * 1987-01-26 1988-08-04 Dirr Josef Verfahren fuer die uebertragung analoger und/oder digitaler information, insbesondere unter zwischenschaltung einer, 2er oder mehrerer vermittlungen in fernmeldeanlagen insbesondere
EP0284019A2 (fr) * 1987-03-23 1988-09-28 Josef Dirr Procédé de génération de variations de la fréquence et/ou de la phase de courants alternatifs, utilisé notamment pour la modulation d'amplitude en quadrature (QAM) et pour la prise d'échantillons
EP0329158A2 (fr) * 1988-02-19 1989-08-23 Josef Dirr Procédé pour le codage numérique et/ou analogique de l'information d'un, de deux ou de plusieurs canaux et/ou la réduction de fréquence ou de bande passante et/ou l'augmentation de la sécurité de transmission

Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE4025026A1 (de) * 1989-12-07 1991-06-13 Dirr Josef Verfahren zur codierung von information
WO1993004572A2 (fr) * 1992-02-24 1993-03-18 Josef Dirr Codage d'images et d'originaux, par exemple pour telecopieurs et televiseurs en couleurs
WO1993004572A3 (fr) * 1992-02-24 1993-06-10 Josef Dirr Codage d'images et d'originaux, par exemple pour telecopieurs et televiseurs en couleurs
US5576835A (en) * 1992-02-24 1996-11-19 Dirr; Josef Method for run-length coding for shortening transmission time
US5581368A (en) * 1992-02-24 1996-12-03 Dirr; Josef Data-reducing coding method for transmitting information from a transmitter to a receiver
US5587797A (en) * 1992-11-06 1996-12-24 Dirr; Josef Process for encoding and transmitting information

Also Published As

Publication number Publication date
CA2001071A1 (fr) 1990-04-19
AU4429689A (en) 1990-05-14
WO1990004895A3 (fr) 1990-07-12

Similar Documents

Publication Publication Date Title
EP0329158B1 (fr) Procédé pour le codage numérique et/ou analogique de l'information d'un, de deux ou de plusieurs canaux et/ou la réduction de fréquence ou de bande passante et/ou l'augmentation de la sécurité de transmission
DE2839548C2 (fr)
EP0110427B1 (fr) Procédé pour la transmission d'informations selon lequel le codage des signaux s'effectue par la grandeur de l'amplitude des demi-ondes ou périodes d'un courant alternatif de forme sinusoidale
DE3828623C2 (de) Verfahren zur Erzeugung von Phasenverschiebungen, beispielsweise für die Phasenmodulation oder Phasentastung (PSK) oder Quadraturamplitudenmodulation
DE19530114A1 (de) PI/4-DQPSK-Modulation mit Abbildungsvorrichtungs-Grobpräzession und Filter-Feinpräzession
DE19743779A1 (de) Verfahren für eine höherwertige Pulsdauercodierung
WO1990004895A2 (fr) Procede de codage d'informations
WO1993004572A2 (fr) Codage d'images et d'originaux, par exemple pour telecopieurs et televiseurs en couleurs
WO1994000973A2 (fr) Procede de codage et de transmission d'informations
EP0197529B1 (fr) Procédé de codage analogique ou numérique d'information pour l'application dans les procédés de modulation d'angle et d'impulsion
DE3904900A1 (de) Verfahren fuer die digitale und/oder analoge codierung von information eines, zweier oder mehrerer kanaele und/oder frequenz-oder bandbreitenreduzierung und/oder erhoehung der uebertragungssicherheit
DE4025026A1 (de) Verfahren zur codierung von information
DE4028927A1 (de) Verfahren fuer die codierung und uebertragung von information, insbesondere von vorlagen und bildern und fuer das fernsehen
EP0284019B1 (fr) Procédé de génération de variations de la fréquence et/ou de la phase de courants alternatifs, utilisé notamment pour la modulation d'amplitude en quadrature (QAM) et pour la prise d'échantillons
DE3940531A1 (de) Verfahren zur codierung von information
DE4025034A1 (de) Verfahren fuer die codierung und uebertragung von information, insbesondere von vorlagen und bildern und fuer das fernsehen
DE4025042A1 (de) Verfahren fuer die codierung und uebertragung von information, insbesondere von vorlagen und bildern und fuer das fernsehen
DE4028928A1 (de) Verfahren fuer die codierung und uebertragung von information, insbesondere von vorlagen und bildern und fuer das fernsehen
DE3831054A1 (de) Verfahren fuer die digitale codierung von information eines, zweier oder mehrerer kanaele und/oder frequenzreduzierung des bezw. der codierwechselstroeme und uebertragung derselben
DE3831055A1 (de) Verfahren fuer die digitale codierung von information eines, zweier oder mehrerer kanaele und/oder frequenzreduzierung des bezw. der codierwechselstroeme und uebertragung derselben
DE3828115A1 (de) Verfahren fuer die codierung von information eines, zweier oder mehrerer kanaele und/oder frequenzreduzierung des bzw. der codierwechselstroeme und uebertragung derselben
EP0543848B1 (fr) Codage d'images, par exemple pour telecopieurs et pour la television en couleurs
DE3828100A1 (de) Verfahren fuer die codierung von information eines zweier oder mehrerer kanaele und/oder frequenzreduzierung des bzw. der codierwechselstroeme und uebertragung derselben
DE3522734A1 (de) Verfahren fuer die codierung von information fuer die verwendung bei winkelmodulationsverfahren (z.b. frequenzmodulation)
AT372230B (de) Anordnung zur datenuebertragung

Legal Events

Date Code Title Description
AK Designated states

Kind code of ref document: A2

Designated state(s): AU BR JP KR SU US

AK Designated states

Kind code of ref document: A3

Designated state(s): AU BR JP KR SU US