US20070116476A1 - Method and apparatus for generating optical duo binary signals with frequency chirp - Google Patents

Method and apparatus for generating optical duo binary signals with frequency chirp Download PDF

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US20070116476A1
US20070116476A1 US11/283,177 US28317705A US2007116476A1 US 20070116476 A1 US20070116476 A1 US 20070116476A1 US 28317705 A US28317705 A US 28317705A US 2007116476 A1 US2007116476 A1 US 2007116476A1
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signal
coded signal
output
delayed
encoded
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Yu Bai
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FutureWei Technologies Inc
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FutureWei Technologies Inc
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Assigned to FUTUREWEI TECHNOLOGIES, INC. reassignment FUTUREWEI TECHNOLOGIES, INC. ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: BAI, YU SHENG
Priority to PCT/CN2006/003114 priority patent/WO2007056959A1/en
Priority to EP06817852A priority patent/EP1955451B1/en
Priority to CN2006800432047A priority patent/CN101313496B/zh
Assigned to HUAWEI TECHNOLOGIES CO., LTD reassignment HUAWEI TECHNOLOGIES CO., LTD CORRECTIVE ASSIGNEMNT TO CORRECT THE ASSIGNEE'S NAME AND ADDRESS PREVIOUSLY RECORDED ON REEL 017264, FRAME 0413. ASSINGOR HEREBY CONFIRMS THE ASSIGNMENT OF THE ENTIRE INTEREST. Assignors: BAI, YU SHENG
Publication of US20070116476A1 publication Critical patent/US20070116476A1/en
Assigned to FUTUREWEI TECHNOLOGIES, INC. reassignment FUTUREWEI TECHNOLOGIES, INC. CORRECTIVE ASSIGNMENT TO CORRECT THE ASSIGNEE NAME TO FUTUREWEI TECHNOLOGIES, INC. PREVIOUSLY RECORDED ON REEL 019380 FRAME 0766. ASSIGNOR(S) HEREBY CONFIRMS THE ASSIGNEE WAS INCORRECTLY LISTED AS HUAWEI TECHNOLOGIES CO., LTD.. Assignors: BAI, YU SHENG
Priority to US13/113,733 priority patent/US8311416B2/en
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/50—Transmitters
    • H04B10/501—Structural aspects
    • H04B10/503—Laser transmitters
    • H04B10/505—Laser transmitters using external modulation
    • H04B10/5055—Laser transmitters using external modulation using a pre-coder
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/50—Transmitters
    • H04B10/501—Structural aspects
    • H04B10/503—Laser transmitters
    • H04B10/505—Laser transmitters using external modulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/50—Transmitters
    • H04B10/516—Details of coding or modulation
    • H04B10/5167—Duo-binary; Alternative mark inversion; Phase shaped binary transmission

Definitions

  • the present invention generally relates to an optical transmitter, and more particularly to optical transmission method and apparatus for generating optical duo binary signals with frequency chirp.
  • SMF standard single-mode fiber
  • the spectral width of a chirp-free optical signal is given by the Fourier transform limit, i.e., the width is equal approximately to the inverse of the minimum pulse duration, or the data rate.
  • the minimum pulse duration is 100 ps and the spectral width is around 10 GHz or 0.08 nm.
  • the signal pulses After 70 km transmission in SMF, the signal pulses would be broadened by around 100 ps, the minimum pulse duration or the bit period. Therefore the dispersion limited transmission distance of a chirp-free 10 Gbps NRZ optical signal is about 70 km in SMF.
  • ODB Optical Duo-Binary modulation
  • a partial response method of generating ODB signal was described in U.S. Pat. No. 5,867,534, “Optical Transmission Method with Reduced Sensitivity to Dispersion, Transmission Device and System For Implementing this Method” by Price, et al.
  • a quasi three level electrical signal is first generated by passing an input NRZ signal through a narrow filter with bandwidth about 25% ⁇ 30% of the data rate. Then the three-level electrical signal is used to drive a MZ modulator biased at null to generate the ODB signal.
  • dispersion limited transmission distance of 210 km in SMF is obtained by applying the partial response method.
  • the longer transmission distance of an ODB signal is not entirely due to the narrower bandwidth.
  • the “bumps” in the optical signal near the “0” bit state also plays a very important role in extending the transmission distance.
  • the “bumps” are by-products of both partial response method and classical 1-bit delayed method using sharp cut-off filters. Since the bumps have 180 degrees phase shift to the adjacent “1” bit, the destructive interference between the bump and the adjacent “1” bit would help to confine the broadening of the “1” bit pulse. Hence the dispersion penalty would be reduced accordingly. Due to its long transmission distance and its simple implementation, the partial response method is the most widely used ODB method, and is often referred as THE ODB method.
  • the “bumps” can be also introduced using a fractional delay, instead of the whole one-bit delay, in the classical ODB method. This method is described in U.S. Pat. No. 6,623,188, “Dispersion Tolerant Optical Data Transmitter” by Dimmick, et al.
  • a four-level electrical signal is generated by combining an input binary signal with its delayed complement through a differential amplifier in this disclosure. The four-level electrical signal is then used to drive a MZ modulator biased at null to generate a four-level optical field, which could be transmitted of 150 km in SMF without any band-limiting filters at 10 Gbps data rate.
  • Chirped ODB modulation was studied in “Chirped duo-binary transmission for mitigating the self-modulation limiting effect”, presented at the OFC 2001, March 2000 by M. Wicher, et al. It shows that negative chirp could improve signal quality at shorter distance ( ⁇ 150 km at 10 Gbps) while positive chirp could improve signal quality at distances greater than 150 km, for example, a positively chirped signal was found to transmit greater than 250 km. In addition, the positive chirp was also found to reduce self phase modulation effect.
  • FIG. 1 is a schematic diagram illustrating a conventional ODB transmitter 100 .
  • An electrical NRZ source 110 is fed into a pre-coder 120 , which is used to make the final optical output signal intensity of this transmitter 100 to be as the same as the input NRZ source 110 .
  • the pre-coder 120 could be a simple XOR gate, with one input being connected to the complement of the incoming NRZ data signal and the other input being connected to the one-bit delayed XOR gate output.
  • the output of the pre-coder 120 is sent into an ODB encoder 130 , which produces a three-level or a four level signal ce(t) to a data driver 140 .
  • the ODB encoder 130 could be implemented using the delay-and-combine methods or using partial response method.
  • the output of the ODB encoder 130 is amplified by the data driver and forwarded to drive a MZ modulator 150 , which also receives optical source from a laser apparatus 160.
  • the optical output of the MZ modulator is an ODB signal where the optical intensity I(t) follows the input NRZ signal d(t).
  • the partial response method is the simplest one to generate chirp-free ODB signals with large dispersion tolerance.
  • all chirp-free ODB signals are very sensitive to non-linear distortion.
  • SPM self phase modulation
  • the frequency domain distortion is converted to time domain distortion, which is the source of non-linear penalty.
  • a positive pre-chirp could be intentionally added to the transmitting signal to compensate the SPM caused negative chirp in order to reduce introduced non-linear penalty.
  • the chirped ODB methods should have better performance with higher signal launch power.
  • the methods disclosed in prior art used double optical modulations, which require precise time alignment between the electrical signals driving the two modulators.
  • These two driving signals in the chirped ODB methods are data patterns; one is NRZ signal and another is pre-coded data.
  • the variable delay lines needed for the timing alignment have to have uniform response over a broad bandwidth, which are usually bulky and expensive. This is a big obstacle for the practical implementation of the chirped ODB modulation methods.
  • the system includes a pre-coder for pre-coding an input signal into a pre-coded signal, an encoder/separator coupled to the pre-coded signal and arranged to encode the pre-coded signal into a first encoded signal with 0 degree phase shift and a second encoded signal with 180 degree phase shift, and an optical modulator for providing optical intensity modulation to the first and second encoded signals with an light source such that the intensity of an output optical duo-binary (ODB) signal with frequency chirp has identical logic sequence as the input signal.
  • ODB optical duo-binary
  • the present invention offers longer transmission distance and better tolerance to non-linear effects comparing to prior art. Furthermore, a single modulator of the present invention is much simpler and less expensive than those methods using double optical modulations. It also makes practical implementation of chirped ODB signal possible.
  • FIG. 1 is a schematic diagram illustrating a conventional ODB transmitter
  • FIG. 2 is a schematic diagram of a chirped ODB transmitter according to one embodiment of the present invention.
  • FIG. 3A is a schematic diagram of the pre-coder and the ODB encoder/bit-separator shown in FIG. 2 ;
  • FIG. 3B is a timing diagram illustrating signals in each stage of the embodiment shown in FIG. 3A ;
  • FIG. 4A is another schematic diagram of the pre-coder and the ODB encoder/bit-separator shown in FIG. 2 ;
  • FIG. 4B is a timing diagram illustrating signals in each stage of the embodiment shown in FIG. 4A ;
  • FIG. 5A is another schematic diagram of the pre-coder and the ODB encoder/bit-separator shown in FIG. 2 ;
  • FIG. 5B is a timing diagram illustrating signals in each stage of the embodiment shown in FIG. 5A ;
  • FIGS. 6A and 6B are two schematic diagrams of the pre-coder and the ODB encoder/bit-separator shown in FIG. 2 ;
  • FIG. 7 is a diagram showing signal distortions of a positive chirped, a negative chirped, and a chirp free 10 Gbps ODB signals at various distances.
  • FIG. 2 is a schematic diagram of a chirped ODB transmitter 200 in accordance with one embodiment of the present invention.
  • An electrical NRZ source 210 provides an input d(t) to be fed into a pre-coder 220 .
  • Both two complementary outputs c(t) 221 and c(t) 222 of the pre-coder 220 are sent to an integrated ODB encoder/bit-separator 230 , which performs a predetermined encoding process and then separates the bits intended for each optical phase in an ODB modulation. After separation, those bits, intended for 0 degree phase shift, are sent to one output of this integrated ODB encoder/bit-separator 230 .
  • the other bits, intended for 180 degree phase shift are sent to another output of the integrated ODB encoder/bit-separator 230 .
  • these two outputs are denoted as a first output c 1 (t) 231 and a second output c 2 (t) 232 , respectively.
  • the two separated sequences, c 1 (t) 231 and c 2 (t) 232 are amplified by a first and a second data drivers 241 and 242 to drive two separate inputs of a dual drive MZ modulator 250 , respectively.
  • the MZ modulator 250 receiving optical source from a laser apparatus 260 , generates an ODB signal I(t) 251 with frequency chirp.
  • the sign of the frequency chirp is determined by choosing either C 1 (t) and C 2 (t) signal, or the complements, C 1 (t) and C 2 (t) , as the driving signals.
  • FIG. 3A is a schematic diagram of the pre-coder 220 and the ODB encoder/bit-separator 230 shown in FIG. 2 .
  • the pre-coder 220 includes an XOR gate 223 with an input receiving d(t) from the NRZ source 210 .
  • the other input of the XOR gate receives a one-bit delayed output of this XOR gate 223 .
  • the output of the XOR gate 223 is referenced as the output signal c(t) 221 .
  • the complementary output signal c(t) 222 is generated by an inverter 225 from the output of the XOR gate 223 .
  • the ODB encoder/bit-separator 230 comprises a first and a second AND gates 233 and 234 .
  • the first AND gate 233 takes the output signal c(t) 221 and its delayed replicated signal c(t ⁇ t) as inputs in order to generate the first output c 1 (t) 231 .
  • the second AND gate 234 takes the complementary output signal c(t) 222 and its delayed replicated signal c(t ⁇ t) as inputs in order to generate the second output c 2 (t) 232 .
  • the time delay, At can be ranged from 0.3 to 1 bit period.
  • FIG. 3B is a timing diagram illustrating signals in each stage of the embodiment shown in FIGS. 2 and 3 A.
  • the NRZ input signal d(t) 210 there are six staged timing sequences, the NRZ input signal d(t) 210 , c(t) 221 , c(t ⁇ t), c 1 (t) 231 , c 2 (t) 232 , and the final output I(t) 251 .
  • the time delay, ⁇ t is 0.7-bit period. Some narrow pulses with 0.3-bit duration could be observed in c 1 (t) 231 and c 2 (t) 232 accordingly.
  • the finite response of the circuit which is at 75% of data rate, lowered the amplitude of these narrow pulses, forming the “bumps”.
  • the timing sequence of I(t) 251 is the optical output of the dual drive MZ modulator 250 .
  • FIG. 4A is another schematic diagram of the pre-coder 220 and the ODB encoder/bit-separator 230 shown in FIG. 2 . Similar to FIG. 3A , two complementary outputs c(t) 221 and c(t) 222 of the pre-coder 220 are sent into the ODB encoder/bit-separator 230 as inputs. However, in this embodiment, the ODB encoder/bit-separator 230 comprises a first and a second LIA (differential limiting amplifiers) 235 and 236 instead of the two AND gates 233 and 234 shown in FIG. 3A .
  • LIA differential limiting amplifiers
  • the basic operational function of an LIA is that when the total input signal level is higher than a specified threshold level, the binary output of the LIA would be switched to logic “high”; otherwise, the binary output would be logic “low”. With a proper set threshold level, either the positive or the negative pulses from the differential input signals could be filtered or selected.
  • the first LIA 235 takes the output c(t) 221 and the delayed complementary output c(t) 222 as inputs.
  • the second LIA 236 takes the delayed output c(t) 221 and the complementary output c(t) 222 as inputs. Similar to the embodiment shown in FIG. 3A , the time delay, ⁇ t, in this embodiment can range from 0.3 to 1 bit period.
  • the differential input signals of these two LIA 235 and 236 could be three-level or four-level signals.
  • the differential input signals are treated as AC signals, which swing from ⁇ 1 to +1.
  • the output of the first LIA 235 could be substantially similar to the output of the first AND gate 233 shown in FIG. 3A .
  • the complementary output of the second LIA 236 could be substantially similar to the output of the second AND gate 234 shown in FIG. 3A .
  • FIG. 4B is a timing diagram illustrating signals in each stage of the embodiment shown in FIG. 4A .
  • this diagram there are six timing sequences, the NRZ input signal d(t) 210 , c(t) 221 , c(t) ⁇ c(t ⁇ t) , c 1 (t) 231 , c 2 (t) 232 , and the final output I(t) 251 .
  • the third timing sequence c(t) ⁇ c(t ⁇ t) the rest of five sequences are also shown in FIG. 3B . It is assumed that the time delay, ⁇ t, is 0.7-bit period in this embodiment.
  • a threshold level 410 of the first LIA 235 is set at +0.5 by assuming that c(t) ⁇ c(t ⁇ t) swings between ⁇ 1 and +1. All signals above this threshold level line 410 are kept by the first LIA 235 as the fourth timing sequence, c 1 (t) 231 .
  • a threshold level (not shown) of the second LIA 236 could be also set at ⁇ 0.5 by assuming that c(t ⁇ t) ⁇ c(t) ranges between ⁇ 1 and +1.
  • the output of this second LIA 236 is shown as the fifth timing sequence, c 2 (t) 232 .
  • the fourth and fifth timing sequences of FIG. 4B resemble the counterparts shown in FIG. 3B .
  • the timing sequence, I(t) 251 is the optical output of the dual drive MZ modulator 250 .
  • FIG. 5A is another schematic diagram of the pre-coder 220 and the ODB encoder/bit-separator 230 shown in FIG. 2 .
  • the ODB encoder/bit-separator 230 further comprises a LPF (low-pass-filter) 237 and the first and second LIA 235 and 236 .
  • the bandwidth of the LPF 237 could be set between 25% and 65% of data rate.
  • the output signal cf(t) 238 of the LPF 237 would be a four-level signal, with shorter pulses having lower amplitudes than those in the conventional art.
  • the output signal cf(t) 238 is treated as an AC signal, which swings in the range from ⁇ 0.5 to +0.5, and splits into the one input of the first LIA 235 and another input for the second LIA 236 .
  • the output of the first LIA 235 could be substantially similar to the output of the first AND gate 231 .
  • the output of the second LIA 236 could be substantially similar to the output of the second AND gate 232 shown in FIG. 3A .
  • FIG. 5B is a timing diagram illustrating signals in each stage of the schematic shown in FIG. 5A .
  • the NRZ input signal d(t) 210 there are six timing sequences, the NRZ input signal d(t) 210 , c(t) 221 , cf(t) 238 , c 1 (t) 231 , c 2 (t) 232 , and the final output I(t) 251 .
  • the third timing sequence cf(t) 238 the rest of five sequences are similar to those shown in FIG. 3B and 4B . It is assumed that the bandwidth of the LPF 237 is set to be 50% of data rate and the magnitude of the signal is expanded by a factor of 2 for illustration.
  • a dash line 510 is used to mark the threshold level, +0.33, for the first and second LIA 235 and 236 , by assuming that the signal, cf(t) 238 , swings in the range of ⁇ 0.5 to +0.5.
  • the timing sequence, I(t) 251 is the optical output of the dual drive MZ modulator 250 .
  • FIG. 6A is another schematic diagram of the pre-coder 220 and the ODB encoder/bit-separator 230 shown in FIG. 2 .
  • the encoder/bit-separator 230 comprises a first and a second LPF 601 and 602 , that receive the complementary outputs c(t) 221 and c(t) 222 as inputs, respectively.
  • the bandwidth of both LPF 601 and 602 can be set between 25% and 65% of the data rate.
  • Both of the output signals cf(t) 603 and cf(t) 604 are four-level signals and treated as AC signals, swinging in the range from ⁇ 0.5 to +0.5.
  • Both cf(t) 603 and cf(t) 604 are sent to the first and second LIA 235 and 236 , which have a common positive threshold, respectively.
  • the output of the first LIA 235 could be substantially similar to the output of the first AND gate 231 .
  • the output of the second LIA 236 could be substantially similar to the output of the second AND gate 232 shown in FIG. 3A .
  • the bandwidth of the first and second LIA 235 and 236 are set to be 50% of the data rate and the common threshold is set at +0.33
  • the resulting timing sequences diagram of this embodiment would be substantially similar to that in FIG. 5B .
  • FIG. 6B is yet another schematic diagram of the pre-coder 220 and the ODB encoder/bit-separator 230 shown in FIG. 2 .
  • This embodiment is essentially identical to that shown in FIG. 6A , except that the two LPF 601 and 602 are substituded by two unbalanced MZ interferometer filters.
  • An unbalanced MZ interferometer filter is formed by first splitting an input signal to two signals, with each passing a path with unequal length, and then recombining the two splitted signals. The unequal length causes a relative delay, ⁇ t, between the signals. Similar to the embodiment shown in FIG. 3A , the time delay, ⁇ t, in this embodiment can range from 0.3 to 1 bit period.
  • the output of the first LIA 235 could be substantially similar to the output of the first AND gate 231 .
  • the output of the second LIA 236 could be substantially similar to the output of the second AND gate 232 shown in FIG. 3A .
  • ⁇ t is set to 0.7 bit period, the resulting timing sequences diagram of this embodiment would be substantially similar to that in FIG. 4B .
  • FIG. 7 contains diagrams a) to m) for showing signal distortions of a positive chirped, a negative chirped, and a chirp free 10 Gbps ODB signals at various distances.
  • the four columns show eye diagrams at 0 km, 100 km, 200 km, and 250 km from left to right.
  • the three rows show eye diagrams of the positive chirped, the negative chirped, and the chirp free ODB signals.
  • the driving voltage for the MZ modulator 250 is 0.5 V ⁇
  • the positive chirped (from a) to d)) and negative chirped (from e) to h)) ODB signals are generated according to the embodiments shown in FIG. 2 , using AND gates for illustration purpose with the understanding that the results of the rest three embodiments are substantially similar to these two rows. It is clear from observing these eye diagrams to conclude that the positive chirped ODB signal could reduce signal distortion at longer distances.
  • the present invention offers longer transmission distance and better tolerance to non-linear effects than conventional art. Furthermore, using a single modulator is much simpler and economical than those conventional methods using double optical modulations. It also makes practical implementation of chirped ODB signals possible.
US11/283,177 2005-11-18 2005-11-18 Method and apparatus for generating optical duo binary signals with frequency chirp Abandoned US20070116476A1 (en)

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US11/283,177 US20070116476A1 (en) 2005-11-18 2005-11-18 Method and apparatus for generating optical duo binary signals with frequency chirp
PCT/CN2006/003114 WO2007056959A1 (en) 2005-11-18 2006-11-20 Method and apparatus for generating optical duo binary signals with frequency chirp
EP06817852A EP1955451B1 (en) 2005-11-18 2006-11-20 Method and apparatus for generating optical duo binary signals with frequency chirp
CN2006800432047A CN101313496B (zh) 2005-11-18 2006-11-20 产生带频率啁啾的光双二进制信号的方法和装置
US13/113,733 US8311416B2 (en) 2005-11-18 2011-05-23 Method and apparatus for generating optical duo binary signals with frequency chirp

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