JPH0656940B2 - Logarithmic amplifier circuit - Google Patents
Logarithmic amplifier circuitInfo
- Publication number
- JPH0656940B2 JPH0656940B2 JP61136664A JP13666486A JPH0656940B2 JP H0656940 B2 JPH0656940 B2 JP H0656940B2 JP 61136664 A JP61136664 A JP 61136664A JP 13666486 A JP13666486 A JP 13666486A JP H0656940 B2 JPH0656940 B2 JP H0656940B2
- Authority
- JP
- Japan
- Prior art keywords
- amplifier circuit
- logarithmic amplifier
- transistors
- differential
- logarithmic
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
Links
Description
【発明の詳細な説明】 〔産業上の利用分野〕 本発明は対数増幅回路に関し、特にMOS集積回路にお
ける対数増幅回路に関する。The present invention relates to a logarithmic amplifier circuit, and more particularly to a logarithmic amplifier circuit in a MOS integrated circuit.
〔従来の技術〕 従来、この種の対数増幅回路は第3図に示すように、バ
イポーラ集積回路においては実現されているが、MOS
集積回路においては存在しなかった。[Prior Art] Conventionally, a logarithmic amplifier circuit of this type has been realized in a bipolar integrated circuit as shown in FIG.
It did not exist in integrated circuits.
上述した従来の対数増幅回路はバイポーラ集積回路とな
っているので、MOS集積回路上には集積化出来ないと
いう欠点があり、例えば対数IF増幅器を構成した場合
にベースバンド部をバイポーラ集積回路で構成すると消
費電流が多くなるという欠点があった。Since the conventional logarithmic amplifier circuit described above is a bipolar integrated circuit, it has the drawback that it cannot be integrated on a MOS integrated circuit. For example, when a logarithmic IF amplifier is constructed, the baseband section is constructed by the bipolar integrated circuit. Then, there is a drawback that the current consumption increases.
本発明の対数増幅回路は、縦続接続された多段のMOS
型差動増幅器の初段入力または各段出力にはそれぞれト
ランジスタのゲート幅Wとゲート長Lの比W/Lが、差
動対を構成する2つのトランジスタでは1/k(k>
1)である等しい2対の差動対が、互いに入力が逆であ
り、かつ、トランジスタのW/Lが等しいトランジスタ
のドレインがそれぞれ共通に接続されており、前記全て
の2対の差動対の各々の同相出力が共通に接続されてい
ることを特徴とする。A logarithmic amplifier circuit according to the present invention is a cascade-connected multistage MOS.
The ratio W / L of the gate width W and the gate length L of each transistor is input to the first stage input or each stage output of the differential amplifier, and is 1 / k (k>
The two differential pairs, which are equal to each other in 1), have mutually opposite inputs, and the drains of the transistors having the same W / L are connected in common. The in-phase outputs of the above are commonly connected.
次に、本発明について図面を参照して説明する。 Next, the present invention will be described with reference to the drawings.
第1図は本発明の一実施例を示す回路図である。第1図
において、カレントソースI01,I02,…,I0nで駆
動される差動対はそれぞれ順次縦続接続されている。カ
レントソースI11,I22,…,In,n+1の2つずつ
で駆動されている2対の差動対は2乗両波整流器となる
ことを式で示す。FIG. 1 is a circuit diagram showing an embodiment of the present invention. In FIG. 1, the differential pairs driven by the current sources I 01 , I 02 , ..., I 0n are sequentially connected in cascade. It is shown by an equation that the two differential pairs driven by two current sources I 11 , I 22 , ..., I n , n + 1 are square-wave double-wave rectifiers.
α=μn(C0x/2)(W1/L1) (1) (ここでμnはモビリティ、C0xはゲート酸化膜容
量。W1,L1はトランジスタT11のゲート幅Wとゲー
ト長L。α = μ n (C 0x / 2) (W 1 / L 1 ) (1) (where μ n is the mobility, C 0x is the gate oxide film capacitance. W 1 and L 1 are the gate width W and the gate of the transistor T11. Long L.
k=(W2/L2)/(W1/L1) (2) (ここでW2,L2はトランジスタT1kのゲート幅Wと
ゲート長L。)とおく。トランジスタT11,T1kか
ら成る一対の差動対において、それぞれのゲート、ソー
ス間電圧をVgs1,Vgs2,およびスレッショルド電圧をV
tとおくと I1=α(Vgs1−Vt)2 (3) I2=kα(Vgs2−Vt)2 (4) I3=α(Vgs3−Vt)2 (5) I4=kα(Vgs4−Vt)2 (6) と表わせる。ここで I1+ I2 = I11 (7) I3+ I4 = I11 (8) V1N=Vgs1 −Vgs2 =Vgs4 −Vgs3 (9) と表わせるので、 と求まる。(11)式により電流ΔI1は入力電圧VINに
対して2乗両波整流特性を有することがわかる。同様に (11)式から(13)式で示されるΔI1,ΔI2,…,Δ
In+1 の値は −2I11≦ΔI1≦2I11 (14) −2I22≦ΔI2≦2I22 (15) −2Inn+1≦ΔIn+1 ≦2Inn+1 (16) であることは明らかであるから、I1N,V1,…,VOUT
の値がいくら大きくなっても(14)式から(16)式で
示される値に入る。またV1,…,VOUT は差動増幅器
の出力となっているら入力信号V1Nが次第に大きくな
るとVOUT から順次V1までの出力が飽和して行く。k = (W 2 / L 2 ) / (W 1 / L 1 ) (2) (where W 2 and L 2 are the gate width W and the gate length L of the transistor T1k). In the pair of differential pairs composed of the transistors T11 and T1k, the gate-source voltage is V gs1 , V gs2 , and the threshold voltage is V gs1 .
putting a t I 1 = α (V gs1 -V t) 2 (3) I 2 = kα (V gs2 -V t) 2 (4) I 3 = α (V gs3 -V t) 2 (5) I 4 = kα (V gs4 −V t ) 2 (6) Here, I 1 + I 2 = I 11 (7) I 3 + I 4 = I 11 (8) V 1N = V gs1 −V gs2 = V gs4 −V gs3 (9) Is asked. It can be seen from the equation (11) that the current ΔI 1 has a square-wave double-wave rectification characteristic with respect to the input voltage V IN . As well ΔI 1 , ΔI 2 , ..., Δ shown in equations (11) to (13)
The value of I n + 1 is −2I 11 ≦ ΔI 1 ≦ 2I 11 (14) −2I 22 ≦ ΔI 2 ≦ 2I 22 (15) −2I nn + 1 ≦ ΔI n + 1 ≦ 2I nn + 1 (16) Since it is clear that there is I 1N , V 1 , ..., V OUT
No matter how large the value of becomes, it enters the value shown by the equation (14) to the equation (16). If V 1 , ..., V OUT are outputs of the differential amplifier, the output from V OUT to V 1 is sequentially saturated when the input signal V 1N is gradually increased.
従ってトランジスタT10,T20;T30,T40;T50,T
60により IOUT =ΔI1+ΔI2+…+ΔIn+1 (17) とすると出力電流IOUT は差動増幅器の最大出力電圧を
カレントソースI01,I02,…I0Nおよび抵抗R01,
R02,…R0nを設定することで一定符号の値に出来
る。Therefore, the transistors T 10 , T 20 ; T 30 , T 40 ; T 50 , T
Assuming that I OUT = ΔI 1 + ΔI 2 + ... + ΔI n + 1 (17) by 60 , the output current I OUT is the maximum output voltage of the differential amplifier as current sources I 01 , I 02 , ... I 0N and resistor R 01 ,
By setting R 02 , ... R 0n , a constant code value can be obtained.
よって出力電流IOUT 特性は第2図に示すように入力信
号V1Nに対して近似的に対数特性にすることが出来
る。Therefore, the output current I OUT characteristic can be approximately logarithmic characteristic with respect to the input signal V 1N as shown in FIG.
以上説明したように本発明は、MOS集積回路において
対数増幅器を実現出来る効果があ、例えば対数IF増幅
器を構成すればIF以後を1チップのMOS集積回路上
に実現出来、低消費電流化を図れる効果がある。As described above, the present invention has the effect of realizing a logarithmic amplifier in a MOS integrated circuit. For example, if a logarithmic IF amplifier is configured, the parts after IF can be realized on a one-chip MOS integrated circuit, and low current consumption can be achieved. effective.
【図面の簡単な説明】 第1図は本発明の一実施例を示す回路図、第2図は第1
図の特性図、第3図は従来例を示す回路図である。 T01,T0n,T11,Tn+1,1,Tn+1,k,T10,…,T
60……トランジスタ、R01,…,R0n……抵抗、T01,
…,I0n,I11,…,In,n+1……カレントソース。BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a circuit diagram showing an embodiment of the present invention, and FIG.
FIG. 3 is a characteristic diagram and FIG. 3 is a circuit diagram showing a conventional example. T 01 , T 0n , T 11 , T n + 1 , 1 , T n + 1 , k , T 10 , ..., T
60 …… Transistor, R 01 ,…, R 0n …… Resistor, T 01 ,
..., I 0n , I 11 , ..., I n , n + 1 ... Current source.
Claims (1)
の初段入力または各段出力にはそれぞれトランジスタの
ゲート幅Wとゲート長Lの比W/Lが、差動対を構成す
る2つのトランジスタでは1/k(k>1)である等し
い2対の差動対が、互いに入力が逆であり、かつ、トラ
ンジスタのW/Lが等しいトランジスタのドレインがそ
れぞれ共通に接続されており、前記全ての2対の差動対
の各々の同相出力が共通に接続されていることを特徴と
する対数増幅回路。1. A ratio W / L of a gate width W of a transistor to a gate length L of two transistors forming a differential pair in a first stage input or each stage output of a cascaded multistage MOS differential amplifier. In the transistors, two equal differential pairs of 1 / k (k> 1) have mutually opposite inputs, and the drains of the transistors having the same W / L are connected in common. A logarithmic amplifier circuit, in which in-phase outputs of all two pairs of differential pairs are commonly connected.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP61136664A JPH0656940B2 (en) | 1986-06-11 | 1986-06-11 | Logarithmic amplifier circuit |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP61136664A JPH0656940B2 (en) | 1986-06-11 | 1986-06-11 | Logarithmic amplifier circuit |
Publications (2)
Publication Number | Publication Date |
---|---|
JPS62292010A JPS62292010A (en) | 1987-12-18 |
JPH0656940B2 true JPH0656940B2 (en) | 1994-07-27 |
Family
ID=15180608
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP61136664A Expired - Lifetime JPH0656940B2 (en) | 1986-06-11 | 1986-06-11 | Logarithmic amplifier circuit |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPH0656940B2 (en) |
Families Citing this family (6)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2643516B2 (en) * | 1990-02-01 | 1997-08-20 | 日本電気株式会社 | Logarithmic amplifier circuit |
JP2687713B2 (en) * | 1990-10-30 | 1997-12-08 | 日本電気株式会社 | Logarithmic amplifier circuit |
CA2069243C (en) * | 1991-05-23 | 1997-08-19 | Katsuji Kimura | Logarithmic intermediate-frequency amplifier |
JP2827826B2 (en) * | 1993-07-13 | 1998-11-25 | 日本電気株式会社 | Logarithmic amplifier circuit |
JP2836452B2 (en) * | 1993-07-14 | 1998-12-14 | 日本電気株式会社 | Logarithmic amplifier circuit |
JP2778540B2 (en) * | 1995-07-18 | 1998-07-23 | 日本電気株式会社 | Logarithmic amplifier circuit |
-
1986
- 1986-06-11 JP JP61136664A patent/JPH0656940B2/en not_active Expired - Lifetime
Also Published As
Publication number | Publication date |
---|---|
JPS62292010A (en) | 1987-12-18 |
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Legal Events
Date | Code | Title | Description |
---|---|---|---|
EXPY | Cancellation because of completion of term |