JP5691565B2 - Drive circuit and switching power supply device - Google Patents

Description

  The present invention relates to a drive circuit for driving a semiconductor switching element and a switching power supply device.

 As a conventional technique, a gate drive circuit for a switching element described in Patent Document 1 is known. FIG. 7 shows an example of a gate drive circuit for a switching element described in Patent Document 1. In this gate drive circuit, the output stage of the gate drive circuit connected to the drive / protection circuit 51 and the gate of the IGBT 31 includes a gate resistor 41, an NPN transistor 42, and a PNP transistor 43.

 Further, the gate drive circuit is provided with a gate voltage determiner 52 that determines the voltage of the gate of the IGBT 31 and a main circuit current determiner 53 that determines the IGBT current flowing in the main circuit of the IGBT 31. When the main circuit current is large, the main circuit current determining unit 53 determines that the main circuit current is large, and the gate voltage determining unit 52 turns on the PMOSFET 44 during the mirror period to turn on the gate. The resistance is reduced and the gate current is controlled.

JP 2007-228447 A

    However, in the example described in Patent Document 1 shown in FIG. 7, the main circuit current and the gate voltage of the switching element are detected, the gate current is adjusted based on the detected value, and the switching loss of the switching element is reduced. . For this reason, a means for detecting the main circuit current and the gate voltage of the switching element is necessary.

  An object of the present invention is to provide a drive circuit and a switching power supply device that can reduce the switching loss of the switching element by adjusting the gate current of the switching element without detecting the main circuit current and gate voltage of the switching element. There is.

In order to solve the above problems, a drive circuit of the present invention is connected between a control circuit that generates a control signal for controlling an on period and an off period of a switching element based on a feedback signal and the switching element, A drive circuit for supplying a gate current to a gate of the switching element, wherein the gate current of the drive circuit in the on period of the control signal is generated only for a predetermined period, and the feedback signal A combined current of a second current component obtained by combining a current generated based on the predetermined period and a current generated only for a predetermined period until the gate voltage of the switching element rises to the gate threshold voltage. It is characterized by that.

The switching power supply device of the present invention includes a switching element that intermittently supplies a DC voltage of a DC power supply to supply to a primary winding of a transformer, a rectifying and smoothing circuit that rectifies and smoothes a voltage generated in a secondary winding of the transformer, A control circuit that generates a control signal that controls an on period and an off period of the switching element based on the feedback signal, and a signal indicating the output voltage of the rectifying and smoothing circuit, the control circuit, and the switching element, And a drive circuit that supplies a gate current to the gate of the switching element, and the gate current of the drive circuit in the ON period of the control signal is generated only for a predetermined period. One current component, a current of a predetermined period generated based on the feedback signal, and the switching element Gate voltage, characterized in that the combined current of the second current component obtained by synthesizing the current generated by a predetermined time to increase the gate threshold voltage of the.

According to the present invention, the gate current in the ON period of the control signal that controls the ON period and the OFF period of the switching element based on the feedback signal is generated based on the first current component generated for a predetermined period and the feedback signal. A combined current of a second current component obtained by combining the current generated for a predetermined period and the current generated only for the predetermined period until the gate voltage of the switching element rises to the gate threshold voltage , It is possible to provide a drive circuit and a switching power supply device that can reduce the switching loss of the switching element.

1 is a configuration diagram of a switching power supply device having a drive circuit of Example 1. FIG. FIG. 6 is a diagram illustrating operation waveforms of respective units of the drive circuit according to the first embodiment. 6 is a configuration diagram of a switching power supply device having a drive circuit according to Embodiment 2. FIG. FIG. 10 is a diagram illustrating operation waveforms of respective units of the drive circuit according to the second embodiment. FIG. 6 is a configuration diagram of a switching power supply device having a drive circuit according to a third embodiment. FIG. 10 is a diagram illustrating operation waveforms of respective parts of the drive circuit according to the third embodiment. It is a block diagram which shows an example of the gate drive circuit of the conventional switching element.

  Hereinafter, a drive circuit and a switching power supply according to an embodiment of the present invention will be described in detail with reference to the drawings.

  The drive circuit according to the present invention is characterized in that the switching loss of the switching element is reduced by adjusting the gate current of the switching element in accordance with the signal value of the feedback signal. One embodiment will be described.

 FIG. 1 is a configuration diagram of a switching power supply device having a drive circuit according to the first embodiment. In the drive circuit of the first embodiment, a signal indicating the output voltage of the rectifying / smoothing circuit that rectifies and smoothes the voltage generated in the secondary winding S1 of the transformer T1 is used as the feedback signal FB. The resistor R6 is selected by the signal value of the feedback signal FB, and the gate current of the switching element Q1 is adjusted. A control signal for controlling the on period and the off period of the switching element Q1 is generated based on the feedback signal FB.

 In the switching power supply apparatus shown in FIG. 1, a series circuit of a primary winding P1 of a transformer T1 and a switching element Q1 made of a GaN FET of a gallium nitride (GaN) device is connected to both ends of a DC power supply V1.

  The anode of the diode D2 is connected to one end of the secondary winding S1 of the transformer T1, the cathode of the diode D2 and one end of the capacitor C3 are connected to one end (+ Vo) of the output terminal, and the other end of the capacitor C3 is output The other end (−Vo) of the terminal is connected to the other end of the secondary winding S1. The diode D2 and the capacitor C3 constitute a rectifying / smoothing circuit. A load (not shown) is connected to the output terminals (+ Vo, −Vo).

  The anode of the diode D4 is connected to one end of the auxiliary winding P2 of the transformer T1, the cathode of the diode D4 is connected to one end of the capacitor C1, and the other end of the auxiliary winding P2 is connected to the other end of the capacitor C1 and the DC power source V1. Is connected to the negative electrode.

  A starting resistor R0 is connected between the positive electrode of the DC power supply V1 and one end of the capacitor C1. A series circuit of a current source Ia and a resistor R7 is connected to both ends of the capacitor C1, and a series circuit of a transistor Q3, a resistor R3, a resistor R5, and a transistor Q2 is connected to both ends of the capacitor C1.

  The voltage detection circuit 11 detects the output voltage of the capacitor C3, outputs a signal indicating the output voltage to the current source Ia as the feedback signal FB, and the current source Ia according to the current value of the feedback signal FB (feedback current IFB). The current value of is variable.

  The inverting input terminal (−) of the comparator CMP1 is connected to the connection point between the current source Ia and the resistor R7, and the oscillator OSC is connected to the non-inverting input terminal (+) of the comparator CMP1. The oscillator OSC generates a triangular wave signal and outputs the triangular wave signal to the comparator CMP1.

  The comparator CMP1 compares the triangular wave signal from the oscillator OSC with the voltage (feedback voltage) generated by the current corresponding to the feedback signal FB flowing through the resistor R7, thereby controlling the ON period according to the feedback signal FB. Generate a signal.

 The output terminal of the comparator CMP1 is connected to the connection point between the resistors R3 and R5 and the gate (control terminal) of the switching element Q1 via the resistor R4. The output terminal of the comparator CMP1 is connected to the base of the transistor Q2 via the inverter INV2. The output terminal of the comparator CMP1 is connected to one input terminal of the AND circuit AND1, one input terminal of the AND circuit AND2, and one end of the resistor R1.

 The connection point between the current source Ia and the resistor R7 is connected to the other input terminal of the AND circuit AND2 via the inverter INV1, and the output terminal of the AND circuit AND2 is connected to the gate of the switching element Q1 via the resistor R6 and the diode D3. It is connected.

 The other end of the resistor R1 is connected to one end of the capacitor C2 and the other input terminal of the AND circuit AND1 via the inverter G1, and the output terminal of the AND circuit AND1 is connected to the transistor Q3 via a parallel circuit of the resistor R2 and the diode D1. Connected to the base.

 The voltage detection circuit 11, the current source Ia, the resistor R7, the oscillator OSC, and the comparator CMP1 constitute a control circuit that generates a control signal for controlling the on period (ton) and the off period (toff) of the switching element Q1. . In addition, the resistors R1 to R3, the capacitor C2, the inverter G1, the AND circuit AND1, the diode D1, and the transistor Q3 have a predetermined period shorter than the ON period, for example, until the gate voltage of the switching element Q1 rises to the gate threshold voltage. A period is set in advance, and a first current component generation circuit that generates a first current component only during the set period is configured. The inverter INV1, the AND circuit AND2, the resistor R6, the diode D3, and the resistor R4 are based on the feedback current IFB. A second current component generation circuit that generates a second current component is configured, and the inverter INV2, the transistor Q2, and the resistor R5 configure an off-gate current generation circuit that generates a gate current in an off period. The drive circuit 10 includes a first current component generation circuit, a second current component generation circuit, and an off-gate current generation circuit. The first current component generation circuit and the second current component generation circuit constitute an on-gate current generation circuit that generates a gate current during the on period.

 Next, the operation of the drive circuit and the switching power supply apparatus according to the first embodiment configured as described above will be described in detail with reference to operation waveforms shown in FIG.

 First, at the time of heavy load (before time t7), the feedback current IFB from the voltage detection circuit 11 becomes small as shown in FIG.

 The feedback current IFB is converted into a feedback voltage by the resistor R7. When the feedback voltage and the triangular wave signal are compared by the comparator CMP1 and an H level output is output to the AND circuit AND1, the transistor Q3 is turned on at time t1. .

 Further, since the feedback voltage is less than the threshold voltage of the inverter INV1, the output of the inverter INV1 is at the H level. When this H level output is input to the AND circuit AND2, the AND circuit AND2 outputs an H level, so that the diode D3 becomes conductive. For this reason, the gate current Ig1 of the switching element Q1 is a combined current of the current flowing through the resistor R3, the current flowing through the resistor R4, and the current flowing through the resistor R6. The current flowing through the resistor R3 corresponds to the first current component, and the sum of the currents flowing through the resistors R4 and R6 corresponds to the second current component.

 Next, when the voltage of the capacitor C2 exceeds the threshold voltage of the inverter G1 at time t2, since the inverter G1 outputs an L level output to the AND circuit AND1, the output of the AND circuit AND1 becomes L level, and the transistor Q3 is turned on. Turn off. For this reason, the gate current Ig2 of the switching element Q1 is a combined current of the current flowing through the resistor R4 and the current flowing through the resistor R6.

 The combined resistance of the parallel circuit is smaller than the resistance R4. For this reason, at times t2 to t3, a larger gate current Ig2 becomes the gate current of the switching element Q1 than when only the resistor R4 is used.

 Next, at time t3 to t4, when the comparator CMP1 outputs L level, the inverter INV2 outputs H level by this L level output, so that the transistor Q2 is turned on and the gate current of the switching element Q1 is zero. Become. The operation at the time of heavy load is also performed at times t4 to t6.

 Next, when the load is light (after time t7), the feedback current IFB from the voltage detection circuit 11 increases as shown in FIG. This feedback current IFB is converted into a feedback voltage by the resistor R7. When the feedback voltage and the triangular wave signal are compared by the comparator CMP1 and an H level output is output to the AND circuit AND1, the transistor Q3 is turned on at time t8. To do.

 Further, since the feedback voltage exceeds the threshold voltage of the inverter INV1, the output of the inverter INV1 becomes L level. When this L level output is input to the AND circuit AND2, the output of the AND circuit AND2 becomes L level, so that the series circuit of the resistor R6 and the diode D3 is opened.

 For this reason, the gate current Ig3 of the switching element Q1 is a combined current of the current flowing through the resistor R3 and the current flowing through the resistor R4.

 Next, when the voltage of the capacitor C2 exceeds the threshold voltage of the inverter G1 at time t9, the inverter G1 outputs an L level output to the AND circuit AND1, so the output of the AND circuit AND1 becomes L level, and the transistor Q3 Turn off. For this reason, the gate current Ig4 of the switching element Q1 becomes a current flowing through the resistor R4. The gate current Ig4 at times t9 to t10 is smaller than the gate current Ig2 at times t2 to t3.

 Thus, according to the drive circuit of the first embodiment, the signal indicating the output voltage of the rectifying / smoothing circuit that rectifies and smoothes the voltage generated in the secondary winding S1 of the transformer T1 is used as the feedback signal FB. Since the resistor R6 is selected based on the signal value and the gate current of the switching element Q1 is adjusted, the switching loss of the switching element can be reduced.

 Further, according to the switching power supply device of the first embodiment, the effect of the drive circuit can be obtained, and the DC voltage of the DC power supply V1 is turned on / off by the switching element Q1 through the primary winding P1 of the transformer T1, and the secondary power supply is obtained. The voltage generated in the winding S1 can be rectified and smoothed by the diode D2 and the capacitor C3 to obtain a stable DC output voltage. Further, the voltage generated in the auxiliary winding P2 can be rectified and smoothed by the diode D4 and the capacitor C1, and supplied as a power source for the control circuit and the drive circuit 10.

  FIG. 3 is a configuration diagram of a switching power supply device having a drive circuit according to the second embodiment. The drive circuit of the second embodiment shown in FIG. 3 differs from the drive circuit shown in FIG. 1 in the following points. The inverter INV1, the AND circuit AND2, the resistors R4 and R6, and the diode D3 shown in FIG. 1 are deleted, and an inverter INV3, a diode D5, resistors R8 and R9, transistors Q4 to Q6, and a capacitor C4 are provided instead. To do.

 In the drive circuit of the second embodiment, a signal indicating the output voltage of the rectifying / smoothing circuit that rectifies and smoothes the voltage generated in the secondary winding S1 of the transformer T1 is used as the feedback signal FB. The time constant circuit is activated by the signal value of the feedback signal FB, and the gate current of the switching element Q1 is adjusted. A control signal for controlling the on period and the off period of the switching element Q1 is generated based on the feedback signal FB.

  One end of the parallel circuit of the diode D5 and the resistor R8 is connected to the output terminal of the comparator CMP1 via the inverter INV3, and the other end of the parallel circuit is connected to the negative electrode of the DC power source V1 via the capacitor C4. At the same time, it is connected to one end of the resistor R9.

  The source of the transistor Q4 and the emitters of the transistors Q5 and Q6 are connected to one end of the capacitor C1.

  The gate of the transistor Q4 is connected to the output terminal of the comparator CMP1, and the drain of the transistor Q4, the collector of the transistor Q5, and the bases of the transistors Q5 and Q6 are connected to the other end of the resistor R9. The collector of the transistor Q6 is connected to the collector of the transistor Q2 via the resistor R5.

 The transistor Q4 functions as a switch that prevents the current mirror circuits Q5 and Q6 from operating during the OFF period of the switching element Q1.

 Next, the operation of the drive circuit and the switching power supply device of the second embodiment configured as described above will be described in detail with reference to operation waveforms shown in FIG.

 First, when the switching element Q1 is turned on, that is, at time t1, the output of the comparator CMP1 becomes H level, the transistor Q3 is turned on, and a gate current flows through the gate of the switching element Q1.

 Further, since the output of the inverter INV3 becomes L level, the capacitor C4 is discharged with a time constant determined by the time constant circuit of the capacitor C4 and the resistor R8, and the voltage Vc4 across the capacitor C4 decreases.

 For this reason, when the voltage between the voltage Vc4 and the collector of the transistor Q5 changes, the value of the current Ic flowing through the resistor R9 varies. In this example, the current Ic increases from time t1 to time t3. The variable current Ic is supplied to the gate of the switching element Q1 through the current mirror circuits Q5 and Q6. When the ON period of the switching element Q1 is short, the base current through the current mirror circuits Q5 and Q6 is reduced, and the power of the drive circuit 10a can be reduced. The collector current of transistor Q6 corresponds to the second current component. At time t2, transistor Q3 is turned off.

 Next, when the switching element Q1 is turned off, that is, at time t3, the output of the comparator CMP1 becomes L level, and the current mirror circuits Q5 and Q6 stop operating. Further, since the output of the inverter INV3 becomes H level, the capacitor C4 is charged via the diode D5. For this reason, the current Ic flowing through the capacitor C4 via the transistor Q5 and the resistor R9 is almost zero.

 In addition, in the gate current of the switching element Q1, from time t1 to t3, the gate current at heavy load is shown, from time t4 to t6, the gate current at medium load is shown, and from time t7 to t9, the light load is shown. The gate current is shown. As the heavy load changes to the light load, the feedback current IFB increases, so that the voltage generated across the resistor R7 increases.

 For this reason, the ON period (ton) of the control signal output from the comparator CMP1 is shortened and the discharge time of the capacitor C4 is shortened, so that the current Ic is reduced and the gate current is reduced.

 Thus, according to the drive circuit of the second embodiment, a signal indicating the output voltage of the rectifying / smoothing circuit that rectifies and smoothes the voltage generated in the secondary winding S1 of the transformer T1 is used as the feedback signal FB. The time constant circuit (R8, C4) is actuated by the signal value and the gate current of the switching element Q1 is adjusted, whereby the switching loss of the switching element can be reduced.

 Further, according to the switching power supply device of the second embodiment, the same effect as that of the switching power supply device of the first embodiment can be obtained.

 FIG. 5 is a configuration diagram of a switching power supply device having a drive circuit according to the third embodiment. The drive circuit according to the third embodiment shown in FIG. 5 differs from the drive circuit shown in FIG. 3 in the following points. The inverter INV3, the diode D5, the resistor R8, and the capacitor C4 shown in FIG. 3 are omitted, and instead, a current source Ib and resistors R10 and R11 are provided.

 In the drive circuit of the third embodiment, a signal indicating the output voltage of the rectifying / smoothing circuit that rectifies and smoothes the voltage generated in the secondary winding S1 of the transformer T1 is used as the feedback signal FB. The gate current of the switching element Q1 is adjusted in inverse proportion to the signal value of the feedback signal FB. A control signal for controlling the on period and the off period of the switching element Q1 is generated based on the feedback signal FB.

 The current source Ib varies the current according to the signal value of the feedback signal FB from the voltage detection circuit 11. The power source Vcc is connected to one end of the current source Ib, the other end of the current source Ib is connected to one end of the resistor R9 and one end of the resistor R10 via the resistor R11, and the other end of the resistor R10 is connected to the negative electrode of the DC power source V1. It is connected.

 Next, the operation of the drive circuit and the switching power supply device according to the third embodiment configured as described above will be described in detail with reference to operation waveforms shown in FIG.

 In the gate current of the switching element Q1 shown in FIG. 6, the gate current at the time of heavy load is shown at times t1 to t3, the gate current at the time of medium load is shown at times t5 to t7, and the light load is shown at times t9 to t11. The gate current is shown.

 First, the feedback current IFB from the voltage detection circuit 11 is converted into a voltage by the resistor R7.

 At the time of heavy load (time t1 to t3), the feedback current IFB is small, so that the voltage drop in the resistor R7 becomes smaller. Further, since the feedback current IFB is small, a smaller current flows through the current source Ib. For this reason, since the current flowing from the current source Ib to the resistor R10 via the resistor R11 is small, the voltage across the resistor R10 becomes small. For this reason, since the voltage across the resistor R9 becomes larger, the gate current flowing to the gate of the switching element Q1 via the current mirror circuits Q5 and Q6 becomes larger.

 Further, at the time of light load (time t9 to t11), since the feedback current IFB is large, the voltage drop at the resistor R7 becomes larger. Further, since the feedback current IFB is large, a larger current flows through the current source Ib. For this reason, since the current flowing from the current source Ib to the resistor R10 via the resistor R11 increases, the voltage across the resistor R10 increases. For this reason, since the voltage across the resistor R9 becomes smaller, the gate current flowing to the gate of the switching element Q1 via the current mirror circuits Q5 and Q6 becomes smaller.

 Note that the current flowing through the transistor Q3 is superimposed on the gate current at times t1 to t2, times t5 to t6, and times t9 to t10.

 Thus, according to the drive circuit of the third embodiment, the signal indicating the output voltage of the rectifying / smoothing circuit that rectifies and smoothes the voltage generated in the secondary winding S1 of the transformer T1 is used as the feedback signal FB. The switching loss of the switching element can be reduced by adjusting the gate current of the switching element Q1 in inverse proportion to the signal value.

 Further, according to the switching power supply device of the third embodiment, the same effect as the switching power supply device of the first embodiment can be obtained.

 The present invention is not limited to the drive circuit and the switching power supply device according to the first to third embodiments described above. In the first to third embodiments, the flyback converter is exemplified as the switching power supply device. However, the present invention can be applied to, for example, a forward converter and a resonant converter.

 The present invention can also be applied to a step-up chopper circuit, a step-down chopper circuit, a synchronous rectifier circuit, and the like.

 In the first to third embodiments, the signal indicating the output voltage of the flyback converter is also a signal indicating the light weight of the load, so that the feedback signal is used. Any signal that can generate a control signal to be controlled can be a feedback signal.

  The present invention is applicable to a power supply device.

V1 DC power source T1 Transformer P1 Primary winding P2 Auxiliary winding S1 Secondary winding Q1 Switching element Q2 to Q6 Transistor OSC Oscillator INV1, INV2, INV3, G1 Inverter Ia, Ib Current source CMP1 Comparator D1-D5 Diode C1-C4 Capacitor R0 Starting resistor R1 to R11 Resistor 10.10a, 10b Drive circuit 11 Voltage detection circuit AND1, AND2 AND circuit

Claims (4)

A drive circuit that is connected between a control circuit that generates a control signal for controlling an on period and an off period of a switching element based on a feedback signal and supplies the gate current to the gate of the switching element. And
The gate current of the drive circuit in the ON period of the control signal, a first current component generated for a predetermined duration, and current of a predetermined period is generated based on the feedback signal, the switching element A drive circuit characterized in that a combined current with a second current component obtained by combining a current generated only for a predetermined period until the gate voltage rises to a gate threshold voltage .   The drive circuit according to claim 1, wherein the current value of the second current component is adjusted by selecting a resistance value according to a signal value of the feedback signal. 2. The drive circuit according to claim 1, wherein the current value of the second current component is adjusted to be inversely proportional to the signal value of the feedback signal. A switching element that intermittently supplies the DC voltage of the DC power supply and supplies it to the primary winding of the transformer;
A rectifying and smoothing circuit for rectifying and smoothing a voltage generated in the secondary winding of the transformer;
A control circuit that generates a control signal for controlling an on period and an off period of the switching element based on the feedback signal, and a signal indicating an output voltage of the rectifying and smoothing circuit;
A drive circuit connected between the control circuit and the switching element and supplying a gate current to the gate of the switching element;
4. The switching power supply device according to claim 1, wherein the drive circuit is the drive circuit according to claim 1.

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