JP4312705B2 - Quadrature demodulation error compensation method and quadrature demodulation error compensation circuit - Google Patents

Description

  The present invention relates to a method and a circuit for compensating for a phase error and an amplitude error of a quadrature demodulator used in a transmission / reception apparatus.

The quadrature demodulator is a demodulator that extracts two demodulated signals having a phase difference of 90 degrees from a modulated signal in a wireless communication receiver.
A conventional quadrature demodulator circuit diagram is shown in FIG. In FIG. 8, the modulated signal input from the input terminal 47 is input to the quadrature demodulator 50. This input signal is divided into two, and one signal is multiplied by the output signal of the local oscillator 53 in the mixer 51, the high frequency component is removed by the low-pass filter 55, and the signal is output to the output terminal 48 as a baseband in-phase signal. The other divided signal is input to the mixer 52, the output signal of the local oscillator 53 is multiplied by the signal whose phase is shifted by 90 degrees by the 90-degree phase shifter 54, and the high-frequency component is removed by the low-pass filter 56. And output to the output terminal 49 as a baseband in-phase signal.

  At this time, if there is a phase error or amplitude error from 90 degrees between the output signal of the local oscillator 53 input to the mixer 51 and the output of the 90-degree phase shifter 54 input to the mixer 52, the demodulation characteristics Deteriorates.

In order to compensate for the phase error and amplitude error of such a quadrature demodulator, as reported in “Non-Patent Document 1” below, between the quadrature modulator side on the transmission side and the quadrature demodulator on the reception side. It was necessary to compensate for the phase error and amplitude error in the above, or to use an ideal quadrature modulator having no phase error and amplitude error. For this reason, in order to perform high-quality transmission / reception, a relatively large and expensive device is required.
Scott A. Olson and Robert E. Stengel, “LINC Imbalance Correction using Baseband Preconditioning,” IEEE Radio and Wireless Conference (RAWCON), pp.179-182, Aug. 1999

  As described above, in order to compensate for phase and amplitude errors during transmission and reception in a conventional communication system using quadrature modulation, a means for compensating for these errors is configured on the transmission side and reception side, or phase error and amplitude are compensated. An ideal quadrature modulator having no error has to be used, which is expensive. In the present invention, it is not necessary to compensate for such a demodulation error on the modulator side, and on the demodulator, that is, on the receiver side, including the error on the modulator side, the circuit configuration is simplified and the orthogonality is low. The object is to provide a communication means.

  In order to achieve the above object, according to claim 1 of the present invention, a first mixer for inputting a reception carrier signal and a transmission modulated signal and outputting a reception in-phase baseband signal, and the reception carrier A quadrature demodulator having a second carrier for inputting a reception carrier signal given a phase difference of 90 degrees to the signal and the modulated signal and outputting a reception quadrature baseband signal; and a transmission carrier signal And the transmission in-phase baseband signal, a third mixer for outputting the in-phase modulated signal, and a transmission carrier signal and a transmission quadrature baseband signal that give a phase difference of 90 degrees to the transmission carrier signal And a fourth mixer that outputs a quadrature modulated signal and an adder that adds the in-phase modulated signal and the quadrature modulated signal and outputs a modulated signal for transmission. And equipped with A quadrature demodulation error compensation method in a receiving apparatus, wherein a known signal having a predetermined pattern is given to the quadrature modulator to obtain coefficients for giving a phase error and an amplitude error of the quadrature modulator, and the known signal The modulated signal for transmission, which is an output signal obtained from the quadrature modulator, is input to the quadrature demodulator, and the quadrature demodulator and the coefficient that give the phase error and the amplitude error of the quadrature modulator The coefficients that give the phase error and amplitude error of the quadrature demodulator are obtained from the output of the quadrature demodulator. A quadrature demodulation error compensation method for compensating for the phase error and the amplitude error of the quadrature demodulator is defined by a given coefficient.

  According to a second aspect of the present invention, the first carrier that receives the reception carrier signal and the modulated signal for transmission and outputs the reception in-phase baseband signal, and the input circuit of the reception carrier signal and the quadrature demodulator are used for the modulated signal. A quadrature demodulator having a second mixer that inputs a signal that gives a phase difference of 90 degrees to the modulated signal and outputs a received quadrature baseband signal, a transmission carrier signal, and a transmission in-phase baseband signal The third mixer that inputs and outputs the in-phase modulated signal, the transmission carrier signal and the transmission quadrature baseband signal are input, and the output signal outputs a quadrature modulated signal with a phase difference of 90 degrees. Quadrature demodulation error compensation in a transmission / reception apparatus comprising: a fourth mixer; and a quadrature modulator having an adder that adds the in-phase modulated signal and the quadrature modulated signal to output a modulated signal for transmission In the way Thus, a known signal having a predetermined pattern is given to the quadrature modulator to obtain phase error and amplitude error coefficients of the quadrature modulator, and an output obtained from the quadrature modulator to which the known signal is input The modulated signal that is a signal is input to the quadrature demodulator, and a coefficient that gives a phase error and an amplitude error of the quadrature modulator and a coefficient that gives a phase error and an amplitude error of the quadrature demodulator from the output of the quadrature demodulator At the time of signal reception, the phase error and amplitude error of the quadrature demodulator are given to the received in-phase baseband signal or the received quadrature baseband signal by the coefficients of the quadrature demodulator phase error and amplitude error. It defines a quadrature demodulation error compensation method for performing compensation processing.

  The quadrature demodulation error compensation method according to claim 1, wherein the transmission in-phase baseband signal of the known signal and the transmission quadrature baseband signal of the known signal are input to the quadrature modulator. Then, the values obtained by averaging the AC components of the in-phase modulated signal, the quadrature modulated signal, and the transmission modulated signal after squaring are obtained as the first modulated signal square mean values, respectively. The second modulated signal mean square value and the third modulated signal mean square value are obtained, and the first, second, and third modulated signal square mean values are used to calculate the quadrature modulator. A quadrature demodulation error compensation method for obtaining a coefficient of phase error and amplitude error and performing compensation processing of the phase error and amplitude error of the quadrature demodulator using the coefficients is defined.

According to a fourth aspect of the present invention, in the quadrature demodulation error compensation method according to any one of the first to third aspects, as the known signal to be input to the quadrature modulator, a baseband in-phase signal and a baseband quadrature signal are respectively preliminarily stored. A modulated signal obtained by inputting a known signal to the quadrature modulator using a signal that repeats two defined signal levels simultaneously at a constant period, and is a modulated signal having carrier components orthogonal to each other. For the first modulated signal and the second modulated signal, and the third modulated signal, which is the sum of the first modulated signal and the second modulated signal, the first to third modulated signals Each square average value obtained by squaring the AC component of each signal and averaging is obtained as a first modulated signal square average value P _RF1 and a second modulated signal square average value P _RF2. The third change Determined as tone signals mean square value P _RF3, the amplitude error of the first modulated signal mean square value P _RF1 and the quadrature modulator from the ratio of the said second modulated signal mean square value P _RF2 A given coefficient G ₁ is obtained, and the first modulated signal mean square value P _RF1 or the second modulated signal mean square value P _RF2 and the third modulated signal mean square value P _RF3 A quadrature demodulation error compensation method for determining the phase error φ ₁ of the quadrature modulator from the ratio and the coefficient G ₁ giving the amplitude error of the quadrature modulator is defined.

  The quadrature demodulation error compensation method according to claim 1, wherein the known signal is input to the quadrature modulator and obtained from the quadrature modulator having a phase error and an amplitude error. An output signal is input to the quadrature demodulator, and an average value of the baseband in-phase output signal of the quadrature demodulator is obtained as a first DC offset, and an average value of the baseband quadrature output signal is obtained as a second DC offset. Subtracting the first DC offset from the baseband in-phase output signal, subtracting the second DC offset from the baseband quadrature output signal, and subtracting the first DC offset from the baseband in-phase output signal; Each baseband quadrature output signal minus the second DC offset is squared and averaged. Further, the coefficients of the quadrature demodulator phase error and amplitude error are obtained from the respective mean square values and the phase error and amplitude error of the quadrature modulator. The baseband in-phase output signal from which the first DC offset has been subtracted or the baseband from which the second DC offset has been subtracted while subtracting the DC offset and subtracting the second DC offset from the baseband quadrature output signal A quadrature demodulation error compensation method is defined in which compensation processing is performed on a quadrature output signal using the phase error of the quadrature demodulator and the coefficient of the amplitude error.

According to a sixth aspect of the present invention, in the quadrature demodulation error compensation method according to the first, second, or fifth aspect, a baseband in-phase signal is predetermined as the known signal to be input to the quadrature modulator. A first known signal that is a periodic signal alternately repeating two signal levels and whose baseband orthogonal signal is always 0;
A second known signal which is a periodic signal in which the baseband in-phase signal is always 0 and the baseband quadrature signal is alternately repeated at two predetermined signal levels; a baseband in-phase signal and a baseband quadrature signal; Is input to the input terminal of the quadrature modulator as a baseband signal using a third known signal that repeats two predetermined signal levels simultaneously at a constant period, and a periodic signal in which the signal level is alternately repeated, a baseband in-phase average value or the first DC offset [delta] _I by averaging the baseband in-phase output signal and the baseband quadrature output signals obtained from the quadrature demodulator in one period or more of time of each said periodic signal the calculated baseband quadrature average [delta] _Q or second DC offset, the quadrature recovery when using the first known signal From the baseband in-phase output signal of the vessel which is the baseband in-phase average value subtracting said first DC offset [delta] _I, the the subtracted value obtained by averaging the square in one period or more of the time of the periodic signal 1 baseband in-phase mean square value P _I1, and the baseband in-phase average value, that is, the first DC offset δ, from the baseband in-phase output signal of the quadrature demodulator when the second known signal is used. _I was subtracted, and a second baseband in-phase mean square value P _I2 obtained by squaring the subtracted value over one period or more of the period of the periodic signal was obtained, and the third known signal was used. It said orthogonal subtracted baseband in-phase output signal the baseband in-phase average value from [delta] _I demodulator, one cycle or more than of the subtracted value said periodic signal when A third baseband in-phase mean square value P _I3 obtained by squaring at the above time is obtained, a coefficient G ₁ giving an amplitude error of the quadrature modulator, a phase error φ ₁ of the quadrature modulator, and the first The phase difference α due to the delay between the quadrature modulator output of the modulated signal for transmission and the quadrature demodulator input is obtained from the mean square value of the second and third baseband in-phase output signals, and the first known signal is obtained. The baseband quadrature average value δ _Q is subtracted from the baseband quadrature output signal of the quadrature demodulator using the quadrature demodulator, and the subtracted value is square-averaged over one period or more of the period signal. 1 baseband quadrature mean square value P _Q1 is obtained, and the baseband quadrature mean value δ _Q is subtracted from the baseband quadrature output signal of the quadrature demodulator when the second known signal is used. The value A baseband of the quadrature demodulator using the third known signal is obtained by _{obtaining a} second baseband quadrature squared mean value _PQ2 obtained by squaring the average of the periodic signal over one period or more. A baseband quadrature average value P _Q3 obtained by subtracting the baseband quadrature average value δ _Q from the quadrature output signal and averaging the subtracted value by a square for one period or more of the period signal is obtained. The phase difference α, the coefficient G ₁ giving the amplitude error of the quadrature modulator, the phase error φ ₁ of the quadrature modulator, and the mean square of the first, second, and third baseband quadrature output signals The phase error φ ₂ of the quadrature demodulator is obtained from the value, the phase difference α, the coefficient G ₁ giving the amplitude error of the quadrature modulator, the phase error φ ₁ of the quadrature modulator, the phase error φ of the quadrature demodulator ₂ , first, second, third Defines the quadrature demodulator error compensating method for performing error compensation process by the mean square of the baseband quadrature output signal to obtain an amplitude error G ₂ of the quadrature demodulator.

The quadrature demodulation error compensation method according to claim 6, wherein the first baseband in-phase mean square value P _I1 , the second baseband in-phase mean square value P _I2 , the first baseband quadrature mean value When at least one of the average value _PQ1 and the second baseband quadrature mean square value _PQ2 is a remarkably small value close to 0, a phase shifter provided between the quadrature modulator and the quadrature demodulator is used. Then, the phase difference α between the carrier wave of the modulated signal and the local oscillator signal of the demodulator is shifted, and the first baseband in-phase mean square value P _I1 , which is a function of the phase difference α, By preventing the root mean square value P _I2 , the first baseband quadrature mean square value P _Q1 and the second baseband quadrature mean square value P _{Q2 from} becoming extremely small values close to 0, the first baseband in-phase Squared When the average value P _I1 , the second baseband in-phase mean square value P _I2 , the first baseband quadrature mean square value P _Q1 and the second baseband quadrature mean square value P _Q2 are extremely small values close to 0 The quadrature demodulation error compensation method for compensating for the phase error and the amplitude error of the quadrature demodulator while reducing the influence of the detection error on the compensation calculation is defined.

  The present invention provides a first mixer that inputs a receiving carrier signal and a modulated signal for transmission and outputs a receiving in-phase baseband signal, and gives a phase difference of 90 degrees to the receiving carrier signal. Receiving a receiving carrier signal and the modulated signal, a quadrature demodulator having a second mixer that outputs a receiving quadrature baseband signal, a transmitting carrier signal and a transmitting in-phase baseband signal, A third mixer that outputs an in-phase modulated signal, a transmission carrier signal that gives a 90-degree phase difference to the transmission carrier signal, and a transmission quadrature baseband signal are input, and a quadrature modulated signal is output. A quadrature modulator, a quadrature modulator having a first adder that adds the in-phase modulated signal and the quadrature modulated signal to output a modulated signal for transmission, and the in-phase of the quadrature modulator Modulated output signal, A known first-mean-square-value detection circuit for detecting a mean-square value of the AC component of each of the modulated signal and the first adder output signal, and a known pattern having a predetermined pattern of the quadrature demodulator A first average value detection circuit for detecting an average value of the baseband in-phase output signal of the signal as a first DC offset, and an average value of the baseband quadrature output signal of the known signal having a predetermined pattern of the quadrature demodulator. A second average value detection circuit that detects the first DC offset; a second adder that subtracts the first DC offset from a baseband in-phase output signal of the quadrature demodulator; and a baseband quadrature output of the quadrature demodulator 2 of the baseband in-phase output signal output from the third adder that subtracts the second DC offset from the signal and the second adder of the quadrature demodulator. A second mean square value detection circuit for detecting an mean value and a mean square value of the baseband orthogonal output signal output from the third adder; and the first and second mean square value detection circuits An arithmetic circuit for obtaining a coefficient for compensating for the phase error and amplitude error of the quadrature demodulator from the mean square value obtained in step (1), and the coefficient obtained by the arithmetic circuit is output from the second adder at the time of reception. A quadrature demodulation error compensation comprising a phase / amplitude compensation circuit for removing the phase error and the amplitude error of the quadrature demodulator with respect to the baseband in-phase signal or the baseband quadrature signal output from the third adder The circuit is specified.

  According to a ninth aspect of the present invention, a first carrier that receives a reception carrier signal and a transmission modulated signal and outputs a reception in-phase baseband signal, and the reception carrier signal and input circuit A quadrature demodulator comprising a second mixer that inputs a modulated signal for transmission with a phase difference of 90 degrees and outputs a received quadrature baseband signal; a carrier signal for transmission and a transmission in-phase baseband signal; A third mixer that inputs and outputs an in-phase modulated signal; and a fourth mixer that receives the transmission carrier signal and the transmission quadrature baseband signal and outputs a quadrature modulated signal with a phase difference of 90 degrees A first adder that adds the in-phase modulated signal and the quadrature modulated signal to output the modulated signal for transmission; an in-phase modulated output signal from the quadrature modulator; and a quadrature modulated output signal And the first A first mean-square value detection circuit that detects a mean-square value of an alternating current component of an arithmetic unit output signal, and an average value of a known baseband in-phase output signal of the quadrature demodulator is detected as a first DC offset. A first average value detection circuit; a second average value detection circuit that detects an average value of a known baseband quadrature output signal of the quadrature demodulator as a second DC offset; and a baseband in-phase output of the quadrature demodulator A second adder for subtracting the first DC offset from the signal; a third adder for subtracting the second DC offset from the baseband quadrature output signal of the quadrature demodulator; and the second adder of the quadrature demodulator. A second mean square value detection circuit for detecting the mean square value of the baseband in-phase output signal output from the adder of 2 and the mean square value of the baseband quadrature output signal output from the third adder. An arithmetic circuit that obtains a coefficient that compensates for a phase error and an amplitude error of the quadrature demodulator from the mean square value obtained by the first and second mean square value detection circuits, and the arithmetic circuit obtained by the arithmetic circuit. The phase error and amplitude error of the quadrature demodulator are removed from the baseband in-phase signal output from the second adder or the baseband quadrature signal output from the third adder at the time of reception by the coefficient. A quadrature demodulation error compensation circuit including a phase / amplitude compensation circuit is defined.

  According to a tenth aspect of the present invention, in the quadrature demodulation error compensation circuit according to any one of the eighth and ninth aspects, the quadrature demodulation error compensation circuit in which a signal of a local oscillator is shared between the quadrature modulator and the quadrature demodulator is defined. ing.

  11. The quadrature demodulation error compensation circuit according to claim 8, wherein the quadrature demodulation error compensation circuit uses the same reference signal in each of the phase locked loops of the quadrature modulator and the quadrature demodulator. The circuit is specified.

  According to a twelfth aspect of the present invention, in the quadrature demodulation error compensation circuit according to the eighth or ninth aspect, a mean square value of a baseband in-phase output signal detected by the second mean square value detection circuit and a base A comparison circuit for determining whether or not the phase of the modulated signal is changed depending on the square mean value of the band orthogonal signal with respect to a predetermined level, and a phase shift for changing the phase of the modulated signal according to the determination result of the comparison circuit The quadrature demodulation error compensation circuit is provided.

  As described above, according to the present invention, the amplitude error and phase error of the communication system on the demodulator side can be compensated including the amplitude error and phase error on the transmitter side. The configuration has been simplified, and a low-cost and highly accurate quadrature modulation communication system can be configured.

(First embodiment)
FIG. 1 is a block diagram showing an orthogonal demodulation error compensation circuit according to the present invention. In FIG. 1, 1 is a reception signal input terminal, 2 and 3 are demodulation signal output terminals having a phase difference of 90 degrees, 4 and 5 are modulation signal input terminals, 6 is a transmission signal output terminal, 7 and 31 are switches, 8 is a quadrature demodulator, 13 and 14 are low-pass filters (LPF), 15 and 16 are average value detection circuits, 17 and 18 are adders, 19 and 30 are mean square value detection circuits, 20 is an arithmetic circuit, and 21 is an arithmetic circuit. A phase / amplitude compensation circuit 25 is a quadrature modulator.

  The quadrature demodulator 8 includes mixers 9 and 10, a local oscillator 11 that oscillates a signal that is a transmission / reception carrier wave, and a 90 ° phase shifter 12. The phase / amplitude compensation circuit 21 includes multipliers 22 and 23 and an adder 24. The quadrature modulator 25 includes mixers 26 and 27 and an adder 29.

  At the time of transmission, the switch 31 connects the output terminal of the adder 29 serving as the output terminal of the quadrature modulator 25 and the transmission signal output terminal 6. At the time of reception, the received signal input terminal 1 and the input terminals of the mixers 9 and 10 which are input terminals of the quadrature demodulator 8 are connected by the switch 7. When the phase error and the amplitude error of the quadrature demodulator 8 are detected, the two mixers serving as the output terminal of the adder 29 serving as the output terminal of the quadrature modulator 25 and the input terminal of the quadrature demodulator 8 by the switch 31 and the switch 7. Connect 9 and 10 input terminals.

In the quadrature demodulation error compensation circuit of FIG. 1, the quadrature modulator 25 and the quadrature demodulator 8 share the output signal of the local oscillator 11 in the quadrature demodulator 8 as a carrier signal, and the angular frequency of this output signal is Assuming that ω, the signal serving as a transmission carrier wave input from the local oscillator 11 to the mixer 26 has sinωt, and has a phase difference of 90 degrees input from the local oscillator 11 to the mixer 27 via the 90-degree phase shifter 12. A signal serving as a transmission carrier can be written as G ₁ cos (ωt + φ ₁ ). Where G ₁ is the amplitude error between the carrier signal input to the mixer 27 and the carrier signal input to the mixer 26, and φ ₁ is the phase between the carrier signal input to the mixer 27 and the carrier signal input to the mixer 26. It is an error.

When phase error and amplitude error are detected by the quadrature demodulator 8 and the quadrature modulator 25, the first modulation signal input to the modulation signal input terminal 4 is I _REF (t) and the second modulation signal input to the modulation signal input terminal 5 is second. Q _REF (t) is a periodic signal in which I _REF (t) alternately repeats signal levels a and −a and Q _REF (t) is always 0, _A second known signal in which _REF (t) is always 0 and Q _REF (t) is a periodic signal in which the signal levels a and -a are alternately repeated, and I _REF (t) and Q _REF (t) are a And a third known signal in which −a is repeated at a constant period simultaneously. Here, a = 1 may be set. At this time,
The first known signal is I _REF (t) = [1, -1,1,-, 1,1, -1, ..., 1, -1],
Q _REF (t) = [0,0,0, ..., 0,0],
The second known signal is I _REF (t) = [0,0,0, ..., 0,0],
Q _REF (t) = [1, -1,1,-, 1,1, -1, ..., 1, -1],
The third known signal is I _REF (t) = [1, -1,1,-, 1,1, -1, ..., 1, -1],
Q _REF (t) = [1, -1,1,-, 1,1, -1, ..., 1, -1],
It is.

When the third known signal is input to the quadrature modulator 25, the mean square value of the modulated signal obtained as the output of the mixer 26 is P _RF1 , and the mean square value of the modulated signal obtained as the output of the mixer 27 is P _RF2. If the sum of the modulated signals obtained from the mixer 26 and the mixer 27, that is, the mean square value of the output signal obtained as the output of the adder 29 is _PRF3 , the mean square value detection circuit 30 squares these signals. As a result of obtaining the average value,

となる。ここでｋ_１は定数である。

It becomes. Where _{k 1} is a constant.

Using the equations (1) and (2), the coefficient G ₁ that gives the amplitude error of the quadrature modulator 25 is

により与えることができる。また、（数１）式、（数３）式より直交変調器２５の位相誤差φ_１は、

Can be given by Furthermore, (Equation 1) wherein the phase error phi ₁ of the quadrature modulator 25 from equation (3),

と求まる。

It is obtained.

  When the modulated signal output from the quadrature modulator 25 having such amplitude error and phase error is S (t), when S (t) is input to the quadrature demodulator 8.

となる。αは送信用被変調信号の直交変調器出力から直交復調器入力までの遅延による位相差である。

It becomes. α is the phase difference due to the delay from the quadrature modulator output to the quadrature demodulator input of the modulated signal for transmission.

This signal S (t) is input to the quadrature demodulator 8 via the switch 31 and the switch 7. The carrier wave signal input to the mixer 9 from the local oscillator 11 in the quadrature demodulator 8 is sinωt, and the carrier wave signal input to the mixer 10 from the local oscillator 11 via the phase shifter 12 is G ₂ cos (ωt + φ ₂ ). Can be written. However, G ₂ is an amplitude error between the signal input from the local oscillator 11 via the 90-degree phase shifter 12 to the mixer 27 and the signal input from the local oscillator 11 to the mixer 26, and φ ₂ is from the local oscillator 11. This is a phase error between the signal input to the mixer 27 via the 90-degree phase shifter 12 and the signal input to the mixer 26 from the local oscillator 11.

Accordingly, after being output from the quadrature demodulator 8, the baseband in-phase output signal I _R (t) obtained through the low-pass filter 13 and the baseband quadrature output signal Q _R (t) obtained through the low-pass filter 14 are obtained. Is

となる。ただしｋ_２は定数、δ_Ｉ、δ_ＱはＤＣオフセットである。一般に能動素子の出力にはＤＣオフセットが含まれているが、直交復調器８の出力信号はベースバンド信号であり、ＤＣ成分を信号として含んでいる。したがって、特に低速信号（低周波信号）を復調する場合には、キャパシタＣ（容量）で低周波成分をカットし、これによりＤＣオフセットを取り除く方法は適用することができない。

It becomes. However _{k 2} is a constant, δ _I, δ _Q is a DC offset. In general, the output of the active element includes a DC offset, but the output signal of the quadrature demodulator 8 is a baseband signal and includes a DC component as a signal. Therefore, particularly when demodulating a low-speed signal (low-frequency signal), it is not possible to apply a method in which a low-frequency component is cut by the capacitor C (capacitance) to thereby remove a DC offset.

Here, a signal in which either I _REF (t) and Q _REF (t), or both are alternately repeated as 1 and −1, such as the first known signal, the second known signal, and the third known signal. When input to the quadrature modulator 25, is a DC offset [delta] _I value obtained by averaging by inputting the average value detecting circuit 15 (7) formula I _R (t). Similarly, the value obtained by inputting Q _R (t) in the equation (8) to the average value detection circuit 16 and averaging it becomes the DC offset δ _Q.

Signals I _dc (t) and Q _dc (t) obtained by subtracting the detected DC offsets δ _I and δ _Q by the adders 17 and 18 are

となる。（数１０）式は、

It becomes. (Equation 10)

に変形できる。

Can be transformed into

When there is no amplitude error and phase error in the quadrature demodulator 8, G ₂ = 1 and φ ₂ = 0, and I _dc (t) in the equation (9) is taken out as an ideal in-phase signal as it is. Can do. On the other hand, if Q _cor (t) is a signal obtained by removing the amplitude error and the phase error from Q _dc (t) in the equation (11), G ₂ = 1 and φ ₂ = 0,

となる。（数９）式および（数１２）式を用いると、（数１１）式は、

It becomes. Using Equation (9) and Equation (12), Equation (11) is

となる。

It becomes.

Accordingly, Q _cor (t) is in a range where φ ₂ is φ ₂ ≠ nπ / 2 (rad) (where n is an odd number).

により与えることができる。

Can be given by

That is, obtains an amplitude error G ₂ and the phase error phi ₂ as follows, by performing the calculation of equation (14) to the signal obtained by removing the DC offset, the amplitude error G ₂ and the phase error phi ₂ The removed ideal quadrature signal can be obtained.

Next, an amplitude error G ₂ and a phase error φ ₂ are obtained.
First, I _REF (t) is a periodic signal that alternately repeats 1 and −1, and a first known signal whose Q _REF (t) is always 0 is input to the quadrature modulator 25. When I _REF (t) = 1, the output I _dc (t) of the adder 17 is expressed by the following equation (9).

となる。また、Ｉ_ＲＥＦ(ｔ)＝０のとき、Ｉ_ｄｃ(ｔ)＝０である。したがって、Ｉ_ＲＥＦ(ｔ)として入力する周期信号の１周期分またはそれ以上の時間でＩ_ｄｃ(ｔ)を２乗平均した値Ｐ_Ｉ１は、

It becomes. When I _REF (t) = 0, I _dc (t) = 0. Therefore, a value P _{I1 obtained} by squaring I _dc (t) over one period or more of the period of the periodic signal input as I _REF (t) is:

となる。

It becomes.

Next, a second known signal that is a periodic signal in which I _REF (t) is always 0 and Q _REF (t) alternately repeats 1 and −1 is input to the quadrature modulator 25. When Q _REF (t) = 1, from equation (9), I _dc (t) is

となる。また、Ｑ_ＲＥＦ(ｔ)＝０のとき、Ｉ_ｄｃ(ｔ)＝０である。したがって、Ｑ_ＲＥＦ(ｔ)として入力する周期信号の１周期分またはそれ以上の時間でＩ_ｄｃ(ｔ)を２乗平均した値Ｐ_Ｉ２は、

It becomes. Further, when Q _REF (t) = 0, I _dc (t) = 0. Therefore, a value P _{I2 obtained} by squaring I _dc (t) over one period or more of a periodic signal input as Q _REF (t) is

となる。（数１６）式と（数１８）式との２条平均した値はそれぞれ等しいことから、

It becomes. Since the two average values of the formula (16) and the formula (18) are equal,

が得られる。ここで、Ａ≡(１／Ｇ_１ ^２)(Ｐ_Ｉ２／Ｐ_Ｉ１)と定義すると、

Is obtained. Here, if defined as A≡ (1 / G ₁ ² ) (P _I2 / P _I1 ),

となる。
γ≡tan^−１{(Ａ＋cos２φ_１)／(sin２φ_１)}と定義し、（数２０）式を変形すると、

It becomes.
γ≡tan ⁻¹ {(A + cos 2φ ₁ ) / (sin 2φ ₁ )}, and the equation (20) is transformed,

となる。したがって、被変調信号の搬送波と直交復調器８の局部発振器信号との位相差αは、

It becomes. Therefore, the phase difference α between the carrier wave of the modulated signal and the local oscillator signal of the quadrature demodulator 8 is

と求まる。（数２２）式中のαは２値存在する。

It is obtained. There are two values of α in the equation (22).

Next, a third known signal that is a periodic signal in which 1 and −1 having the same I _REF (t) and Q _REF (t) are alternately input is input to the quadrature modulator 25. When I _REF (t) = 1 and Q _REF (t) = 1, from equation (9), I _dc (t) is

となる。また、Ｉ_ＲＥＦ(ｔ)＝０でかつＱ_ＲＥＦ(ｔ)＝０のとき、Ｉ_ｄｃ(ｔ)＝０である。したがって、Ｉ_ＲＥＦ(ｔ)、Ｑ_ＲＥＦ(ｔ)として入力する周期信号の１周期分またはそれ以上の時間でＩ_ｄｃ(ｔ)を２乗平均した値Ｐ_Ｉ３は、

It becomes. Further, when I _REF (t) = 0 and Q _REF (t) = 0, I _dc (t) = 0. Therefore, a value P _{I3 obtained} by squaring I _dc (t) over one period or more of the period of the periodic signal input as I _REF (t) and Q _REF (t) is

It becomes. From (Equation 16) and (Equation 24),

（数２２）式の２値のαのうち（数２５）式を満たす値が、求める解である。

A value satisfying Expression (25) among the binary α in Expression (22) is a solution to be obtained.

Next, attention is focused on the output Q _dc (t) of the adder 18 obtained with the same modulation signal. First, in the case of the first known signal, when I _REF (t) = 1, Q _dc (t)

となる。また、Ｉ_ＲＥＦ(ｔ)＝０のとき、Ｑ_ｄｃ(ｔ)＝０である。したがって、Ｉ_ＲＥＦ(ｔ)として入力する周期信号の１周期分以上の時間でＱ_ｄｃ(ｔ)を２乗平均した値Ｐ_Ｑ１は、

It becomes. When I _REF (t) = 0, Q _dc (t) = 0. Therefore, a value P _{Q1 obtained} by squaring the average of Q _dc (t) over a period of one period or more of the periodic signal input as I _REF (t) is

となる。

It becomes.

Next, for the second known signal, when I _REF (t) = 1, Q _dc (t) is

となる。また、Ｑ_ＲＥＦ(ｔ)＝０のとき、Ｑ_ｄｃ(ｔ)＝０である。したがって、Ｑ_ＲＥＦ(ｔ)として入力する周期信号の１周期分以上の時間でＱ_ｄｃ(ｔ)を２乗平均した値Ｐ_Ｑ２は、

It becomes. When Q _REF (t) = 0, Q _dc (t) = 0. Therefore, a value P _{Q2 obtained} by squaring Q _dc (t) over a period of one period or more of the periodic signal input as Q _REF (t) is

となる。（数２７）式と（数２９）式から、

It becomes. From Equation (27) and Equation (29),

が得られる。ここで、Ｂ＝(１／Ｇ_１２)(Ｐ_Ｑ２／Ｐ_Ｑ１)と定義すると、

Is obtained. Here, if defined as B = (1 / G ₁₂ ) (P _Q2 / P _Q1 ),

となる。
λ≡tan^−１（Ｂ＋cos２φ_１）と定義し、（数３１）式を変形すると、

It becomes.
By defining λ≡tan ⁻¹ (B + cos2φ ₁ ) and transforming the equation (31),

となる。したがって、直交復調器８の位相誤差φ_２は、

It becomes. Therefore, the phase error φ ₂ of the quadrature demodulator 8 is

と求まる。（数３３）式中のφ_２は２値存在する。

It is obtained. There are two values of φ ₂ in the equation (33).

Next, a third known signal that is a periodic signal in which 1 and −1 having the same I _REF (t) and Q _REF (t) are alternately input is input to the quadrature modulator 25. When I _REF (t) = 1 and Q _REF (t) = 1, Q _dc (t) is

となる。また、Ｉ_ＲＥＦ(ｔ)＝０でかつＱ_ＲＥＦ(ｔ)＝０のとき、Ｑ_ｄｃ(ｔ)＝０である。したがって、Ｉ_ＲＥＦ(ｔ)、Ｑ_ＲＥＦ(ｔ)として入力する周期信号の１周期分またはそれ以上の時間でＱ_ｄｃ(ｔ)を２乗平均した値Ｐ_Ｉ３は、

It becomes. When I _REF (t) = 0 and Q _REF (t) = 0, Q _dc (t) = 0. Therefore, a value P _{I3 obtained} by averaging the squares of Q _dc (t) in one period or more of the period of the periodic signal input as I _REF (t) and Q _REF (t) is

となる。（数２９）式と（数３５）式から、

It becomes. From Equation (29) and Equation (35),

（数３３）式における２値のφ_２のうち（数３６）式を満たす値が、求める解である。

A value satisfying Equation (36) among the binary φ ₂ in Equation (33) is a solution to be obtained.

  From (Equation 16) and (Equation 29),

が得られる。したがって（数３７）式を変形することによって直交復調器８の振幅誤差Ｇ_２は、

Is obtained. Therefore, by modifying the equation (37), the amplitude error G ₂ of the quadrature demodulator 8 is

と求まる。

It is obtained.

The calculations of the above (Expression 1) to (Expression 5) and (Expression 15) to (Expression 38) are performed by the root mean square detection circuits 19 and 30 and the operation circuit 20, and tanφ ₂ and G ₂ cosφ ₂ are obtained and input to the multipliers 22 and 23 in the phase / amplitude compensation circuit 21 as coefficients, respectively.

  In this state, the received signal input terminal 1 and the input terminal of the quadrature demodulator 8 are connected by the switch 7 to output an ideal quadrature signal from which the DC offset, amplitude error and phase error have been removed from the received signal. 3 can be obtained. An ideal in-phase signal from which the DC offset is removed is output to the output terminal 2.

  In the first embodiment, the amplitude error and phase error of the quadrature demodulator 8 are compensated with high accuracy without using the time not received in the quadrature modulator 25 to compensate for the amplitude error and phase error of the quadrature modulator 25. Is possible.

(Second Embodiment)
FIG. 2 is a block diagram showing an orthogonal demodulation error compensation circuit according to the second embodiment. The same parts as those in FIG. 1 are given the same reference numerals.
In the quadrature demodulation error compensation circuit of FIG. 2, the quadrature modulator 25 has a local oscillator 11 and a 90-degree phase shifter 33 independently of the quadrature demodulator 8. By using different local oscillators 11 and 32 for the quadrature demodulator 8 and the quadrature modulator 25, normal signal transmission can be performed using the quadrature modulator 25 when the transmission and reception carrier frequencies are different. Further, even when the local oscillators are separated as described above, if the same reference signal is used for the phase locked loop of each of the quadrature demodulator 8 and the quadrature modulator 25, the same level as in the first embodiment is used. The operation is such that the phase difference α does not vary with time.

  In the circuit of FIG. 2, the output signal of the local oscillator 11 is input to the demodulating mixers 9 and 10 in phase, and the modulated signal input to the mixers 9 and 10 via the switch 7 has a phase of 90 degrees. A phase difference of 90 degrees is given by the converter 34, the output signal of the local oscillator 32 is inputted to the mixers 26 and 27 in the same phase, and the phase of the modulated signal output from the mixer 27 is changed by 90 degrees by the 90 degree phase shifter 33. ing.

  Thus, whether the 90 degree phase is given is the output of the quadrature demodulator 8 is the same regardless of whether the signal is output from the local oscillator or the modulated signal, the amplitude error and phase error of the quadrature demodulator 8 are reduced. Compensation is possible in the same way.

(Third embodiment)
FIG. 3 is a block diagram showing an orthogonal demodulation error compensation circuit according to the third embodiment. 1 and 2 are assigned the same reference numerals.
In the third embodiment, the output of the first low-pass filter 13 is input to the first A / D converter 35 and the output of the second low-pass filter 14 is input to the second A / D converter 36. Then, after conversion into digital signals, average value detection, mean square, calculation, and phase / amplitude compensation are performed. By performing these by digital signal processing, the operation can be performed with high accuracy. The A / D converter may be placed in front of the quadrature demodulator 8 so that the quadrature demodulator is a digital circuit.

  Further, as shown in the block diagram of FIG. 4, the mean square value detection circuit 30 inputs the output of the mixer 26 to the third A / D converter 37, and outputs the output of the adder 29 to the fourth A / D converter. 38, the output of the mixer 27 may be input to the fifth A / D converter 39 and converted into a digital signal, and then the mean square may be obtained by the arithmetic processing of the arithmetic circuit 40.

  Further, the mean square value detection circuit 30 converts the output of the mixer 26 into a low frequency signal by the local oscillator 41 and the mixer 42 and inputs the signal to the third A / D converter 37 as shown in the block diagram of FIG. The output of the adder 29 is converted to a low frequency signal by the local oscillator 41 and the mixer 43 and input to the fourth A / D converter 38, and the output of the mixer 27 is converted to a low frequency by the local oscillator 41 and the mixer 44. It is also possible to employ a configuration in which the mean square is obtained by the arithmetic processing of the arithmetic circuit 40 after being converted into a digital signal and inputted to the fifth A / D converter 39 and converted into digital signals.

(Fourth embodiment)
FIG. 6 is a block diagram showing an orthogonal demodulation error compensation circuit according to the fourth embodiment. The same parts as those in FIGS. 1 to 3 are denoted by the same reference numerals.
The fourth embodiment is effective when the frequency of the output signal of the quadrature modulator 25 and the frequency of the received signal input to the quadrature demodulator 8 are different. In the fourth embodiment, an oscillator 45 and a mixer 46 for frequency conversion are provided between the switch 31 and the switch 7, and the frequency of the output signal of the quadrature modulator 25 is received from the received signal input terminal 1. It is converted to match the signal frequency. As a result, the output signal of the quadrature modulator 25 can be used for phase error detection of the quadrature demodulator 8 as in the first, second, and third embodiments.

(Fifth embodiment)
FIG. 7 is a block diagram showing an orthogonal demodulation error compensation circuit according to the fifth embodiment. Levels of the values of P _I1 , P _I2 , P _Q1 and P _Q2 obtained by the root mean square detection circuit 19 are determined by the comparison circuit 45, and at least one of P _I1 , P _I2 , P _Q1 and P _Q2 is close to 0. When the value is extremely small, the phase shifter 46 provided between the quadrature modulator 25 and the quadrature demodulator 8 is used to delay the phase difference between the quadrature modulator output of the modulated signal and the direct demodulator input. By shifting α so that P _I1 , P _I2 , P _Q1 and P _{Q2 as} a function of this phase difference α do not become extremely small values close to 0, these P _I1 , P _I2 , P _Q1 and It is possible to eliminate the influence on the compensation calculation of the detection error that occurs when P _Q2 is a remarkably small value close to 0, and to perform the compensation process of the phase error and the amplitude error of the quadrature demodulator 8 with high accuracy.

(Other embodiments)
In the first to fourth embodiments described above, the processing for compensating the phase error and the amplitude error for the baseband quadrature output signal on the output terminal 3 side with reference to the baseband in-phase output signal on the output terminal 2 side. However, conversely, the baseband quadrature output signal can be similarly applied to the baseband in-phase output signal.

1 is a block diagram showing an orthogonal demodulation error compensation circuit according to a first embodiment of the present invention. The block diagram which shows the orthogonal demodulation error compensation circuit which is the 2nd Embodiment of this invention. The block diagram which shows the orthogonal demodulation error compensation circuit which is the 3rd Embodiment of this invention. The block diagram which shows the 1st structural example of the square mean value detection circuit of the output signal of the quadrature modulator of the 3rd Embodiment of this invention. The block diagram which shows the 2nd structural example of the square mean value detection circuit of the output signal of the quadrature modulator of 3rd Embodiment. The block diagram which shows the orthogonal demodulation error compensation circuit which is the 4th Embodiment of this invention. The block diagram which shows the orthogonal demodulation error compensation circuit which is the 5th Embodiment of this invention. The block diagram which shows the conventional orthogonal demodulator.

Explanation of symbols

1: Received signal input terminal 2: Demodulated in-phase signal output terminal 3: Demodulated 90 degree phase difference signal output terminal 4, 5: Modulated signal input terminal 6: Transmitted signal output terminal 7, 31: Switch 8, 50: Quadrature demodulator 9, 10, 26, 27, 42, 43, 44: Mixer 11, 32, 53: Local oscillator 12, 33, 34, 45, 54: 90 degree phase shifter 13, 14, 55, 56: Low-pass filter 15, 16: Average value detection circuit 17, 18: Adder 19, 30: Root mean value detection circuit 20: Arithmetic circuit 21: Phase / amplitude compensation circuit 22, 23: Multiplier 24, 29: Adder 25: Quadrature modulator 37, 38, 39: A / D converter

Claims (12)

A first mixer that inputs a reception carrier signal and a modulated signal for transmission and outputs a reception in-phase baseband signal; and a reception carrier signal that gives a phase difference of 90 degrees to the reception carrier signal; A quadrature demodulator having a second mixer that inputs the modulated signal and outputs a received quadrature baseband signal;
A third mixer that inputs a transmission carrier signal and a transmission in-phase baseband signal and outputs an in-phase modulated signal, and a transmission carrier signal that gives a phase difference of 90 degrees to the transmission carrier signal and transmission A fourth mixer that inputs a quadrature baseband signal and outputs a quadrature modulated signal; and an adder that adds the in-phase modulated signal and the quadrature modulated signal to output a modulated signal for transmission. A quadrature demodulation error compensation method in a transmission / reception apparatus comprising:
Applying a known signal having a predetermined pattern to the quadrature modulator to obtain a coefficient that gives a phase error and an amplitude error of the quadrature modulator;
Further, the modulated signal for transmission, which is an output signal obtained from the quadrature modulator to which the known signal is input, is input to the quadrature demodulator,
Obtaining a coefficient that gives the phase error and the amplitude error of the quadrature demodulator from an output of the quadrature demodulator and a coefficient that gives the phase error and the amplitude error of the quadrature modulator;
At the time of signal reception, compensation processing for the phase error and the amplitude error of the quadrature demodulator is performed on the received in-phase baseband signal or the received quadrature baseband signal using coefficients that give the phase error and amplitude error of the quadrature demodulator. A quadrature demodulation error compensation method characterized by: A first mixer that inputs a reception carrier signal and a transmission modulated signal and outputs a reception in-phase baseband signal, and an input circuit of the reception carrier signal and a quadrature demodulator to the modulation signal 90 A quadrature demodulator having a second mixer that inputs a signal giving a phase difference of degrees and outputs a received quadrature baseband signal;
A third mixer for inputting a transmission carrier signal and a transmission in-phase baseband signal and outputting an in-phase modulated signal, a transmission carrier signal and a transmission quadrature baseband signal, and a 90 ° output circuit A quadrature modulator comprising: a fourth mixer that outputs a quadrature modulated signal with a phase difference; and an adder that adds the in-phase modulated signal and the quadrature modulated signal to output a modulated signal for transmission And a quadrature demodulation error compensation method in a transmission / reception apparatus comprising:
Applying a known signal having a predetermined pattern to the quadrature modulator to determine the phase error and amplitude error coefficients of the quadrature modulator;
Further, the modulated signal that is an output signal obtained from the quadrature modulator to which the known signal is input is input to the quadrature demodulator,
Obtaining a coefficient that gives a phase error and an amplitude error of the quadrature modulator and a coefficient that gives a phase error and an amplitude error of the quadrature demodulator from the output of the quadrature demodulator,
Compensation processing that gives the phase error and amplitude error of the quadrature demodulator to the received in-phase baseband signal or the received quadrature baseband signal by the coefficients of the phase error and amplitude error of the quadrature demodulator for the received in-phase baseband signal or the received quadrature baseband signal A quadrature demodulation error compensation method, characterized in that: In the orthogonal demodulation error compensation method according to claim 1 or 2,
The transmission in-phase baseband signal of the known signal and the transmission quadrature baseband signal of the known signal are input to the quadrature modulator, and each of the in-phase modulated signal, the quadrature modulated signal, and the modulated signal for transmission The values obtained by averaging the AC components after squaring are obtained as the mean square value of the first modulated signal, the mean square value of the second modulated signal, and the mean square value of the third modulated signal, respectively. Coefficients of phase error and amplitude error of the quadrature modulator are obtained from the mean square values of the first, second and third modulated signals for transmission, and the phase error and amplitude of the quadrature demodulator are obtained using the coefficients. An orthogonal demodulation error compensation method characterized by performing error compensation processing. In the orthogonal demodulation error compensation method according to any one of claims 1 to 3,
As the known signal to be input to the quadrature modulator, a baseband in-phase signal and a baseband quadrature signal each use a signal that repeats two predetermined signal levels simultaneously at a constant period,
A modulated signal obtained by inputting the known signal to the quadrature modulator, a first modulated signal and a second modulated signal, which are two modulated signals whose carrier wave components are orthogonal to each other, and Obtained by averaging the third modulated signal, which is the sum of one modulated signal and the second modulated signal, after squaring the alternating current component of each of the first to third modulated signals. The respective mean square values obtained are obtained as a first modulated signal mean square value P _RF1 , a second modulated signal mean square value P _RF2 , and a third modulated signal mean square value P _RF3 ,
A coefficient G ₁ giving an amplitude error of the quadrature modulator is obtained from a ratio between the first modulated signal mean square value P _RF1 and the second modulated signal mean square value P _RF2, and Modulated signal mean square value P _RF1 or the ratio of the second modulated signal mean square value P _RF2 to the third modulated signal mean square value P _RF3 and the amplitude error of the quadrature modulator are given. A quadrature demodulation error compensation method, wherein a phase error φ ₁ of the quadrature modulator is obtained from a coefficient G ₁ . In the orthogonal demodulation error compensation method according to claim 1 or 2,
The known signal is input to the quadrature modulator, and an output signal obtained from the quadrature modulator having a phase error and an amplitude error is input to the quadrature demodulator,
An average value of the baseband in-phase output signal of the quadrature demodulator is obtained as a first DC offset, an average value of the baseband quadrature output signal is obtained as a second DC offset, and the first DC offset is obtained as the baseband. Subtracting from the in-phase output signal and subtracting the second DC offset from the baseband quadrature output signal, subtracting the first DC offset and the baseband in-phase output signal subtracting the second DC offset From the respective square mean values obtained by averaging the band quadrature output signals after squaring, and the phase error and amplitude error of the quadrature modulator, the phase error and amplitude error coefficients of the quadrature demodulator are obtained,
Upon signal reception, the first DC offset is subtracted from the baseband in-phase output signal, and the second DC offset is subtracted from the baseband quadrature output signal,
The baseband in-phase output signal from which the first DC offset has been subtracted or the baseband quadrature output signal from which the second DC offset has been subtracted is compensated by the phase error and amplitude error coefficients of the quadrature demodulator. An orthogonal demodulation error compensation method characterized by performing processing. In the quadrature demodulation error compensation method according to claim 1, 2 or 5,
As the known signal to be input to the quadrature modulator, a first known signal in which the baseband in-phase signal is a periodic signal that alternately repeats two predetermined signal levels and the baseband quadrature signal is always 0 ,
A second known signal that is a periodic signal in which the baseband in-phase signal is always 0 and the baseband quadrature signal is alternately repeated between two predetermined signal levels;
Using a third known signal in which a baseband in-phase signal and a baseband quadrature signal repeat two predetermined signal levels simultaneously at a constant period,
A periodic signal in which the signal level is alternately repeated is input as a baseband signal to an input terminal of the quadrature modulator, and a baseband in-phase output signal and a baseband quadrature output signal obtained from the quadrature demodulator are respectively input to the periodic signal. A baseband in-phase average value, that is, a first DC offset δ _I and a baseband quadrature average value δ _Q, that is, a second DC offset, are averaged over one period or more time
Subtracting said first DC offset [delta] _I from the baseband in-phase output signal is the baseband in-phase average value of the quadrature demodulator when using the first known signal, for the subtracted value the periodic signal A first baseband in-phase mean square value P _I1 obtained by squaring over one period or more time is obtained;
The baseband in-phase average value, that is, the first DC offset δ _I is subtracted from the baseband in-phase output signal of the quadrature demodulator when the second known signal is used, and this subtracted value is 1 of the periodic signal. A second baseband in-phase mean square value P _I2 obtained by averaging the mean squares over a period of time or longer;
It said orthogonal subtracted baseband in-phase output signal from the baseband in-phase average value [delta] _I demodulator, one cycle or longer in the subtracted value said periodic signal when using the third known signal To obtain a third baseband in-phase mean square value P _I3 obtained by squaring at
From the coefficient G ₁ that gives the amplitude error of the quadrature modulator, the phase error φ ₁ of the quadrature modulator, and the mean square value of the first, second, and third baseband in-phase output signals, the modulated signal for transmission Find the phase difference α due to the delay between the quadrature modulator output and the quadrature demodulator input of the signal,
It said orthogonal subtracted base from said band quadrature output signal baseband quadrature average [delta] _Q demodulator, one cycle or longer in the subtracted value said periodic signal when using the first known signal The first baseband orthogonal mean square value P _Q1 obtained by squaring at
It said orthogonal subtracted base from said band quadrature output signal baseband quadrature average [delta] _Q demodulator, one cycle or longer in the subtracted value said periodic signal when using the second known signal To obtain a second baseband orthogonal mean square value P _Q2 obtained by squaring
The baseband quadrature average value δ _Q is subtracted from the baseband quadrature output signal of the quadrature demodulator when the third known signal is used, and this subtracted value is a time corresponding to one period or more of the periodic signal. To obtain a third baseband orthogonal mean square value P _Q3 obtained by squaring
From the phase difference α, the coefficient G ₁ giving the amplitude error of the quadrature modulator, the phase error φ ₁ of the quadrature modulator, and the mean square value of the first, second, and third baseband quadrature output signals the quadrature demodulator obtains a phase error phi ₂ of the phase difference alpha, factor G ₁ to give an amplitude error of the quadrature _modulator, the phase error phi ₁ of the quadrature _modulator, the quadrature demodulator of the phase error phi _2, first, second, orthogonal demodulation error compensation method characterized by performing error compensation process by obtaining the amplitude error G ₂ of the quadrature demodulator from mean square value of the third respective baseband quadrature output signal. The quadrature demodulation error compensation method according to claim 6,
At least one of first baseband in-phase mean square value P _I1 , second baseband in-phase mean square value P _I2 , first baseband quadrature mean square value P _Q1, and second baseband quadrature mean square value P _Q2 Phase difference between the carrier wave of the modulated signal and the local oscillator signal of the demodulator using a phase shifter provided between the quadrature modulator and the quadrature demodulator. By shifting α, the first baseband in-phase mean square value P _I1 , the second baseband in-phase mean square value P _I2 , the first baseband quadrature mean square value P _Q1, which are functions of the phase difference α, and By preventing the second baseband quadrature mean square value P _{Q2 from} becoming a remarkably small value close to 0, the first baseband in-phase mean square value P _I1 , the second baseband in-phase mean square value P _I2 , 1st base Command orthogonal mean square value P _Q1 and the second baseband quadrature mean square value P _Q2 is of the quadrature demodulator by reducing the influence of the compensation calculation in the detection error caused when a considerably small value close to 0 phase An orthogonal demodulation error compensation method characterized by performing error and amplitude error compensation processing. A first mixer that inputs a reception carrier signal and a modulated signal for transmission and outputs a reception in-phase baseband signal; and a reception carrier signal that gives a phase difference of 90 degrees to the reception carrier signal; A quadrature demodulator having a second mixer that inputs the modulated signal and outputs a received quadrature baseband signal;
A third mixer that inputs a transmission carrier signal and a transmission in-phase baseband signal and outputs an in-phase modulated signal, and a transmission carrier signal that gives a phase difference of 90 degrees to the transmission carrier signal and transmission A fourth mixer that inputs a quadrature baseband signal and outputs a quadrature modulated signal; and a first addition that adds the in-phase modulated signal and the quadrature modulated signal to output a modulated signal for transmission. A quadrature modulator having a
A first mean square value detection circuit for detecting a mean square value of alternating current components of the in-phase modulated output signal, the quadrature modulated output signal, and the first adder output signal of the quadrature modulator;
A first average value detection circuit that detects an average value of a baseband in-phase output signal of a known signal having a predetermined pattern of the quadrature demodulator as a first DC offset;
A second average value detection circuit for detecting an average value of a baseband quadrature output signal of a known signal having a predetermined pattern of the quadrature demodulator as a first DC offset;
A second adder for subtracting the first DC offset from the baseband in-phase output signal of the quadrature demodulator;
A third adder for subtracting the second DC offset from the baseband quadrature output signal of the quadrature demodulator;
A second means for detecting a mean square value of the baseband in-phase output signal output from the second adder of the quadrature demodulator and a mean square value of the baseband quadrature output signal output from the third adder; A root mean square value detection circuit;
An arithmetic circuit for obtaining a coefficient for compensating for the phase error and the amplitude error of the quadrature demodulator from the mean square value obtained by the first and second mean square value detection circuits;
Based on the coefficients obtained by this arithmetic circuit, the baseband in-phase signal output from the second adder at the time of reception or the baseband quadrature signal output from the third adder at the time of reception, the quadrature demodulator A quadrature demodulation error compensation circuit comprising a phase / amplitude compensation circuit for removing the phase error and the amplitude error. A first mixer that inputs a reception carrier signal and a transmission modulated signal and outputs a reception in-phase baseband signal; and a phase difference of 90 degrees with respect to the modulation signal in the reception carrier signal and input circuit A quadrature demodulator comprising: a second mixer that inputs a modulated signal for transmission to which is given, and outputs a received quadrature baseband signal;
A third mixer that inputs a transmission carrier signal and a transmission in-phase baseband signal and outputs an in-phase modulated signal, and inputs the transmission carrier signal and a transmission quadrature baseband signal, giving a phase difference of 90 degrees A fourth mixer for outputting a quadrature modulated signal;
A first adder that adds the in-phase modulated signal and the quadrature modulated signal to output the modulated signal for transmission;
A first mean square value detection circuit for detecting a mean square value of alternating current components of the in-phase modulated output signal, the quadrature modulated output signal and the first adder output signal of the quadrature modulator;
A first average value detection circuit for detecting an average value of a known baseband in-phase output signal of the quadrature demodulator as a first DC offset;
A second average value detection circuit for detecting an average value of known baseband quadrature output signals of the quadrature demodulator as a second DC offset;
A second adder for subtracting the first DC offset from the baseband in-phase output signal of the quadrature demodulator;
A third adder for subtracting the second DC offset from the baseband quadrature output signal of the quadrature demodulator;
A second mean value for detecting a mean square value of the baseband in-phase output signal output from the second adder of the quadrature demodulator and a mean square value of the baseband quadrature output signal output from the third adder. A mean square detection circuit;
An arithmetic circuit for obtaining coefficients for compensating for the phase error and amplitude error of the quadrature demodulator from the mean square value obtained by the first and second mean square value detection circuits;
Based on the coefficients obtained by this arithmetic circuit, the baseband in-phase signal output from the second adder at the time of reception or the baseband quadrature signal output from the third adder at the time of reception, the quadrature demodulator A quadrature demodulation error compensation circuit comprising: a phase / amplitude compensation circuit for removing the phase error and the amplitude error. The orthogonal demodulation error compensation circuit according to claim 8 or 9,
A quadrature demodulation error compensation circuit, wherein the quadrature modulator and the quadrature demodulator share a signal of a local oscillator. The orthogonal demodulation error compensation circuit according to claim 8 or 9,
An orthogonal demodulation error compensation circuit, wherein the same reference signal is used in each of the phase locked loops of the orthogonal modulator and the orthogonal demodulator. The orthogonal demodulation error compensation circuit according to claim 8 or 9,
Whether the mean square value of the baseband in-phase output signal detected by the second mean square value detection circuit and the mean square value of the baseband quadrature signal change the phase of the modulated signal depending on the magnitude of a predetermined level A comparison circuit for determining whether or not;
A quadrature demodulation error compensation circuit comprising: a phase shifter that changes a phase of a modulated signal according to a determination result of the comparison circuit.

Images