JP2016205973A - Light pulse detection circuit and electronic apparatus - Google Patents

Abstract

PROBLEM TO BE SOLVED: To prevent decrease of hysteresis of a hysteresis comparator caused by increase of power supply noise.SOLUTION: A light pulse detection circuit (1) includes a light receiving element (2a), a dummy light receiving element (2b), and a hysteresis comparator (3), and is provided with a capacitive element (C1) for injecting noise of a power supply line (L) into at least one of a route of a pulse voltage signal (S13) and a route of a shading voltage signal (S17).SELECTED DRAWING: Figure 1

Description

  The present invention relates to an optical pulse detection circuit and an electronic device for detecting an optical pulse, and more particularly to an optical pulse detection circuit and an electronic device which are main components of a small object detection device to be mounted on a portable device such as a mobile phone. .

  In recent years, a sensor that detects the presence or absence of a nearby object (hereinafter also referred to as “proximity sensor”) is generally mounted on a portable device such as a mobile phone. Proximity sensors for portable device applications such as those described above must be able to achieve resistance to ambient light, such as sunlight and fluorescent lamps, and sensing characteristics such as desired detection sensitivity and response time in a very small mounting area. It is. Further, it is strongly desired that the proximity sensor itself has extremely low power consumption. Such a proximity sensor is disclosed in Patent Document 1, for example.

Patent No. 04644732 (issued on March 2, 2011)

  In portable devices such as the above-described mobile phones, there is a situation where power line noise input to the optical pulse detection circuit (proximity sensor) is not sufficiently smoothed due to downsizing and price reduction. In many cases, power line noise generated from a switching power supply, a digital circuit, or the like generates noise having a frequency included in the light receiving band frequency of the optical pulse detection circuit. When such power supply line noise is input to the optical pulse detection circuit, the hysteresis of the optical pulse detection circuit that is set to increase stability decreases, and chattering may occur near the detection threshold of the input signal. is there.

  The reason why the hysteresis of the conventional optical pulse detection circuit is lowered due to power line noise will be described below.

  FIG. 17 is a circuit diagram of a conventional optical pulse detection circuit 90. The optical pulse detection circuit 90 includes a light emitting element driving circuit 6. The light emitting element driving circuit 6 drives the light emitting element 5 by a signal S11 representing a light emitting element current having a certain period. The light emitting element 5 driven by the light emitting element driving circuit 6 irradiates the object D with the irradiation pulse light L1. The reflected pulsed light L2 (signal S12) obtained by reflecting the irradiation pulsed light L1 by the detected object D is received by the light receiving element 2a provided in the light receiving amplifier circuit 7 and converted into a pulse current signal. The pulse current signal is converted into a pulse voltage signal S13 by a transimpedance amplifier 4a provided in the light receiving amplifier circuit 7. The pulse voltage signal S13 converted by the transimpedance amplifier 4a is input to the hysteresis comparator 3.

  The dummy amplifier circuit 8 includes a dummy light receiving element 2 b shielded from light by a light shielding plate 9. A light shielding current signal is supplied to the transimpedance amplifier 4b from the dummy light receiving element 2b shielded by the light shielding plate 9. The light shielding current signal is converted into a light shielding voltage signal S17 by a transimpedance amplifier 4b provided in the dummy amplifier circuit 8. The shading voltage signal S17 converted by the transimpedance amplifier 4b is input to the hysteresis comparator 3.

  The hysteresis comparator 3 outputs a comparator output signal Vcmp based on the pulse voltage signal S13 converted by the transimpedance amplifier 4a, the shading voltage signal S17 converted by the transimpedance amplifier 4b, and the threshold current value Ith.

  FIG. 18 is a circuit diagram of the hysteresis comparator 3 provided in the optical pulse detection circuit 90. FIGS. 19A to 19G are timing charts showing the operation at the time of detection when the optical pulse detection circuit 90 has no power supply noise.

  The pulse voltage signal S13 is input to the comparator input 1 from the transimpedance amplifier 4a of the light receiving amplifier circuit 7. The light shielding voltage signal S17 is input to the comparator input 2 from the transimpedance amplifier 4b of the dummy amplifier circuit 8.

  The switches SW01, SW02, and SW05 provided in the hysteresis comparator 3 are turned on during the offset cancellation period in which the offset cancellation signal S16 shown in FIG. Then, the drain output of the PMOS transistor 415 and the NMOS transistor 419 is input to the gate of the PMOS transistor 405, so that a negative feedback configuration appears. Then, the voltage of the reference voltage source 401 is input to the gate of the PMOS transistor 406, and the voltage of the reference voltage source 401 is virtually short-circuited to the gate of the PMOS transistor 405, whereby the offset voltage present in the hysteresis comparator 3 is changed to the capacitive element 403. And the capacitor 403.

  In the offset cancel period shown in FIG. 19G, the switches SW03 and SW04 are turned on, and the offset voltage is held in the capacitive element 402 and the capacitive element 403, so that the offset present in the hysteresis comparator 3 is reduced. Canceled. The threshold current value Ith supplied from the line provided with the switch SW03 becomes the threshold value of the hysteresis comparator 3. The threshold current value Ith is switched by control from the outside of the hysteresis comparator 3. Thereby, the hysteresis of the hysteresis comparator 3 is provided.

  In the configuration of the hysteresis comparator 3 shown in FIG. 18, since the reference voltage source 401 is connected to one comparator input 1 of the hysteresis comparator 3 during the offset cancellation period, the power supply noise is not canceled in the same phase. For this reason, power supply noise greatly affects offset cancellation.

  FIG. 19 shows a timing chart at the time of detection determination of the hysteresis comparator 3 when there is no power supply noise. In the state at the time of detection determination of the hysteresis comparator 3, the threshold current value Ith of the hysteresis comparator 3 is set to the threshold current value Ithon.

  When the signal S12 representing the reflected pulsed light L2 is turned on, the pulse current signal (light emitting element current) is also turned on, and the pulse voltage signal S13 (light receiving amplifier output) also rises. When the signal S14 representing the differential current Idiff based on the pulse voltage signal S13 based on the reflected pulsed light L2 and the light shielding voltage signal S17 reaches the threshold current value Iton, the comparator output signal Vcmp is turned on.

  20A to 20G are timing charts showing the operation at the time of non-detection in the case where there is no power supply noise of the optical pulse detection circuit 90. FIG. The same components as those described above with reference to FIG. 19 are denoted by the same reference numerals. Detailed description of these components will not be repeated.

  In the state at the time of non-detection determination of the hysteresis comparator 3, the threshold current value Ith of the hysteresis comparator 3 is set to a value of Ithoff smaller than Ithon. When the signal S14 representing the differential current Idiff based on the pulse voltage signal S13 based on the reflected pulsed light L2 and the light-shielding voltage signal S17 does not reach the threshold current value Ithoff, the comparator output signal Vcmp does not react.

  Next, FIGS. 21 and 22 show timing charts at the time of detection determination in the presence of power supply noise and timing charts at the time of non-detection determination, respectively. 21A to 21G are timing charts showing the operation at the time of detection when the power pulse noise of the optical pulse detection circuit 90 exists. FIGS. 22A to 22G are timing charts showing the operation at the time of non-detection when the power pulse noise of the optical pulse detection circuit 90 exists.

  FIG. 21 shows a state in which the signal light component Ion obtained by subtracting the power supply noise component Ioc and the normal power supply noise component Ipd from the peak value of the signal S14 representing the differential current Idiff is the smallest during detection determination (the detection distance becomes long). State). Power supply noise enters from the reference voltage source 401 during the offset cancellation period. As shown in FIG. 21E, when the end of the offset cancellation period ends with the + side peak of the power supply noise, the signal S14 representing the differential current Idiff is held at the peak voltage on the + side of the power supply noise. Is done. This power supply noise component Ioc works in the direction of decreasing the signal component Ion with respect to the threshold current value Ith = Ithon, and works in the direction of increasing the detection distance.

  FIG. 22 shows a state in which the signal light component Ion obtained by subtracting the power supply noise component Ioc and the normal power supply noise component Ipd from the peak value of the signal S14 representing the differential current Idiff is maximized at the time of non-detection determination (the detection distance is short). State). Power supply noise enters from the reference voltage source 401 during the offset cancellation period. As shown in FIG. 22E, when the end of the offset cancellation period ends with the negative peak of the power supply noise, the signal S14 representing the differential current Idiff holds the negative peak voltage of the power supply noise. Is done. This power supply noise component Ioc works to increase the signal component Ioff with respect to the threshold current value Ith = Ithoff, and works to reduce the detection distance.

  The phenomenon shown in FIG. 21 and FIG. 22 shows that the hysteresis due to Ithon and Ithoff, which are the set values of the threshold current value Ith, becomes smaller as the power supply noise increases.

  These effects are formulated as distance conversion as shown in FIG. FIG. 23 is a diagram illustrating calculation formulas for the detection distance and the non-detection distance.

  In general, a lens is used for a light emitting unit and a light receiving unit in an optical pulse detection circuit, and therefore the distance conversion is shown to be proportional to the inverse of the half power of the signal light. A formula representing the detection distance Lon is shown in (Formula 1), and a formula showing the non-detection distance Loff is shown in (Formula 2). The formula for defining hysteresis is shown in (Formula 3).

here,
Ithon: threshold current value at the time of detection,
Ithoff: threshold current value at non-detection,
Goc: Gm during the offset cancellation period with respect to the power supply voltage,
Gpd: Gm other than the normal period for the power supply voltage,
Vac: power supply noise amplitude,
It is.

  In the conventional configuration, assuming that Gm of Gm in the offset cancellation period is sufficiently large and Gpd of Gm outside the offset cancellation period is considered as 0, the detection distance characteristic corresponds to the detection distance Lon as shown in FIG. And a curve G2 corresponding to the non-detection distance Loff (the detection distance Lon is normalized so as to be 1 under the condition of no noise). As the power supply noise amplitude represented by the horizontal axis increases, the distance between the curve G1 corresponding to the detection distance Lon and the curve G2 corresponding to Loff decreases, and chattering is likely to occur. .

here,
Ithon = 1,
Ithoff = 0.5,
Goc = 0.002,
Gpd = 0
It is.

  FIG. 25 is a graph showing distance-converted hysteresis with respect to the power supply noise amplitude of the optical pulse detection circuit 90. The curve G3 corresponds to a value obtained by subtracting the value corresponding to the curve G1 from the value corresponding to the curve G2 shown in FIG. 24, and the hysteresis is determined by the difference between the detection distance corresponding to Lon and the detection distance corresponding to Loff. The absolute value of hysteresis converted to the distance of the comparator 3 is shown.

  As described above, the conventional configuration has a problem that the hysteresis of the hysteresis comparator due to the set values of the threshold current value Ith decreases due to an increase in power supply noise.

  An object of the present invention is to provide an optical pulse detection circuit and an electronic device that can prevent a decrease in hysteresis of a hysteresis comparator due to an increase in power supply noise.

  In order to solve the above problems, an optical pulse detection circuit according to an aspect of the present invention includes a first light receiving element that converts pulsed light into a pulse electric signal, and a second light receiving element that is shielded from light and supplies the light shielded electric signal. And, during the non-reception period in which the first light receiving element does not receive the pulsed light, the path of the pulse electrical signal and the light-shielded electrical signal is blocked to suppress its own offset, and in the reception period in which the pulsed light is received. A first capacitor that maintains a state in which the offset is suppressed and includes a hysteresis comparator that reconnects the path of the pulse electrical signal and the light-shielded electrical signal, and injects noise of a power source into the path of the pulse electrical signal An element is provided between the first light receiving element and the power source.

  According to one aspect of the present invention, it is possible to prevent a decrease in hysteresis of the hysteresis comparator due to an increase in power supply noise.

1 is a circuit diagram of an optical pulse detection circuit according to Embodiment 1. FIG. (A)-(g) is a timing chart which shows the operation | movement at the time of the detection of the said optical pulse detection circuit. (A)-(g) is a timing chart which shows the operation | movement at the time of the non-detection of the said optical pulse detection circuit. It is a graph which shows the detection distance characteristic with respect to the power supply noise amplitude of the said optical pulse detection circuit. It is a graph which shows the hysteresis of distance conversion with respect to the power supply noise amplitude of the said optical pulse detection circuit. It is a graph which shows the other detection distance characteristic with respect to the power supply noise amplitude of the said optical pulse detection circuit. It is a graph which shows the other hysteresis of distance conversion with respect to the power supply noise amplitude of the said optical pulse detection circuit. 6 is a circuit diagram of an optical pulse detection circuit according to Embodiment 2. FIG. FIG. 6 is a circuit diagram of an optical pulse detection circuit according to a third embodiment. FIG. 6 is a circuit diagram of an optical pulse detection circuit according to a fourth embodiment. FIG. 9 is a circuit diagram of an object detection sensor according to a fifth embodiment. It is a circuit diagram of a signal processing circuit provided in the object detection sensor. It is a timing chart which shows the transition timing to the detection state from the non-detection state of the said object detection sensor. It is a timing chart which shows the transition timing from the detection state of the said object detection sensor to a non-detection state. (A) is a figure which shows the capacitor structure of the optical pulse detection circuit which concerns on Embodiment 6, (b) is a circuit diagram for demonstrating the said optical pulse detection circuit. (A)-(i) is a flowchart for demonstrating operation | movement of the optical pulse detection circuit which concerns on Embodiment 7. FIG. It is a circuit diagram of the conventional optical pulse detection circuit. It is a circuit diagram of a hysteresis comparator provided in the optical pulse detection circuit. (A)-(g) is a timing chart which shows the operation | movement at the time of the detection when there is no power supply noise of the said optical pulse detection circuit. (A)-(g) is a timing chart which shows the operation | movement at the time of the non-detection in case there is no power supply noise of the said optical pulse detection circuit. (A)-(g) is a timing chart which shows the operation | movement at the time of detection when the power supply noise of the said optical pulse detection circuit exists. (A)-(g) is a timing chart which shows the operation | movement at the time of non-detection in case the power supply noise of the said optical pulse detection circuit exists. It is a figure which shows the calculation formula of a detection distance and a non-detection distance. It is a graph which shows the characteristic of the detection distance when the power supply noise of the said optical pulse detection circuit exists. It is a graph which shows the hysteresis of distance conversion with respect to the power supply noise amplitude of the said optical pulse detection circuit.

  Hereinafter, embodiments of the present invention will be described in detail.

Embodiment 1
(Configuration of optical pulse detection circuit 1)
FIG. 1 is a circuit diagram of an optical pulse detection circuit 1 according to the first embodiment.

  The optical pulse detection circuit 1 includes a light emitting element driving circuit 6. The light emitting element driving circuit 6 drives the light emitting element 5 by a signal S11 representing a light emitting element current having a certain period. The light emitting element 5 driven by the light emitting element driving circuit 6 irradiates the object D with the irradiation pulse light L1. The reflected pulsed light L2 (pulsed light, signal S12) obtained by reflecting the irradiation pulsed light L1 by the detection object D is received by the light receiving element 2a (first light receiving element) provided in the light receiving amplifier circuit 7 to be a pulse current signal. (Pulse electric signal). The pulse current signal is converted into a pulse voltage signal S13 (pulse electric signal) by a transimpedance amplifier 4a (first transimpedance amplifier) provided in the light receiving amplifier circuit 7. The pulse voltage signal S13 converted by the transimpedance amplifier 4a is input to the hysteresis comparator 3.

  In the present embodiment, a capacitive element C1 (first capacitive element) is provided between the light receiving element 2a and the power supply line L (power supply). The power supply line L is a power supply line related to the entire optical pulse detection circuit 1. The power supply line used for the reference voltage source 401 described above with reference to FIG.

  The dummy amplifier circuit 8 includes a dummy light receiving element 2b (second light receiving element) shielded by the light shielding plate 9. A light shielding current signal (light shielding electrical signal) is supplied from the dummy light receiving element 2b shielded by the light shielding plate 9 to the transimpedance amplifier 4b (second transimpedance amplifier). The light-shielded current signal is converted into a light-shielded voltage signal S17 (light-shielded electrical signal) by a transimpedance amplifier 4b provided in the dummy amplifier circuit 8. The shading voltage signal S17 converted by the transimpedance amplifier 4b is input to the hysteresis comparator 3.

  The hysteresis comparator 3 outputs a comparator output signal Vcmp based on the pulse voltage signal S13 converted by the transimpedance amplifier 4a, the shading voltage signal S17 converted by the transimpedance amplifier 4b, and the threshold current value Ith. The hysteresis comparator 3 has a configuration similar to that described above with reference to FIG.

  The hysteresis comparator 3 suppresses its own offset by blocking the path of the pulse voltage signal S13 and the light-shielding voltage signal S17 during the non-reception period in which the light receiving element 2a does not receive the reflected pulsed light L2. The hysteresis comparator 3 maintains the state in which the offset is suppressed during the reception period in which the light receiving element 2a receives the reflected pulsed light L2, and reconnects the paths of the pulse voltage signal S13 and the light shielding voltage signal S17.

  The capacitive element C1 provided between the light receiving element 2a and the power supply line L injects noise from the power supply line L into the path of the pulse voltage signal S13.

(Operation of optical pulse detection circuit 1)
FIGS. 2A to 2G are timing charts showing operations at the time of detection by the optical pulse detection circuit 1.

  FIG. 2 corresponds to FIG. 15 described above, and the signal light component Ion obtained by subtracting the power supply noise component Ioc and the normal power supply noise component Ipd from the peak value of the signal S21 representing the differential current Idiff at the time of detection determination is the smallest. (A state where the detection distance becomes long).

  The difference from FIG. 15 is that the noise injected through the capacitive element C1 between the light receiving element 2a and the power supply line L is superimposed on the signal S14 representing the differential current Idiff. As a result, the normal power noise component Ipd increases, and the ratio of the offset cancel power noise component Ioc to the normal power noise component Ipd decreases.

  FIGS. 3A to 3G are timing charts showing the operation when the optical pulse detection circuit 1 is not detected.

  FIG. 3 corresponds to FIG. 16 described above, and the signal light component Ioff obtained by subtracting the power supply noise component Ioc and the normal power supply noise component Ipd from the peak value of the signal S14 representing the differential current Idiff at the time of non-detection determination is the highest. A state in which the detection distance increases (a state in which the detection distance decreases) is shown.

  The difference from FIG. 16 is that the noise injected through the capacitive element C1 between the light receiving element 2a and the power supply line L is superimposed on the signal S14 representing the differential current Idiff, as in FIG. . As a result, the normal power noise component Ipd increases, and the ratio of the offset cancel power noise component Ioc to the normal power noise component Ipd decreases.

  As shown in FIGS. 2 and 3, noise is injected from the power supply line L through the capacitive element C1, and the normal-time power supply noise component Ipd superimposed on the differential current Idiff of the hysteresis comparator 3 is increased, thereby detecting detection. The ratio of the offset noise power noise component Ioc to the hysteresis can be reduced both at the time of non-detection determination.

  As shown in FIG. 23, when the hysteresis is defined as Loff−Lon based on the detection distance Lon and the non-detection distance Loff (Equation 3), the power noise component Ipd during normal time is compared with the power noise component Ioc during offset cancellation. It can be seen that a decrease in hysteresis with respect to power supply noise can be suppressed by increasing the value.

  FIG. 4 is a graph showing the detection distance characteristic with respect to the power supply noise amplitude of the optical pulse detection circuit 1. The horizontal axis represents power supply noise amplitude (mV), and the vertical axis represents the detection distance. The characteristic of the detection distance when Gpd of Gm other than the normal period with respect to power supply noise is set to twice Gc of Gm in the offset cancellation period with respect to power supply noise is shown. As shown in FIG. 4, the characteristic of the detection distance is represented by a curve G4 corresponding to the detection distance Lon and a curve G5 corresponding to the non-detection distance Loff.

  FIG. 5 is a graph showing the distance-converted hysteresis with respect to the power supply noise amplitude of the optical pulse detection circuit 1. The horizontal axis represents the power supply noise amplitude (mV), and the vertical axis represents the absolute value of hysteresis converted to the detection distance. The curve G6 corresponds to a value obtained by subtracting a value corresponding to the curve G4 from a value corresponding to the curve G5 shown in FIG. 4, and a hysteresis is obtained by a difference between a detection distance corresponding to Lon and a detection distance corresponding to Loff. The absolute value of hysteresis converted to the distance of the comparator 3 is shown.

  FIG. 5 shows an aspect in which the decrease in the hysteresis of the curve G6 due to the increase in power supply noise amplitude is delayed from the decrease in the hysteresis of the conventional curve G3 shown in FIG. 19 due to the effect that Gpd is twice that of Goc. It is. Thus, according to the present embodiment, a decrease in hysteresis of the hysteresis comparator 3 due to an increase in power supply noise is prevented.

  FIG. 6 is a graph showing another detection distance characteristic with respect to the power supply noise amplitude of the optical pulse detection circuit 1. The horizontal axis represents power supply noise amplitude (mV), and the vertical axis represents the detection distance. The characteristic of the detection distance when Gpd of Gm other than the normal period with respect to the power supply voltage is set to 3 times Goc of Gm in the offset cancellation period with respect to the power supply voltage is shown. The characteristic of the detection distance is represented by a curve G7 corresponding to the detection distance Lon and a curve G8 corresponding to the non-detection distance Loff, as shown in FIG.

  FIG. 7 is a graph showing another hysteresis of distance conversion with respect to the power supply noise amplitude of the optical pulse detection circuit 1. The horizontal axis represents the power supply noise amplitude (mV), and the vertical axis represents the absolute value of hysteresis converted to the detection distance.

  The effect that Gpd is three times that of Goc indicates that the hysteresis does not decrease to 120 mV, which is the limit of the power supply noise amplitude capable of hysteresis operation, as the power supply noise amplitude increases.

[Embodiment 2]
The following will describe another embodiment of the present invention with reference to FIG. For convenience of explanation, members having the same functions as those described in the embodiment are given the same reference numerals, and descriptions thereof are omitted.

  FIG. 8 is a circuit diagram of an optical pulse detection circuit 1a according to the second embodiment. The difference from the optical pulse detection circuit 1 described in the first embodiment is that a fully differential operational amplifier 10 is provided. The pulse voltage signal S13 supplied from the transimpedance amplifier 4a is input to the non-inverting input terminal of the fully differential operational amplifier 10. The shading voltage signal S17 supplied from the transimpedance amplifier 4b is input to the inverting input terminal of the fully differential operational amplifier 10. Two outputs of the fully differential operational amplifier 10 are connected to the capacitive element 402 and the capacitive element 403, respectively.

  By inserting the fully differential operational amplifier 10 before the hysteresis comparator 3, the gain adjustment of the optical pulse detection circuit 1a is facilitated. In addition, since the total gain of the optical pulse detection circuit 1a can be increased, the capacitive element and the light receiving element connected to the power supply voltage can be reduced, and the size and cost can be reduced.

[Embodiment 3]
FIG. 9 is a circuit diagram of an optical pulse detection circuit 1b according to the third embodiment. About the member which has the same function as the member demonstrated in the said embodiment, the same code | symbol is attached and the description is abbreviate | omitted.

  In the optical pulse detection circuit 1 of the first embodiment shown in FIG. 1 and the optical pulse detection circuit 1a of the second embodiment shown in FIG. 8, instead of providing the capacitive element C1 between the light receiving element 2a and the power supply line L, A capacitive element C1 may be provided between the dummy light receiving element 2b and the power supply line L. This is because the hysteresis comparator 3 differentially inputs the pulse voltage signal S13 and the light-shielding voltage signal S17, so that the same effect as in the first and second embodiments can be obtained.

  Capacitance elements may be provided both between the light receiving element 2a and the power supply line L and between the dummy light receiving element 2b and the power supply line L.

[Embodiment 4]
FIG. 10 is a circuit diagram of an optical pulse detection circuit 1c according to the fourth embodiment. About the member which has the same function as the member demonstrated in the said embodiment, the same code | symbol is attached and the description is abbreviate | omitted.

  In the first to third embodiments, the dummy light receiving element 2b can be substituted with the dummy capacitive element Cd. It is preferable to set the capacitance value of the dummy capacitance element Cd to the same capacitance value as that of the dummy light receiving element 2b, because the dummy capacitance element Cd can obtain the same AC characteristics as the dummy light receiving element 2b. When the optical pulse detection circuit 1c is formed in the semiconductor chip, since the capacitance value of the light receiving element is smaller than the capacitance value using the gate oxide film of the MOS, the dummy light receiving element 2b is replaced by the dummy capacitance element Cd. The pulse detection circuit 1c can be reduced in size and cost.

[Embodiment 5]
FIG. 11 is a circuit diagram of the object detection sensor 11 according to the fifth embodiment. FIG. 12 is a circuit diagram of the signal processing circuit 13 provided in the object detection sensor 11. FIG. 13 is a timing chart showing the transition timing of the object detection sensor 11 from the non-detection state to the detection state. FIG. 14 is a timing chart showing the transition timing from the detection state of the object detection sensor 11 to the non-detection state. About the member which has the same function as the member demonstrated in the said embodiment, the same code | symbol is attached and the description is abbreviate | omitted.

  The optical pulse detection circuit configured as described in the first to fourth embodiments, the light emission pulse, offset cancel timing control circuit, the logic circuit that holds the detection / non-detection determination, and the irradiation pulse light L1 and the reflected pulse light L2 (or By integrating the optical lenses 12a and 12b for condensing the transmitted pulsed light), the reflected light detection type or the transmitted light detection type object that makes it possible to reduce the decrease in hysteresis due to power supply noise. The detection sensor 11 can be realized.

  The object detection sensor 11 includes an optical pulse detection circuit 1. The object detection sensor 11 is provided with an optical lens 12a that condenses the irradiation pulsed light L1 and an optical lens 12b that condenses the reflected pulsed light L2.

  The object detection sensor 11 generates an offset cancel signal S37 based on the oscillation circuit 15 that generates the clock signal S38, and supplies the offset cancel signal S37 to the hysteresis comparator 3, and generates a light emitting element driving signal S35. A timing generation circuit 14 that supplies the drive circuit 6 to generate a threshold switching signal S32 and supplies the threshold switching signal S32 to the threshold current switching circuit 16, a comparator output signal Vcmp from the hysteresis comparator 3, a synchronization gate signal S36 from the timing generation circuit 14, The signal processing circuit 13 generates a signal processing circuit output signal S33 based on the reset signal S34 and supplies the signal processing circuit output signal S33 to the timing generation circuit 14, and outputs the output signal S39 based on the detection state output signal S31 from the timing generation circuit 14. And an output circuit 17.

  The signal processing circuit 13 includes an AND circuit 18 to which the comparator output signal Vcmp and the synchronization gate signal S36 are supplied, and an SR latch circuit that outputs the signal processing circuit output signal S33 based on the reset signal S34 and the output of the AND circuit 18. 19. Based on the signal processing circuit output signal S33 at the timing A1 shown in FIGS. 13 and 14, the detection state of the object detection sensor 11 is determined.

  Further, by mounting the object detection sensor on an electronic device such as a copying machine or a portable terminal, it is possible to prevent a chattering malfunction due to a decrease in hysteresis, thereby realizing a sensing operation with high malfunction tolerance.

[Embodiment 6]
FIG. 15A is a diagram showing a capacitor structure of the optical pulse detection circuit according to the sixth embodiment, and FIG. 15B is a circuit diagram for explaining the optical pulse detection circuit.

  When the capacitive element C1 connected to the power supply line L is mounted in the semiconductor chip, it can be mounted using a parasitic capacitance having a double polycapacitor DPC structure as shown in FIG.

  The double polycapacitor DPC includes an N-type well (NWell) formed on a P-type silicon substrate (Psub) and polysilicon GP · FG. A thin insulating film is formed between the polysilicon GP and the polysilicon FG (not shown), and a capacitance that is inversely proportional to the thickness of the insulating film exists. An insulating film thicker than the insulating film between the polysilicon GP and the polysilicon FG (not shown) is formed between the polysilicon GP and the N-type well (NWell), and is inversely proportional to the thickness of the insulating film. There is a parasitic capacitance. With this configuration, the double polycapacitor DPC can be used as a capacitor having the polysilicon FG and the polysilicon GP as electrodes.

  In this case, the area of the capacitive element C1 connected to the power supply line L can be reduced, leading to a reduction in size and cost of the optical pulse detection circuit. In a place where the actual capacitive element C1 is used, a capacitive element used for a transimpedance amplifier or the like can be used as the capacitive element C1.

[Embodiment 7]
FIGS. 16A to 16I are flowcharts for explaining the operation of the optical pulse detection circuit according to the seventh embodiment.

  In the first to sixth embodiments, the noise peak period when the normal power supply noise component Ipd as shown in FIG. 2 is large by performing noise determination as shown in the timing chart of FIG. Can be invalidated. For this reason, the detection signal component can be determined with a large period, and the hysteresis can be kept higher.

  First, after the offset cancel period in which the offset cancel signal S16 is on ends, the threshold current value Ith is changed from Ithon to Ithoff. Then, the signal S21 representing the differential current Idiff is compared with the threshold current value Ith = Ithoff in the noise determination timing period in which the noise determination timing signal S18 is on.

  When the signal S21 becomes larger than Ithoff and the comparator output signal Vcmp appears, the noise determination holding signal S19 is turned on and held until one cycle is completed. Thereafter, the threshold current value Ith is returned from Ithoff to Ithon. Then, the signal S21 representing the differential current Idiff is compared with the threshold current value Ith = Ithon. When the signal S21 reaches Iton, the comparator output signal Vcmp is turned on. However, when the noise determination holding signal S19 is held on, the comparator output signal Vcmp is invalidated.

  When the signal S21 does not reach Ithoff, the noise determination holding signal S19 is held off until one cycle is completed. Thereafter, the threshold current value Ith is returned from Ithoff to Ithon. Then, the signal S21 representing the differential current Idiff is compared with the threshold current value Ith = Ithon. When the signal S21 has reached Iton, the comparator output signal Vcmp is turned on and output from the hysteresis comparator 3.

  The pulse light receiving circuits according to the first to seventh embodiments can suppress a reduction in hysteresis due to power supply noise with a small number of components, and can improve stability at a small size and at low cost.

[Summary]
The optical pulse detection circuits 1 and 1a according to the first aspect of the present invention are shielded from light by a first light receiving element (light receiving element 2a) that converts pulsed light (reflected pulsed light L2) into a pulse electric signal (pulse current signal). A second light receiving element (dummy light receiving element 2b) for supplying a light shielding electric signal (light shielding current signal) and a non-reception period in which the first light receiving element (light receiving element 2a) does not receive the pulsed light (reflected pulsed light L2). By blocking the path of the pulse electric signal (pulse voltage signal S13) and the light shielding electric signal (light shielding voltage signal S17), the offset of itself is suppressed, and during the reception period of receiving the pulsed light (reflected pulsed light L2). , Maintaining the state in which the offset is suppressed, and reconnecting the path of the pulse electric signal (pulse voltage signal S13) and the light shielding electric signal (light shielding voltage signal S17). And a hysteresis comparator 3 for injecting noise of the power supply (power supply line L) into at least one of the path of the pulse electric signal (pulse voltage signal S13) and the path of the light shielding electric signal (light shielding voltage signal S17). An element C1 is provided.

  According to said structure, the noise inject | poured through the capacitive element from the power supply is superimposed on at least one of a pulse electric signal and a light-shielding electric signal. For this reason, the power noise component at the normal time increases, and the ratio of the power noise component at the time of offset cancellation to the hysteresis decreases. Therefore, it is possible to prevent the hysteresis comparator from decreasing the hysteresis due to an increase in power supply noise.

  The optical pulse detection circuit 1a according to the second aspect of the present invention is the fully differential operational amplifier according to the first aspect, which amplifies a difference between the pulse electric signal (pulse voltage signal S13) and the light shielding electric signal (light shielding voltage signal S17). 10 and the output from the fully differential operational amplifier 10 may be input to the hysteresis comparator 3.

  According to said structure, the gain adjustment of the optical pulse detection circuit 1a becomes easy. In addition, since the total gain of the optical pulse detection circuit 1a can be increased, the capacitive element and the light receiving element connected to the power supply voltage can be reduced, and the size and cost can be reduced.

  The optical pulse detection circuit according to Aspect 3 of the present invention is the optical pulse detection circuit according to Aspect 1, because the capacitive element C1 injects noise of the power supply (power supply line L) into the path of the pulse electric signal (pulse voltage signal S13). Are provided between the first light receiving element (light receiving element 2a) and the power supply (power supply line L).

  According to said structure, the noise inject | poured through the capacitive element from the power supply is superimposed on a pulse electrical signal. For this reason, the power noise component at the normal time increases, and the ratio of the power noise component at the time of offset cancellation to the hysteresis decreases. Therefore, it is possible to prevent the hysteresis comparator from decreasing the hysteresis due to an increase in power supply noise.

  In the optical pulse detection circuit according to aspect 4 of the present invention, in the above aspect 1, the second light receiving element (dummy light receiving element 2b) may be a dummy capacitive element.

  According to said structure, an optical pulse detection circuit can be reduced in size and cost.

  In the optical pulse detection circuits 1 and 1a according to the aspect 5 of the present invention, in the above aspect 1, the first light receiving element (light receiving element 2a) converts the pulsed light (reflected pulsed light L2) into a pulse current signal. A second light-receiving element (dummy light-receiving element 2b) supplies a light-shielding current signal, converts the pulse current signal into a pulse voltage signal S13, and the light-shielding current signal as a light-shielding voltage. You may further provide the 2nd transimpedance amplifier (transimpedance amplifier 4b) converted into signal S17.

  According to the above configuration, it is possible to prevent the hysteresis comparator from decreasing due to an increase in power supply noise with a simple configuration.

  An electronic device according to aspect 6 of the present invention includes the optical pulse detection circuit according to any one of aspects 1 to 5 of the present invention.

  The present invention is not limited to the above-described embodiments, and various modifications are possible within the scope shown in the claims, and embodiments obtained by appropriately combining technical means disclosed in different embodiments. Is also included in the technical scope of the present invention. Furthermore, a new technical feature can be formed by combining the technical means disclosed in each embodiment.

  INDUSTRIAL APPLICABILITY The present invention can be used in an optical pulse detection circuit and an electronic device that detect an optical pulse, and in particular, an optical pulse detection that is a main component of a small object detection device to be mounted on a portable device such as a cellular phone. It can be used for circuits and electronic devices.

1 Optical Pulse Detection Circuit 2a Light Receiving Element (First Light Receiving Element)
2b Dummy light receiving element (second light receiving element)
3 Hysteresis Comparator 4a Transimpedance Amplifier (First Transimpedance Amplifier)
4b Transimpedance amplifier (second transimpedance amplifier)
DESCRIPTION OF SYMBOLS 5 Light emitting element 6 Light emitting element drive circuit 7 Light reception amplifier circuit 8 Dummy amplifier circuit 9 Shading board 10 Fully differential operational amplifier 11 Object detection sensor 12a, 12b Lens 13 Signal processing circuit 14 Timing generation circuit 15 Oscillation circuit 16 Threshold current switching circuit 17 Output Circuit 18 AND circuit 19 SR latch circuit C1 Capacitance element (first capacitance element)
L Power line L1 Irradiation pulsed light L2 Reflected pulsed light (pulsed light)
S1 Pulse current signal (pulse electric signal)
S2 Pulse voltage signal (pulse electrical signal)
S3 Shading current signal (shading electrical signal)
S4 Shading voltage signal (shading electrical signal)
D Object to be detected

Claims (5)

A first light receiving element that converts pulsed light into a pulsed electrical signal;
A second light-receiving element that is shielded from light and supplies a light-shielded electrical signal;
The first light receiving element suppresses its own offset by blocking the path of the pulse electric signal and the light shielding electric signal in a non-reception period in which the pulse light is not received, and in the reception period in which the pulse light is received, A hysteresis comparator that maintains the state in which the offset is suppressed and reconnects the path of the pulse electrical signal and the light-shielded electrical signal,
An optical pulse detection circuit, wherein a capacitive element for injecting power source noise is provided in at least one of the path of the pulse electric signal and the path of the light shielding electric signal. Further comprising a fully differential operational amplifier for amplifying a difference between the pulse electrical signal and the light shielding electrical signal;
The optical pulse detection circuit according to claim 1, wherein an output from the fully differential operational amplifier is input to the hysteresis comparator.   2. The optical pulse detection circuit according to claim 1, wherein the capacitive element is provided between the first light receiving element and the power supply in order to inject noise of the power supply into a path of the pulse electric signal.   The optical pulse detection circuit according to claim 1, wherein the second light receiving element is a dummy capacitive element.   An electronic apparatus comprising the optical pulse detection circuit according to any one of claims 1 to 4.

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