Classifications

• • G—PHYSICS
  • G01—MEASURING; TESTING
  • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
  • G01S17/00—Systems using the reflection or reradiation of electromagnetic waves other than radio waves, e.g. lidar systems
  • G01S17/02—Systems using the reflection of electromagnetic waves other than radio waves
  • G01S17/06—Systems determining position data of a target
  • G01S17/08—Systems determining position data of a target for measuring distance only
  • G01S17/32—Systems determining position data of a target for measuring distance only using transmission of continuous waves, whether amplitude-, frequency-, or phase-modulated, or unmodulated
  • G01S17/36—Systems determining position data of a target for measuring distance only using transmission of continuous waves, whether amplitude-, frequency-, or phase-modulated, or unmodulated with phase comparison between the received signal and the contemporaneously transmitted signal
• • G—PHYSICS
  • G01—MEASURING; TESTING
  • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
  • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
  • G01S7/48—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S17/00
  • G01S7/491—Details of non-pulse systems
• • G—PHYSICS
  • G01—MEASURING; TESTING
  • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
  • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
  • G01S7/48—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S17/00
  • G01S7/491—Details of non-pulse systems
  • G01S7/4911—Transmitters
• • G—PHYSICS
  • G01—MEASURING; TESTING
  • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
  • G01S17/00—Systems using the reflection or reradiation of electromagnetic waves other than radio waves, e.g. lidar systems
  • G01S17/02—Systems using the reflection of electromagnetic waves other than radio waves
  • G01S17/06—Systems determining position data of a target
  • G01S17/42—Simultaneous measurement of distance and other co-ordinates

Definitions

• the present invention relates to a method for determining a distance to an object, comprising the steps:
• Emitting a transmitted light beam from a light emitter Emitting a transmitted light beam from a light emitter
• the invention also relates to a device for determining a distance to an object, comprising a light transmitter for emitting a transmitted light beam, having a light receiver for receiving a received light beam, wherein the received light beam is formed by reflection of the transmitted light beam on the object, and having an evaluation unit for determining the distance of the object based on a transit time of the transmit and receive light beams, wherein the transmit light beam is amplitude modulated with a square waveform modulation signal, and wherein the modulation signal has a plurality of square pulses occurring in a plurality of groups.
• a method and a device of this kind are known from DE 40 27 990 C1.
• the invention relates to a so-called laser scanner which is designed to measure a spatial area and / or an object three-dimensionally.
• a laser scanner is described, for example, in DE 103 61 870 AI.
• This known laser scanner has a measuring head, which is rotatable about a vertical axis.
• the measuring head includes a rotor which is rotatable about a horizontal axis.
• the rotor emits a transmitted light beam and receives a reception beam of light reflected from an object.
• Reflection in the sense of the present invention does not necessarily have to be a total reflection, but may also be a diffuse reflection or scattering of the emitted light beam.
• the distance between the measuring head and the object is determined.
• the rotation of the rotor and the measuring head makes it possible to move the transmitted light beam through 360 ° in the azimuth and about 270 ° in the elevation. In this way it is possible to measure almost the entire space around the known laser scanner.
• Typical applications for such laser scanners are the measurement of buildings (inside and / or outside), tunnels or the measurement of large objects, such as ship hulls.
• the determination of the transit time of the transmitted and received light beam is possible in various ways. Basically, a distinction is made between pulse transit time method and CW (Continuous Wave) method.
• the transmitted light beam contains only a short transmission pulse for each measuring process. The time is measured until the reflected pulse arrives in the receiver.
• CW Continuous Wave
• a (at least largely) continuous transmitted light beam is emitted and the transit time is determined by means of a phase shift between the transmitted and received light beam.
• the transmitted light beam is modulated in its amplitude by means of a modulation signal and the phase shift of the modulation signal in the emitted and received light beam is used for transit time determination.
• the higher the modulation frequency the more accurate the distance can be determined here.
• the unambiguity range decreases with increasing modulation frequency; because the phase shift between the transmitted and received light beam repeats after a phase pass of 360 °.
• the aforementioned DE 40 27 990 C1 therefore proposes a rangefinder with a modulated transmitted light beam according to the CW method, wherein the transmitted light beam is amplitude modulated with a rectangular wave modulation signal having a first, relatively high modulation frequency, and wherein this transmitted light beam after a certain number of periods the modulation signal is interrupted for a long period of time. These interruptions can be interpreted as an amplitude modulation with a second modulation signal with a second, lower modulation frequency.
• the transmitted light beam is amplitude-modulated with a first higher and a second lower modulation frequency, wherein the two different modulation frequencies determine the uniqueness range. This is significantly larger than when using only one modulation frequency.
• DE 43 03 804 AI the method according to DE 40 27 990 Cl is considered disadvantageous insofar as that is reduced by the amplitude modulation with the lower second modulation frequency over the duration of the entire signal period averaged transmission light intensity. This leads to a reduction of the signal / noise ratio and as a result that objects with a low reflectivity can no longer be measured.
• DE 43 03 804 A1 proposes to alternately modulate the transmission light beam with the higher first and lower second modulation frequencies, i. In each time interval, the transmitted light beam is modulated with only one of the two modulation frequencies.
• this method results in extended measurement times, since each object must be measured twice. The higher measuring time is particularly disadvantageous in the case of a laser scanner because the transmitted light beam can then only be pivoted relatively slowly.
• This object is achieved according to one aspect of the invention by a method and a device of the aforementioned type, wherein the groups of rectangular pulses occur at varying time intervals from each other and have varying numbers of rectangular pulses.
• the new method and the new device continue to be based on the principle of transit time measurement according to the CW method, ie the transit time is determined by means of a ner phase shift of the modulation signal in the received light beam relative to the modulation signal in the transmitted light beam determined. Furthermore, the new method and apparatus use a square-wave modulation signal to amplitude-modulate the transmitted light beam.
• DE 40 27 990 C1 mentioned at the outset has already taken into consideration a rectangular-wave-shaped modulation signal for amplitude modulation of a transmitted light beam. In practice, however, typically sinusoidal modulation signals are used.
• a rectangular-wave-shaped modulation signal has the advantage over a sinusoidal modulation signal that the modulation signal remains at its respective maximum value for the same signal amplitude (pulse peak) and the same modulation frequency for a longer time.
• the use of a square wave modulation signal allows a higher signal-to-noise ratio than the use of a comparable sinusoidal modulation signal Take advantage of modulation signal much better.
• the square wave-modulated transmitted light beam is not only periodically suppressed according to the new method, but the modulation signal itself is modulated in a manner such that the square pulses occur at varying time intervals with each other and with changing pulse numbers .
• the modulation signal is a binary rectangular signal (in the manner of a digital O-1 sequence), wherein the individual rectangular pulses occur with varying pulse-pause ratio and varying pulse accumulation.
• the square pulses may be pulse peaks of a non-binary square wave modulation signal, for example the pulse peaks of a quaternary square wave signal.
• the square-wave pulses of the modulation signal are distributed such that the modulation signal itself is frequency-modulated, preferably according to a periodically recurring pattern.
• the amplitude of the transmitted light beam is modulated with a modulation signal which, due to its own changing characteristics, includes a plurality of different modulation frequencies. These plurality of different modulation frequencies are not only the harmonic multiples which each square-wave signal contains due to the Fourier connection per se.
• the new modulation signal includes a multiplicity of different modulation frequencies, which in particular are smaller than the first harmonic of the square wave signal.
• the new modulation signal is thus a combined modulation signal with which the light transmitter can be controlled continuously.
• the different modulation frequencies which are contained in the new modulation signal are preferably evaluated at least approximately simultaneously so that, in principle, one measuring operation suffices for each distance measurement. Due to the high modulation frequencies contained in the combined modulation signal, the distance can be determined with high accuracy.
• the modulation signal also contains lower modulation frequencies, so that a large uniqueness range is obtained.
• the time intervals change periodically.
• the time intervals between the groups of square pulses become longer after a periodically repeating pattern and shorter.
• the periodically varying time intervals result in a modulation frequency in the rectangular waveform modulation signal that is small compared to the fundamental frequency of the rectangular waveform modulation signal.
• the low modulation frequency allows a large uniqueness range.
• this embodiment allows a higher peak load of the light transmitter with the same average light output, which results in a further improvement of the signal / noise ratio.
• the number of square pulses per group changes periodically.
• This configuration provides for a further "low" modulation frequency in the combined modulation signal and can therefore contribute to a further increase of the uniqueness range.
• ⁇ br/> ⁇ br/> Particularly advantageous is the combination of this embodiment with the preceding embodiment, wherein the periodically changing distances and the periodically changing number of square-wave pulses In this case, the larger time intervals between groups of square-wave pulses results from the smaller number of square-wave pulses per group, which simplifies the practical realization and allows a very good utilization of the available light output.
• the modulation signal is generated by adding a first square-wave modulation signal having a first modulation frequency and a second rectangular-wave modulation signal having a second modulation frequency, wherein the first modulation frequency is large compared to the second modulation frequency.
• the first modulation frequency is at least five times greater than the second modulation frequency.
• This embodiment allows a very simple and cost-effective generation of the new modulation signal and thus a simple and cost-effective implementation of the new device.
• Addition of the first and second modulation signals also reduces the number of unneeded "secondary frequencies" in the modulation signal in comparison to a principle also conceivable multiplication. As a result, the available light output is more focused on the usable and used modulation frequencies.
• a third square-wave modulation signal having a third modulation frequency is added to the first and second rectangular-wave modulation signals, the second and third modulation frequencies being different, and the first modulation frequency being also large compared to the third modulation frequency. It is particularly advantageous if the second and third modulation frequencies are approximately equal or close to each other.
• the difference between the second and third modulation frequency is substantially smaller than the difference between the second and the first modulation frequency or the difference between the third and the first modulation frequency.
• the first modulation frequency is about 125 MHz
• the second modulation frequency is about 15 MHz
• the third modulation frequency is about 13 MHz.
• This refinement has the advantage that a third modulation frequency is available for signal evaluation, as a result of which the uniqueness range can be further increased. It is particularly advantageous if the second and third modulation frequencies are relatively close to one another, as in the preferred exemplary embodiment, because in such cases, a beat arises whose frequency corresponds to the difference between the second and the third modulation frequency. This difference is very small compared to the actual frequencies of the modulation signals. As a result, the uniqueness range can be greatly increased without the need to separately provide the low beat frequency.
• the selection and tuning of the individual circuit components of the new device can be significantly simplified in this embodiment.
• the second and the third modulation signal have the same pulse amplitudes. This embodiment simplifies the signal evaluation and leads to a further improved light output. It is particularly advantageous if the second and third modulation frequencies are so close together that a beat frequency is available for signal evaluation.
• the first modulation signal has a greater pulse amplitude than the second modulation signal.
• the pulse amplitude of the first modulation signal is larger by about a factor of 2 than the pulse amplitudes of the second or third modulation signal, the latter being equal.
• This embodiment contributes to increasing the time intervals between the groups of rectangular pulses in the combined modulation signal, which at first sight results in a reduction of the average transmission power of the transmitted light beam.
• the pulse or peak power with which the light transmitter is operated increases. This is possible by the larger distances between the groups of rectangular pulses without destroying the light transmitter and helps to increase the signal / noise ratio in the useful signal again.
• all square-wave pulses of the modulation signal have an at least substantially equal pulse amplitude.
• the combined modulation signal is a binary signal, as is commonly used in the field of digital technology to represent a 0-1 sequence.
• the combined modulation signal could be a square wave signal having a plurality (n> 2) of pulse amplitude values.
• the preferred embodiment has the advantage that the combined modulation signal can be generated very simply and efficiently with the aid of digital circuits, the modulation signals to be combined and the combined modulation signal in this case being provided digitally as O-1 sequences.
• the maximum amplitude of the transmitted light beam can be exploited, which also contributes to an optimal use of the available light output.
• the square-wave modulation signal is generated with the aid of a digital circuit as a binary, rectangular-wave-shaped modulation signal.
• this embodiment allows a very simple and cost-effective implementation of the new method and the new device.
• the combined modulation signal in this embodiment can be varied very flexibly and adapted to different environments and / or measurement tasks.
• the square wave modulation signal is generated from at least two sinusoidal signals of different frequencies, the sinusoidal signals being respectively amplified and amplitude limited.
• the square-wave modulation signal is generated by means of analog circuit technology.
• This embodiment allows a very simple and cost-effective implementation of the new device using circuit components that were previously operated with sinusoidal signals.
• the new method in this embodiment can be very easily integrated into existing circuit concepts according to the prior art.
• the transit time of the transmitted and received light beam is determined on the basis of a phase difference of the modulation signal in the transmitted light beam and in the received light beam, the phase position of the modulation signal in the transmitted light beam being measured at the light transmitter.
• the phase position of the modulation signal in the transmitted light beam is determined metrologically and this phase is used as a reference for the transit time determination.
• the phase position currently present in the transmitted light beam is used to determine the transit time.
• the light transmitter includes a laser diode and if the phase angle of the control current flowing through the laser diode is measured.
• the phasing of the tax Erstroms can be easily determined and it represents the actual instantaneous phase position of the modulation signal in the transmitted light beam with high accuracy. This embodiment allows a very high accuracy of measurement, because a phase drift in the region of the light emitter is eliminated from the distance determination.
• FIG. 1 shows a laser scanner according to a preferred embodiment of the invention
• FIG. 2 shows a simplified representation of a plurality of modulation signals that can be used in the laser scanner according to FIG. 1,
• FIG. 4 shows the frequency spectrum of the modulation signal from FIG. 3, FIG.
• Fig. 6 shows a circuit for generating the new modulation signal according to another embodiment of the invention.
• a laser scanner in its entirety is designated by the reference numeral 10.
• the laser scanner 10 is a preferred embodiment of a device according to the present invention.
• the new device and the new method can also be applied to other devices in which a distance to an object by means of a transmitted light beam and a Receiving light beam to be determined.
• the invention is not limited to the use of light beams in the narrower sense (preferred wavelengths between 300 and 1000 nm), but can in principle be realized with electromagnetic waves from a larger wavelength range, as long as a quasi-optical propagation is present.
• the term light beam used here therefore also includes such electromagnetic waves.
• the laser scanner 10 includes a light emitter 12 and a light receiver 14, both of which are connected to an evaluation and control unit 16.
• the light emitter 12 includes a laser diode 13 (see illustration in FIGS. 5 and 6) adapted to emit a laser beam 18 to illuminate an object point on an object 20.
• the laser beam 18 is amplitude modulated here with a rectangular wave modulation signal, as explained in more detail below with reference to Figures 2 to 6.
• the transmitted light beam has a wavelength of about 790 nm in a preferred embodiment.
• the laser beam 18 is deflected here via a mirror 22 to the object 20.
• the reference numeral 24 denotes a received light beam which is reflected by the object 20 and which is deflected via the mirror 22 to the receiver 14.
• the evaluation and control unit 16 is designed to determine the distance of the laser scanner 10 to the illuminated point on the object 20 from the transit time of the emitted laser beam 18 and the received reflected beam 24. For this purpose, a phase shift between the transmitted light beam 18 and the received light beam 24 is determined and evaluated.
• the mirror 22 is arranged here on the front end face of a cylinder 26 which is connected via a shaft 28 with a rotary drive 30. With the aid of the rotary drive 30, the mirror 22 can be rotated about a rotation axis 32. The respective rotational position of the mirror 22 can be determined with the aid of an encoder 34. The output signals of the encoder 34 are also fed to the evaluation and control unit 16, which is not shown here for reasons of clarity.
• the axis of rotation 32 is arranged horizontally and the mirror 22 is inclined relative to the axis of rotation 32 at an angle of approximately 45 °.
• a rotation of the mirror 22 about the horizontal axis 32 therefore results in the transmitted light beam 18 being deflected along a vertical plane (elevation) which is perpendicular to the axis of rotation 32.
• the transmitted light beam 18 effectively forms a fan with which the spatial region 36 is scanned in a vertical plane.
• the laser scanner 10 here has a housing structure which essentially has two housing parts 38, 40.
• the housing parts 38, 40 are arranged on a common base plate 42.
• the transmitter 12, the receiver 14 and the evaluation and control unit 16 are housed in the housing part 38 shown on the left in Fig. 1.
• the housing part 40 shown on the right in FIG. 1 accommodates the rotary drive 30 with the encoder 34 and the cylinder 26, wherein the cylinder 26 protrudes with the mirror 22 from the housing part 40, so that the mirror 22 approximately centrally between the two housing parts 38, 40th is arranged.
• the base plate 42 is arranged on a rotary drive 44 which sits on a stand 46.
• the stand 46 is adjustable in height and has a scale 48 in order to make a reproducible height adjustment can.
• the reference numeral 50 denotes a further encoder, with the aid of which the rotational position of the rotary drive 44 can be determined.
• the output signals of the encoder 50 are likewise supplied to the evaluation and control unit 16 (not shown here).
• the rotary drive 44 allows rotation of the laser scanner 10 about a vertical axis 52 which, together with the axis of rotation 32, defines an axis of intersection.
• the intercept point is approximately centered on the mirror 22 and, in preferred embodiments, defines the origin of a coordinate system to which all range readings are related.
• the vertical "scanning fan" which is generated with the aid of the rotating mirror 22, can be rotated by up to 360 ° in the azimuth, so that the transmitted light beam 18 can illuminate almost every object point in the vicinity of the laser scanner 10. Shading only takes place downwards through the base plate 42, so that the viewing angle of the laser scanner 10 after is limited.
• the evaluation and control unit 16 includes in this embodiment, a microprocessor 54 and an FPGA (field programmable gate array) 56.
• the FPGA 56 generates here a binary square waveform modulation signal with which the laser diode of the light emitter 12 is driven.
• the microprocessor 54 reads digitized receive data from the light receiver 14 and uses this data to determine the distance d between the laser scanner 10 and the object 20.
• the microprocessor 54 and the FPGA 56 communicate with each other, the microprocessor 54 inter alia including the phase information of the modulation signal for the laser Runtime determination receives.
• FIG. 2 shows three idealized modulation signals 60, 62, 64 over a time axis.
• the first modulation signal 60 is a rectangular waveform modulation signal having a fundamental frequency of, for example, 125 MHz.
• the second modulation signal 62 is a rectangular wave signal having a fundamental frequency of 13 MHz, and the third modulation signal 64 is a rectangular wave signal having a fundamental frequency of 15 MHz.
• Reference numeral 66 represents a sum signal resulting from an addition of the three modulation signals 60, 62, 64.
• the sum signal 66 is a rectangular wave signal having a number of square pulses 68, 70 which follow one another at the fundamental frequency of the first modulation signal 60.
• the square pulses 68, 70 of the sum signal 66 have different pulse heights.
• the sum signal 66 is therefore a combined signal in which 60 additional signal frequencies are included in addition to the base frequency of the first modulation signal.
• the sum signal 66 includes a signal frequency corresponding to the difference of the base frequencies of the second and third modulation signals 62, 64. This further signal frequency is reflected in the periodic pattern with which the highest square pulses 68 exceed the threshold indicated at 72.
• the sum signal 66 contains a signal frequency which corresponds to the mean value of the fundamental frequencies of the two modulation signals 62, 64.
• the sum signal includes a signal frequency of about 2 MHz (15 MHz-13 MHz) and a signal frequency of about 14 MHz (15 MHz + 13 MHz / 2).
• the sum signal 66 This results in a modulation signal for an amplitude modulation of the transmitted light beam 18, the relatively high signal frequency of 125 MHz providing a fine phase for the exact determination of the distance d, while the low signal frequency of 2 MHz provides a coarse phase for a large uniqueness range. It is understood that these different signal frequencies and phase differences in the evaluation and control unit of the new device are evaluated accordingly, preferably in each individual measurement cycle.
• the pulse amplitude of the first modulation signal 60 is twice as high as the pulse amplitude of the second and third modulation signals 62, 64.
• the sum signal 66 is a quaternary signal in which the rectangular pulses 68, 70 assume one of four possible pulse values. Basically, this quaternary signal 66 can be used as a modulation signal for the transmitted light beam.
• the quaternary sum signal 66 that is used, but a binary modulation signal 74 resulting from the sum signal 66, using only the rectangular pulses 68 that extend beyond the pulse value at reference numeral 72.
• a binary modulation signal 74 resulting from the sum signal 66, using only the rectangular pulses 68 that extend beyond the pulse value at reference numeral 72.
• the "high" pulse peaks of the sum signal 66 are used, which are designated by the reference numeral 68 'in Fig. 2.
• the lower part of the signal 66 is "cut off”.
• the time intervals PA between the rectangular pulses 68 ' change periodically.
• the number of square pulses 68 'per group 76 varies from square pulses 68'.
• the modulation signal 74 is therefore a frequency-modulated, square-wave, binary signal whose fundamental frequency corresponds to the fundamental frequency of the first modulation signal 60 (in this case, 125 MHz). This fundamental frequency is frequency-modulated with the beat frequency resulting from the frequency difference of the second and third modulation signals 62, 64.
• FIG. 3 shows a modulation signal calculated with the aid of a digital circuit, which corresponds to the modulation signal 74 from FIG. 2.
• Fig. 4 shows the frequency spectrum of the modulation signal of Fig. 3.
• At reference numeral 80 is a first peak indicating a high signal component at the fundamental frequency of 125 MHz.
• the reference numeral 82 denotes further peaks which are at 375 MHz, 625 MHz, 875 MHz, etc. These are odd multiples of the fundamental frequency, which are typical for a square-wave signal.
• the reference numerals 84, 86 show further peaks which occur as a result of the combination with the second and third modulation signals 62, 64.
• the further peaks 84, 86 designate frequency components which are also included in the combined modulation signal 74 and which in the preferred embodiments of the invention are evaluated in addition to the fundamental frequency of the first modulation signal 60 to determine the transit time of the transmitted light beam 18 and the received light beam 24 and, consequently, the To determine distance d.
• only the fundamental frequencies, but not the other harmonic frequencies 82, 88 are evaluated to determine a phase shift between the transmitted light beam 18 and the received light beam 24.
• the harmonic frequencies i. the frequencies at the peaks 82 and the frequencies 88 grouped around them are evaluated.
• the harmonic frequencies 82, 88 are suppressed by means of a suitable input filter in the region of the light receiver 14. It is understood that such an input filter (not shown here) can be omitted and / or modified if the harmonic frequency components are also to be evaluated.
• the modulation signal 74 is generated by means of a digital circuit in the form of the FPGA 56 as a binary rectangular wave modulation signal.
• a calculation specification and / or a value table is stored for this purpose, which represents the modulation signals 60, 62, 64.
• the FPGA 56 With the help of this calculation rule and / or a value table, the FPGA 56 generates the binary pulse sequence, which is fed to the light transmitter 12 as a modulation signal 74.
• Fig. 5 shows an alternative embodiment in which the modulation signal for the light emitter 12 is generated in an analogous manner.
• the light transmitter 12 includes the laser diode 13 and a transistor 90 through which a control current I flows, with which the laser diode 13 is fed.
• the phase angle of the control current I is a measure of the phase position of the modulation signal with which the transmitted light beam is modulated.
• the phase position of the control current I is measured with a phase detector 91 and reported as a reference phase to the microprocessor 54.
• a portion of the emitted light beam is diverted with a signal splitter and the diverted portion is measured with a light-sensitive monitor diode. Obtained in this way the phase position of the modulation signal in the emitted light beam.
• a communication channel of the FPGA 56 is used to transmit the phase information.
• the base of the transistor 90 is supplied with a sum signal, which corresponds to the sum signal 66 from FIG. 2, for example.
• the sum signal is generated by adding a first modulation signal 60, a second modulation signal 62 and a third modulation signal 64 at a summing point 91.
• the modulation signals 60, 62, 64 are generated by means of three sinusoidal signals 92, 94, 96.
• Each of the three sinusoidal signals 92, 94, 96 is amplified by means of an amplifier 98 and then "cut off" by means of a limiter 100. In this way, the sinusoidal signals 92, 94, 96 become square-wave signals, as idealized in FIG are shown.
• Fig. 6 shows a further embodiment.
• the sinusoidal signals 92, 94, 96 are each amplified so much by means of the amplifiers 98 that the sum signal leads the transistor 90 into saturation.
• the transistor 90 itself acts as a limiter, which generates the square-wave modulation signal from the sinusoidal modulation signals 92, 94, 96.

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• Engineering & Computer Science (AREA)
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• Computer Networks & Wireless Communication (AREA)
• General Physics & Mathematics (AREA)
• Radar, Positioning & Navigation (AREA)
• Remote Sensing (AREA)
• Electromagnetism (AREA)
• Optical Radar Systems And Details Thereof (AREA)
• Measurement Of Optical Distance (AREA)
• Length Measuring Devices By Optical Means (AREA)

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