EP2062346A1 - Procédé d'utilisation d'un circuit redresseur et dispositif en vue de la mise en uvre du procédé - Google Patents

Procédé d'utilisation d'un circuit redresseur et dispositif en vue de la mise en uvre du procédé

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Publication number
EP2062346A1
EP2062346A1 EP07820230A EP07820230A EP2062346A1 EP 2062346 A1 EP2062346 A1 EP 2062346A1 EP 07820230 A EP07820230 A EP 07820230A EP 07820230 A EP07820230 A EP 07820230A EP 2062346 A1 EP2062346 A1 EP 2062346A1
Authority
EP
European Patent Office
Prior art keywords
component
power value
filter
transformation
filter output
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP07820230A
Other languages
German (de)
English (en)
Inventor
Leonardo Serpa
Srinivas Ponnaluri
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
ABB Schweiz AG
Original Assignee
ABB Schweiz AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by ABB Schweiz AG filed Critical ABB Schweiz AG
Publication of EP2062346A1 publication Critical patent/EP2062346A1/fr
Withdrawn legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from ac input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • H02M7/53875—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with analogue control of three-phase output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation

Definitions

  • the invention relates to the field of power electronics. It is based on a method for operating a converter circuit and a device for carrying out the method according to the preamble of the independent claims.
  • Conventional converter circuits comprise a converter unit with a plurality of controllable power semiconductor switches, which are connected in a known manner for switching at least two switching voltage levels.
  • An LCL filter is connected to each phase connection of the inverter unit.
  • a capacitive energy store which is conventionally formed by one or more capacitors, is also connected to the converter unit.
  • a device is provided which has a control device for generating a hysteresis active power value, a hysteresis reactive power value and a selected flux sector, which via a drive circuit for forming a drive signal from the hysteresis. active power value, the hysteresis reactive power value and the selected flux sector is connected to the controllable power semiconductor switches. By means of the drive signal thus the power semiconductor switches are driven.
  • a problem with a converter circuit mentioned above is that the LCL filters cause a permanent distortion, i. can cause unwanted oscillations in the filter output currents and filter output voltages due to resonant oscillations of the LCL filters, as shown in a common time course of filter output currents according to FIG. 3.
  • a permanent distortion i. can cause unwanted oscillations in the filter output currents and filter output voltages due to resonant oscillations of the LCL filters, as shown in a common time course of filter output currents according to FIG. 3.
  • an electrical alternating voltage network typically connected to the filter outputs or in the case of an electrical load connected to the filter outputs, such distortions can lead to damage or even destruction and are therefore highly undesirable.
  • the object of the invention is therefore to provide a method for operating a converter circuit, by means of which distortions in the filter output currents and filter output voltages caused by LCL filters connected to the converter circuit can be actively damped. Furthermore, it is the object of the invention to provide a device with which the method can be carried out in a particularly simple manner.
  • the converter circuit has a converter unit with a large number of controllable power semiconductor switches and an LCL filter connected to each phase connection of the converter unit.
  • the controllable power semiconductor switches are now controlled by means of a drive signal formed from a hysteresis active power value, from a hysteresis flash power value and from a selected flux sector.
  • the hysteresis effective power value is formed from a differential active power value by means of a first hysteresis controller, and the difference active power value from the subtraction of an estimated active power value and a damping active power value from a reference an effective power value is formed, wherein the damping power value is formed from a multiplying a low-pass filtered d-component of the Park-Clarke transform of filter capacitance voltages by a d-component of the Park-Clarke transform of filter capacitance voltages filtered with respect to the fundamental of the filter output currents.
  • the hysteresis reactive power value is formed from a differential reactive power value by a second hysteresis controller, and the differential reactive power value is formed from subtracting an estimated reactive power value and an attenuation reactive power value from a reference reactive power value, the attenuation reactive power value being a negative multiplied by the adjustable attenuation factor of a Park Clarke low-pass filtered d component Transformation of filter capacitance voltages with a filtered with respect to the fundamental of the filter output currents q component of the Park-Clarke transformation of filter capacitance voltages is formed.
  • a further advantage of the method according to the invention is that no discrete, space-consuming, costly realized and therefore more expensive damping resistor has to be connected to the respective phase connection in order to be able to effectively dampen the undesired distortions.
  • the device according to the invention for carrying out the method for operating the converter circuit has a regulation device serving to generate a hysteresis active power value, a hysteresis reactive power value and a selected flux sector, which is connected to the controllable power semiconductor switches via a drive circuit for forming a drive signal.
  • the control means comprises a first calculation unit for forming the hysteresis power value, the hysteresis flow value and the selected flux sector, the first calculation unit comprising a first hysteresis controller for forming the hysteresis active power value from a differential active power value, a second hysteresis controller for forming the hysteresis reactive power value from a differential reactive power value and a vector - A -
  • the controller further comprises a first summer for forming the differential active power value from subtracting an estimated active power value and a damping active power value from a reference active power value and a second summer for forming the differential reactive power value from subtracting an estimated reactive power value and an attenuation reactive power value from a reference reactive power value.
  • control means comprises a second calculation unit for forming the damping active power value and the damping reactive power value, the damping active power value being divided by the adjustable damping factor multiplied by the low-pass filtered d-component of the Park-Clarke transformation of filter capacitance voltages with respect to the fundamental of the filter output currents d component of the Park-Clarke transform of filter capacitance voltages is formed.
  • the attenuation blank power value is further formed from the negative multiplied by the adjustable attenuation factor of the low-pass filtered d-component of the Park-Clarke transform of filter capacitance voltages with the q component of the Park-Clarke transform of filter capacitance voltages filtered with respect to the fundamental of the filter output currents.
  • the device according to the invention for carrying out the method for operating the converter circuit can thus be implemented very simply and cost-effectively, since the circuit complexity can be kept extremely low and, moreover, only a small number of components are required for the structure.
  • the inventive method is thus particularly simple to carry out.
  • Show it: 1 shows an embodiment of an inventive device for carrying out the inventive method for operating a converter circuit
  • Fig. 4 shows a time course of the filter output currents with active damping according to the inventive method
  • FIG. 5 shows an embodiment of a second calculation unit.
  • FIG. 1 shows an embodiment of a device according to the invention for carrying out the method according to the invention for operating a converter circuit.
  • the converter circuit has a converter unit 1 with a plurality of controllable power semiconductor switches and an LCL filter 3 connected to each phase connection 2 of the converter unit 1.
  • each LCL filter 3 has a first filter inductance L fl , a second filter inductance L fg and a filter capacitance C f , the first filter inductance L fl with the associated phase connection 2 of the converter unit 1, with the second filter inductance L fg and with the filter capacitance C f is connected.
  • the filter capacitances C f of the individual LCL filters 3 are connected to one another.
  • the power converter unit 1 is exemplified three-phase. It should be mentioned that the converter unit 1 is generally used as any converter unit 1 for switching> 2 switching voltage levels (multi-level converter circuit) with respect to the voltage of a drive unit connected to the converter unit. unit 1 connected capacitive energy storage 19 may be formed, in which case the capacitive energy storage 19 is formed by any number of capacities, which capacities are then adapted to the corresponding executed partial converter circuit are connected.
  • the controllable power semiconductor switches of the converter unit 1 are now controlled by means of a drive signal S formed from a hysteresis effective power value d P , a hysteresis flash power value d Q and a selected flux sector ⁇ n .
  • a drive signal S formed from a hysteresis effective power value d P , a hysteresis flash power value d Q and a selected flux sector ⁇ n .
  • a look-up table is commonly used, in which hysteresis active power values d P , hysteresis flash power values d Q and selected flow sectors ⁇ n are assigned to corresponding drive signals S, or a modulator based on the pulse width modulation.
  • the hysteresis effective power value dp is formed from a differential active power value P dlff by means of a first hysteresis regulator 16, as shown in FIG. 1. Furthermore, the differential active power value P d i ff is formed from the subtraction of an estimated active power value P and a damping active power value P d from a reference active power value P ref , where the damping effective power value P d is calculated from a multiplication of a low-pass filtered d divided by an adjustable damping factor k d.
  • the reference active power value P ref is freely adjustable and is the desired value of the active power, which should be present at the output of the LCL filter 3.
  • the hysteresis reactive power value d Q is formed from a differential reactive power value Q dlff by means of a second hysteresis controller 17 and the differential reactive power value Q dlff is derived from the subtraction of an estimated reactive power value Q and an attenuation reactive power value Q d from a reference reactive power value Q ref , the attenuation reactive power value Q d being negative the adjustable damping factor k d divided multiplication of a low-pass filter d-component of the Park-Clarke transformation of filter capacitance voltages u T c f , d with a q- component of the Park-Clarke transformation of filter capacitance voltages u G c f filtered with respect to the fundamental of the filter output currents i fg1 , i fg2 , i
  • the reference reactive power value Q ref is freely adjustable and is the target value of the reactive power which is to be present at the output of the LCL filter 3.
  • a further advantage of the method according to the invention is that no discrete, space-consuming, costly realized and therefore more expensive damping resistor has to be connected to the respective phase connection 2 in order to be able to effectively dampen the undesired distortions.
  • the inventive apparatus for carrying out the Inventions according to method for operating a converter circuit to one of the generation of the Hysteresewirk nowadaysshongs dp, the Hystereseblind orientalshongs d Q and the selected flux sector ⁇ to n serving control device 4, the one via a drive circuit 5 for forming Control signal S with the controllable power semiconductor switches is bound.
  • the drive circuit 5 comprises, for example, a look-up table in which hysteresis active power values d P , hysteresis reactive power values d Q and selected flow sectors ⁇ n are assigned to corresponding drive signals S, or a modulator based on the pulse width modulation.
  • the regulation device 4 comprises a first calculation unit 6 for forming the hysteresis reactive power value dp, the hysteresis flow value d Q and the selected flux sector ⁇ n , the first calculation unit 6 determining the first hysteresis controller 16 for forming the hysteresis effective power value d P from the differential effective power value P dlff second hysteresis controller 17 for forming the hysteresis reactive power value d Q from the differential reactive power value Q dlff and a vector mapper 18 for forming the selected flux sector ⁇ n .
  • control device 4 comprises a first summer 7 for forming the differential active power value P dlff from the subtraction of the estimated effective power value P and the damping active power value P d from the reference active power value P ref and a second summer 8 for forming the differential reactive power value Q dlff from the subtraction of the estimated one Reactive power value Q and of
  • the control device 4 comprises a second calculation unit 9 for forming the damping effective power value P d and the damping reactive power value Q d , the damping effective power value P d being determined from the multiplication of the low-pass filtered d component of the Park Clarke divided by the adjustable damping factor k d .
  • Transformation of filter capacitance voltages u T c f, d is formed with the respect to the fundamental of the filter output currents i f gi, i f g 2 , i f g3 filtered d-component of the Park-Clarke transformation of filter capacitance voltages u G c f, d and the Damping reactive power value Q d from the negative multiplication, divided by the adjustable damping factor k d , of the low-pass filtered d component of the Park-Clarke transformation of filter capacitance voltages u T c f, d with respect to the fundamental of the filter output currents i fg i, i fg2 , i fg3 q- component of the Park-Clarke transform of Fil terkapazticiansliden u G c f, q is formed.
  • the inventive device for carrying out the method for operating the converter circuit is therefore very easy and inexpensive to implement, since the circuit complexity can be kept extremely low and also only a small number of Components needed for the construction.
  • the method according to the invention is thus particularly easy to carry out.
  • x is a complex size
  • x d is the d-component of the Park-Clarke transformation of size x
  • x q is the q-component of the Park-Clarke transformation of size x.
  • the Park-Clarke transformation not only the fundamental of the complex variable x is transformed, but also all occurring harmonics of the complex magnitude x.
  • the low-pass filtered d component of the Park-Clarke transform of filter capacitance voltages u T c f, d , the d-component of the Park-Clarke transformation of filter capacitance voltages u G filtered with respect to the fundamental of the filter output currents i fg1 , i fg2 , i fg3 c f, d and the q component of the Park-Clarke transformation of filter capacitance voltages u G c f , q filtered with respect to the fundamental of the filter output currents i fg1 , i fg2 , i fg3 is preferably selected from the filter capacitance currents i Cf1 , i Cf2 , i Cf3 educated.
  • an embodiment of the second calculation unit 9 which also includes the formation of the low-pass filtered d-component of the Park-Clarke transformation of filter capacitance voltages u T c f, d , with respect to the fundamental of the filter output currents i f gi, i f g 2 , i f g3 filtered d-component of the Park-Clarke transformation of filter capacitance voltages u G c f, d and the fundamental with respect to the filter output currents i f gi, i f g 2 , i f g 3 filtered q-component of the Park-Clarke transform of filter capacitance voltages u G c f, q from the filter capacitance currents i Cf1 , i Cf2 , i Cf3 .
  • the ⁇ component and the ⁇ component of the space vector transformation of the filter capacitance currents i Cf, ⁇ ⁇ are formed from supplied filter capacitance currents i Cf1 , i Cf2 , ic f3 by space vector transformation. Thereafter, the ⁇ component and the ⁇ component of the space vector transformation of the filter capacitance currents i Cf, ⁇ ⁇ are integrated so that an ⁇ component and a ⁇ component of the space vector transformation of the filter terkapazticiansliden u Cf , ⁇ ß is generated.
  • the ⁇ component and the ⁇ component of the space vector transformation of the filter capacitance voltages u Cf , ⁇ Park Clarke transformed where only the resulting d component of the Park-Clarke transform of the filter capacitance voltages u Cf, d is further used.
  • the d-component of the Park-Clarke transformation of the filter capacitance voltages u Cf , d is filtered by means of a low-pass filter, so that said low-pass filtered d-component of the Park-Clarke transformation of filter capacitance voltages u T c f , d is generated.
  • the low-pass filtering advantageously has the effect that the low-pass filtered d component of the Park-Clarke transformation of filter capacitance voltages u T c f, d has only one fundamental oscillation component with respect to the filter output currents i fg1 , i fg2 , i fg3 and accordingly all the harmonics are filtered out.
  • the filter capacitance voltages u Cf , ⁇ with respect to the fundamental of the filter output currents i fg i, i fg2 , i fg3 by means of a band reject filter with respect to the fundamental of the filter output currents i fg1 , i fg2 , i fg3 filtered ⁇ component and ⁇ component of the space vector transformation of the filter capacitance voltages Gc f . ⁇ ß generated.
  • the filtering advantageously has the effect that the ⁇ component and ⁇ component of the space vector transformation of the filter capacitance voltages G Cf, ⁇ ⁇ , which are filtered with respect to the fundamental mode of the filter output currents i fg1 , advantageously only have harmonic components with respect to the filter output currents i fg1 , i fg2 , i fg3 and therefore the fundamental component is filtered out.
  • the fundamental oscillation component with respect to the filter output currents i fg1 , i fg2 , i fg3 advantageously corresponds to a resonance frequency depending on the second filter inductance L fg and the filter capacitance C f , which then increases
  • the ⁇ -component and ⁇ -component of the space-vector transformation of the filter capacitance voltages Q Cf , ⁇ are Park-Clarke-transformed with respect to the fundamental of the filter output currents i f gi, i fg 2 , i fg3 , whereby then the said one the basic oscillation of the filter output currents i fg i, i fg2 , i fg3 filtered d-component of the Park-Clarke transformation of filter capacitance voltages u G c f, d and the q- filtered with respect to the fundamental of the filter output currents i fg i, i fg2 , i fg3 Component of parking Clarke transformation of filter capacitance voltages u G c f , q is generated.
  • the attenuation waveguide value P d is then multiplied by the multiplication of the low-pass filtered d component of the Park-Clarke transformation of filter capacitance voltages u T c f , d by the divided damping factor k d the dc component of the Park-Clarke transformation of filter capacitance voltages Ucc f .d formed with respect to the fundamental of the filter output currents i fg i, i fg2 , i fg3 and the attenuation reactive power value Q d are formed from the negative multiplied low-pass filtered by the adjustable attenuation factor k d d component of the Park-Clarke transformation of filter capacitance voltages u T c f, d with the q component of the Park-Clarke transformation of filter capacitance voltages u G c f , q filtered with respect to the fundamental of the filter output
  • the above-mentioned estimated active power value P and the estimated reactive power value Q are respectively formed from an ⁇ component of the space vector transformation of filter output currents i fg ⁇ , from a ⁇ component of the space vector transformation of filter output currents i fg ⁇ , from an ⁇ component of the space vector transformation of filter output flows ⁇ L ⁇ and from a ß-component of the space pointer transformation of filter output flows ⁇ Lß formed, which illustrate in particular subsequent formulas.
  • the control device 4 In order to form the estimated effective power value P and the estimated reactive power value Q, the control device 4 according to FIG. 1 has a third calculation unit 10, by means of which the estimated active power value P and the estimated reactive power value Q are calculated in each case according to the above-mentioned formula.
  • the ⁇ component of the space vector transformation of filter output flows ⁇ L ⁇ is formed from an ⁇ component of the space vector transformation of estimated filter capacitance ⁇ c f und and from the ⁇ component of the space vector transformation of filter output currents i f g ⁇ , which illustrates in particular the following formula.
  • ⁇ L " ⁇ C fa - Lfa fg - 'i' fg ⁇
  • the ⁇ component of the space vector transformation of filter output flows ⁇ L ⁇ is formed from a ⁇ component of the space vector transformation of estimated filter capacitance ⁇ Cf ⁇ and from the ⁇ component of the space vector transformation of filter output currents i f g ⁇ , which illustrates in particular the following formula. - i fg
  • the control device 4 In order to form the ⁇ component of the space vector transformation of filter output flows ⁇ L ⁇ and the ⁇ component of the space vector transformation of filter output flows ⁇ Lss , the control device 4 according to FIG. 1 has a fourth calculation unit 1 1, by means of which the ⁇ component of the space vector transformation of filter output flows ⁇ L ⁇ and the ⁇ component of the space pointer transformation of filter output flows ⁇ L ⁇ is calculated in each case according to the above-mentioned formula.
  • the ⁇ component of the space vector transformation of filter output currents i fg ⁇ is formed from the ⁇ component of the space vector transformation of phase connection currents i f ⁇ , which is formed by space vector transformation of the phase connection currents i fl1 , i fl2 , i fl3 measured according to FIG. 1, and of the ⁇ component the space vector transformation of the filter capacitance currents b ⁇ , which is formed by space vector transformation of the measured according to FIG. 1 filter capacitance currents i C ⁇ , ict 2 , ict3, formed by summation.
  • the .beta.-component of the space vector transformation of filter output currents i will FGSS from the SS component of the space vector transformation of phase connection currents i fl ß, which measured by the space vector transformation of the FIG. 1 phase connection currents i fl i, i fl2, i is formed f ⁇ 3, and from the ß-component of the space vector transformation of the filter capacitance currents i Cf ß, which is formed by space pointer transformation of the measured according to FIG. 1 filter capacitance currents ic ⁇ , i Cf2 , ic f3 formed by summation.
  • a measurement of the filter output currents i fg1 , i fg2 , i fg3 can thus advantageously be dispensed with, as a result of which the device is simplified, since no measuring sensors, in particular no current transformers, are required.
  • the ⁇ component of the space vector transformation of estimated filter capacitance fluxes ⁇ c f ⁇ is formed from a current DC voltage value u dc of the capacitive energy store 19 connected to the converter unit 1, from the drive signal S and from the ⁇ component of the space vector transformation of phase connection currents i f ⁇ illustrates the following formula, where u C ⁇ is the ⁇ component of the phase connection voltage of the converter unit 1 formed from the current DC voltage value u dc and from the drive signal.
  • the ⁇ -component of the space-vector transformation is formed by estimated filter capacitance ⁇ c f ⁇ from the current DC voltage value u dc of the capacitive energy store 19 connected to the converter unit 1, from the drive signal S and from the ⁇ -component of the space-vector transformation of phase-terminal currents i fl ⁇ .
  • u C ⁇ ⁇ is the ⁇ component of the phase connection voltage of the converter unit 1 formed from the current DC voltage value u dc and from the drive signal.
  • the control unit 4 In order to form the ⁇ component of the space vector transformation of estimated filter capacitance fluxes ⁇ Cf ⁇ and the ⁇ component of the space vector transformation of estimated filter capacitance ⁇ c f ⁇ , the control unit 4 according to FIG. 1 has a fifth calculation unit 12, by means of which the ⁇ component of the space vector transformation of estimated filter capacitance ⁇ Cf ⁇ and the ⁇ component of the space vector transformation of estimated filter capacitance ⁇ Cf ⁇ each according to the above-mentioned formula is calculated.
  • a compensation reactive power value Q COmp is additionally added, the compensation reactive power value Qco m p being formed by low-pass filtering of an estimated filter capacitance reactive power value Q Cf by means of a low-pass filter 15. It is thus advantageously avoided that unwanted reactive power components of the LCL filters 3, in particular of the filter capacitances C f of the LCL filters 3, are present at the output of the LCL filters 3, so that it can be ensured that the output of the LCL filters 3 sets only a reactive power value according to the set reference reactive power value Q ref .
  • the second summer 8 is additionally supplied with the compensation reactive power value Q COm p.
  • the estimated filter capacitance reactive power value Q Cf is calculated from the ⁇ component of the space vector transformation of the filter capacitance currents aa , from the ⁇ component of the space vector transformation of the filter capacitance currents i Cf ⁇ , from the ⁇ component of the space vector transformation of the estimated filter capacitance ⁇ c f ⁇ and from the ⁇ Component of the space pointer transformation of the estimated filter capacity flows ⁇ Cf ß formed, which illustrates in particular the following formula.
  • the control means 4 comprises the formation of the estimated value Q Cf Filterkapazticiansblindleis- processing according to FIG. 1 of a sixth calculation unit 13, by means of which the estimated filter capacitance wattless component value Q Cf is calculated by above-mentioned formula.
  • At least one compensation harmonic active power value P h is additionally added with respect to the fundamental vibration of the filter output currents i fg i, i fg2 , i fg3 . Furthermore, in order to form the above-mentioned differential reactive power value Q dlff, in addition at least one compensation upper-harmonic reactive power value Q h is added relative to the basic oscillation of the filter output currents i fg1 , i fg2 , i fg3 . According to FIG. 1, the first summer 7 is additionally supplied with the compensation harmonic active power value P h in order to form the difference active power value P dlff .
  • the second summer 7 is additionally supplied with the compensation harmonic power value Q h in order to form the differential reactive power value Qdi ff according to FIG.
  • the compensation harmonic power value P h and the Kompensationsoberschwingungsblind orientalswert Q h is in each case from the ⁇ -component of the space vector transformation of the filter output currents i fg ⁇ , from the ß-component of the space pointer transformation of the filter output currents i fg ß, from the ⁇ -component of the space pointer transformation of the filter output flows ⁇ L ⁇ , from the ß-component of the space vector transformation of the filter output flows ⁇ L ß and from the fundamental oscillation angle ⁇ t with respect to the fundamental of the filter output currents i fg i, i formed fg2 , i fg3 .
  • the fundamental oscillation angle ⁇ t is provided to the calculation units 9, 10, 13, 14 and the vector allocator 18 according to FIG. 1 by a phase locked loop (PLL).
  • the control device 4 has a seventh calculation unit 14 for the calculation of the compensation harmonic active power value P h and the compensation upper harmonic power value Q h , an embodiment of the seventh calculation unit 14 being shown in FIG.
  • the addition or connection of at least one compensation harmonic active power value P h for forming the differential effective power value P dlff and at least one compensation harmonic power value Q h for forming the differential reactive power value Q dlff advantageously results in an active reduction of harmonics and thus a further improvement in the reduction of harmonics.
  • the ⁇ component of the space vector transformation of the filter output currents i fg ⁇ and the ⁇ component of the space vector transformation of the filter output currents i f gß are first formed from supplied filter output currents i fg1 , i fg2 , i fg3 by space vector transformation.
  • the ⁇ component of the space pointer transformation of the filter output currents i fg ⁇ and the ⁇ component of the space vector transformation of the filter output currents i fg ⁇ are Park-Clarke-transformed, low-pass filtered and d-component and the q-component of the Park-Clarke transformation of at least one desired one selected harmonic of the filter output currents i hd , i hq with respect to the fundamental of the filter output currents i fg i, i fg2 , i fg 3 output.
  • the d-component and the q-component of the Park-Clarke transformation of the desired selected h-th harmonic of the filter output currents i hd , i hq are each reduced to an associated predefinable reference value i * hd , i * hq , preferably a proportional-integral characteristic, corrected and then inverse-parking Clarke-transformed, whereby an ⁇ -component of the space- hysterestransform of the h-th harmonic of reference filter output currents i * h ⁇ and a ⁇ -component of the space-vector transformation of the h-th harmonic of reference filter output currents i * h ⁇ are formed.
  • the compensation harmonic active power value P h and the compensation harmonic power value Q h are respectively derived from the ⁇ -
  • FIG. 3 shows a common time profile of the filter output currents i fg1 , i fg2 , i fg3 .
  • FIG. 4 shows a time profile of the filter output currents i f gi, i f g 2 , i f g3, in which unwanted oscillations in the filter output currents i fg1 , i fg2 , i fg3 are actively attenuated so that these distortions are greatly reduced.
  • the additional active reduction of harmonics according to the method according to the invention described above brings about a further improvement in the reduction of harmonics.
  • All steps of the method according to the invention can be realized as software, which can then be loaded, for example, onto a computer system, in particular with a digital signal processor, and run on it.
  • the digital delay times occurring in such a system, in particular for the calculations, can generally be taken into account, for example, by adding an additional term to the fundamental frequency cot in the Park-Clarke transformation.
  • inventive device described above in detail also in a Computer system, in particular in a digital signal processor, be realized.
  • the device according to the invention for carrying out the method according to the invention for operating the converter circuit shown particularly in FIG. 1
  • the inventive method is particularly easy to carry out.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Supply And Distribution Of Alternating Current (AREA)
  • Inverter Devices (AREA)

Abstract

L'invention concerne un procédé et un dispositif auquel est raccordé un filtre LCL (3), dans lequel les semi-conducteurs de puissance asservis sont commandés par la valeur de la puissance effective d'hystérèse (dP), la valeur de la puissance aveugle d'hystérèse (dQ) et un facteur de flux (On) sélectionné. La valeur de la puissance effective d'hystérèse (dP) est formée à partir d'une valeur de différence entre les puissances effectives (Pdiff) au moyen d'un premier régulateur d'hystérèse (16) et la valeur de différence entre les puissances effectives (Pdiff) est formée en soustrayant une valeur estimée de la puissance effective (P) et une valeur d'atténuation de la puissance effective (Pd) d'une valeur de référence de la puissance effective (Pref). La valeur d'atténuation de la puissance effective (Pd) est formée en multipliant la composante d filtrée passe-bas de la transformation de Park-Clarke des tensions de capacité du filtre (UTCf, d) par la composante d, dont l'oscillation de base des courants de sortie du filtre (ifg1, ifg2, ifg3) a été filtrée, de la transformation de Park-Clarke des tensions de capacité du filtre (UGCf, d) et en divisant par un facteur d'atténuation (kd) réglable. La valeur de la puissance aveugle d'hystérèse (dQ) est formée à partir de la valeur de la différence entre les puissances aveugles (Qdiff) au moyen d'un deuxième régulateur d'hystérèse (17) et la valeur de la différence entre les puissances aveugles (Qdiff) est formée en soustrayant une valeur estimée de la puissance aveugle (Q) et une valeur d'atténuation de la puissance aveugle (Qd) d'une valeur de référence de la puissance aveugle (Qref). La valeur d'atténuation de la puissance aveugle (Qd) est formée en multipliant une composante d filtrée passe-bas de la transformation de Park-Clarke des tensions de capacité du filtre (UTCf, d) par une composante q, dont l'oscillation de base des courants de sortie de filtre (ifg1, ifg2, ifg3) a été filtrée, de la transformation de Park-Clarke des tensions de capacité de filtre (UGCf, q) et en divisant par l'opposé du facteur d'amortissement (kd) réglable.
EP07820230A 2006-09-15 2007-09-14 Procédé d'utilisation d'un circuit redresseur et dispositif en vue de la mise en uvre du procédé Withdrawn EP2062346A1 (fr)

Applications Claiming Priority (2)

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US84467506P 2006-09-15 2006-09-15
PCT/EP2007/059727 WO2008031893A1 (fr) 2006-09-15 2007-09-14 procédé d'utilisation d'un circuit redresseur et dispositif en vue de la mise en Œuvre du procédé

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EP2062346A1 true EP2062346A1 (fr) 2009-05-27

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US (1) US7778052B2 (fr)
EP (1) EP2062346A1 (fr)
JP (1) JP5054110B2 (fr)
CN (1) CN101517874B (fr)
RU (1) RU2410828C2 (fr)
WO (1) WO2008031893A1 (fr)

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CN101517874B (zh) 2012-01-11
RU2410828C2 (ru) 2011-01-27
WO2008031893A1 (fr) 2008-03-20
CN101517874A (zh) 2009-08-26
US7778052B2 (en) 2010-08-17
JP5054110B2 (ja) 2012-10-24
RU2009114148A (ru) 2010-10-20
US20090237964A1 (en) 2009-09-24

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