EP1676373B1 - Suppression d'echos radiofréquence en duplex integral - Google Patents

Suppression d'echos radiofréquence en duplex integral Download PDF

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Publication number
EP1676373B1
EP1676373B1 EP04817328.0A EP04817328A EP1676373B1 EP 1676373 B1 EP1676373 B1 EP 1676373B1 EP 04817328 A EP04817328 A EP 04817328A EP 1676373 B1 EP1676373 B1 EP 1676373B1
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EP
European Patent Office
Prior art keywords
signal
reflection
radio frequency
reflection signal
feedback
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
EP04817328.0A
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German (de)
English (en)
Other versions
EP1676373A4 (fr
EP1676373A2 (fr
Inventor
Mark Duron
Raj Bridgelall
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Symbol Technologies LLC
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Symbol Technologies LLC
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Publication of EP1676373A4 publication Critical patent/EP1676373A4/fr
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Publication of EP1676373B1 publication Critical patent/EP1676373B1/fr
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/50—Circuits using different frequencies for the two directions of communication
    • H04B1/52—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa
    • H04B1/525—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa with means for reducing leakage of transmitter signal into the receiver
    • G—PHYSICS
    • G06—COMPUTING; CALCULATING OR COUNTING
    • G06K—GRAPHICAL DATA READING; PRESENTATION OF DATA; RECORD CARRIERS; HANDLING RECORD CARRIERS
    • G06K7/00—Methods or arrangements for sensing record carriers, e.g. for reading patterns
    • G06K7/0008—General problems related to the reading of electronic memory record carriers, independent of its reading method, e.g. power transfer

Definitions

  • Radio frequency identification (“RFID”) systems are used in a plethora of commercial contexts requiring a unique identification system for large numbers of items. Such contexts include everything from department store inventory and check-out systems to the tracking of military supplies to and from the front lines. Similar in utility to bar code technology, RFID systems are often preferred due to their increased range, lack of a line of sight requirement between a tag and its reader and the high multi-tag throughput of RFID readers ( i.e., RFID readers may read many tags in their large field of view at very high transport speeds).
  • VSWR voltage standing wave ratio
  • WO 00/21204 discusses a system for suppressing RF signals transmitted by a transmitter from the RF signals received by a receiver.
  • WO 00/52838 discusses a technique for eliminating crosstalk in a transmitter which is operated according to a frequency multiplex-full duplex mode.
  • a system comprising a transmitter element creating an interrogation signal and transmitting the interrogation signal and a receiver element receiving a reflection signal of the interrogation signal and combining the reflection signal and a feedback signal to cancel at least a portion of radio frequency echo signals in the reflection signal.
  • a method comprising the steps of receiving a reflection signal, deriving a feedback signal from the reflection signal by isolating an error component of the reflection signal and combining the reflection signal and the feedback signal to cancel at least a portion of radio frequency echo signals in the reflection signal.
  • a method comprising the steps of demodulating a reflection signal into an in-phase signal and a quadrature signal, filtering the in-phase signal to isolate an in-phase error signal, filtering the quadrature signal to isolate a quadrature error signal, modulating the in-phase error signal and the quadrature error signal to create a feedback signal and combining the reflection signal and the feedback signal to cancel at least a portion of radio frequency echo signals in the reflection signal.
  • FIG. 1 illustrates the basic components of an RFID system 1, in which RF "tags" located on objects in the environment may reflect radio waves originating from a transceiver 10 in a pre-determined bit pattern and data rate via the principle of backscatter radiation. These reflections may be received by the transceiver 10, stripped of their carrier signal and converted into in-phase (“I”) and quadrature ("Q") components. These components may then be independently digitized and sent to a base-band processor 20 for bit decoding. This decoded information may then be sent on to a reader control 30 which may perform such processes as error correction, command interpretation, and management of access to the RF channel.
  • a host interface 40 performs filtering operations and translation of the results of the reader control 30 into a format intelligible to the host, and likewise translates host requests into a format intelligible to the reader control 30.
  • the transmitter portion of an RFID transceiver may create an interrogation signal for transmission by using a modulator 105 and a variable gain amplifier ("VGA") 110 to modulate a carrier signal.
  • VGA variable gain amplifier
  • Use of the VGA 110 may result in an amplitude modulated (AM) carrier wave.
  • This modulated carrier wave may then be sent to a power amplifier 115 and band-pass filter 120.
  • This amplified and filtered modulated carrier wave may then be sent to a circulator or coupler element 125 for transmission to the antenna 130.
  • the incoming signal may arrive at the antenna 130 containing both valuable information from an RF tag and an error signal.
  • this composite signal may be sent through a circulator 125 which may route the incoming signal into one input of an RF combiner 140.
  • the combiner 140 may add this incoming signal to the output of the feedback circuit discussed below, and may feed the sum of these two signals into a band-pass filter 145.
  • the band-pass filter 145 removes signal components outside of the frequency range of the modulated data signal of interest.
  • the signal may then be amplified by an automatic gain control (“AGC”) 150.
  • AGC automatic gain control
  • This amplified signal may then be carrier-demodulated in quadrature using a demodulator 155.
  • Both of the resulting demodulated signals (the in-phase signal Irx and the quadrature signal Qrx) may then be split.
  • Two separate branches may take the in-phase and quadrature signals through band-pass filters 1801 and 180Q before continuing towards the transceiver output for further processing by the base-band decoder 20.
  • Each of these branches includes a second path as input for a feedback loop.
  • the feedback loop achieves echo cancellation in the transceiver by isolating the noise (error) component of the incoming signal using low-pass filters 1601 and 160Q, subjecting this signal to a phase inversion, and then combining it with the incoming signal using another input of the RF combiner 140.
  • the required phase inversion may be accomplished by modulating the physical path length of the return loop.
  • the path length may be controlled by either controlling the microwave traces on the circuit board at the design phase, or by adding a variable delay element for adaptive control.
  • the feedback loop may be designed to converge with the incoming signal within the impulse response time of the low-pass filter, which is usually within a few cycles of the carrier signal.
  • both the in-phase signal Irx and the quadrature signal Qrx may first be passed through low-pass filters 1601 and 160Q.
  • These low-pass filters may isolate the undesirable echo signal since the majority of the base band error signal is of a lower frequency than the signal of interest.
  • the error signal is of a lower frequency and therefore low pass filters are used.
  • the outputs of these low-pass filters 1601 and 160Q may then be modulated using modulator 165.
  • the two signals may then be combined using a summing element 170.
  • the exemplary embodiment of the present invention shown in Figure 3 may be more cost-effective than that shown in Figure 2 , either by reducing the number of components in the transceiver or by substituting less expensive yet equally effective components for more expensive ones.
  • this arrangement may introduce other problems such as non-linearity and amplification of harmonics.
  • the non-linearity may be controlled by recording it digitally and then adding a correction factor into the feedback loop.
  • Amplified harmonics may be controlled by adding a low-pass filter (not shown) to the output of the feedback amplifier 175.
  • Figure 4 shows a second alternative exemplary embodiment of the present invention with a sample and hold circuit 305 inserted into the feedback loop.
  • the sample and hold circuit 305 (shown as sample and hold components 3051 and 305Q) may be inserted in the feedback loop in between the low-pass filters 1601 and 160Q.
  • the sample and hold circuit 305 may cancel the static reflection components of the received signal by activating its hold mode when the transceiver is receiving a backscatter signal. While the sample and hold circuit 305 may not cancel noise components caused by slow movements in the environment, the effects of these movements may be minimized due to the long duration of such reflection changes relative to the hold periods of the circuit.
  • the sample and hold circuit 305 may also result in an overall reduction in noise caused by coupling between the In-phase (Irx) and Quadrature (Qrx) components of the received signal.
  • the embodiment of Fig. 6 also shows a balanced amplifier 512 in the feedback loop.
  • the balanced amplifier may operate in the same manner as the amplifier 175 described with reference to the previous embodiments.
  • the balance amplifier 512 may be used for impedance matching to the low pass filter 514.
  • the low pass filter 514 is optional and does not need to be included in the feedback loop of this embodiment. In the event that the low pass filter 514 is not included, the balanced amplifier 512 may still be used to match impedance to the coupler 205 to reduce non-linearities.
  • FIG. 7 shows the sub-system interfaces through which the transceiver described by the present invention may interact with other components of an RFID system 1.
  • a data conversion block 600 may provide a simple analog signal interface with digital controls.
  • a programmable logic device 605 may provide a parallel interface to a digital signal processor 610.
  • An MCU 615 may provide additional user controls and interfaces with the transceiver and other components.
  • the MCU 615 may provide the protocol for the communications between the reader and the tag including multi-tag arbitration. Such protocols may include those published by the UCC (Uniform Code Council), EAN (European Article Numbering), and ISO (International Standards Organization).
  • the MCU 615 may also provide packet data synthesis for conversion to a bit stream that may be bit encoded, modulated and transmitted by the transceiver, provide frequency hopping and channel access protocols, provide automatic gain control for a maximum signal to noise ratio and dynamic range of the received signal and provide automatic level control for transmission power control for power savings, interference mitigation, user selectable power profiling, and any applications where power control is advantageous.

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  • Engineering & Computer Science (AREA)
  • Artificial Intelligence (AREA)
  • Computer Vision & Pattern Recognition (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Theoretical Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Near-Field Transmission Systems (AREA)
  • Radar Systems Or Details Thereof (AREA)
  • Transceivers (AREA)

Claims (5)

  1. Système comportant :
    un élément émetteur (105, 110, 115, 120, 125, 130) créant un signal d'interrogation et transmettant le signal d'interrogation,
    un élément récepteur (125, 130, 140, 150, 155I, 155Q, 180I, 180Q), recevant et démodulant un signal de réflexion du signal d'interrogation et combinant (140) le signal de réflexion et un signal de rétroaction pour annuler au moins une partie des signaux d'écho radiofréquence dans le signal de réflexion, dans lequel le signal de réflexion comporte une composante d'erreur comportant de l'énergie de signal d'interrogation réfléchie par des objets dans un environnement autres qu'une étiquette radiofréquence, et dans lequel le signal de rétroaction comporte la au moins une partie des signaux d'écho radiofréquence comportant la composante d'erreur à des fréquences inférieures à un signal de données présentant un intérêt,
    dans lequel le signal de rétroaction est obtenu en isolant la composante d'erreur du signal de réflexion, et dans lequel la composante d'erreur du signal de réflexion est isolée par un filtrage passe-bas du signal de réflexion.
  2. Système selon la revendication 1, dans lequel la composante d'erreur du signal de réflexion est isolée dans un signal parmi un signal en phase et un signal en quadrature.
  3. Système selon la revendication 1, dans lequel le signal de rétroaction est combiné avec le signal de réflexion sur un temps de réponse d'impulsion d'un élément filtrant qui filtre le signal de réflexion.
  4. Système selon la revendication 1, dans lequel le signal de réflexion est réfléchi par l'étiquette radiofréquence et d'autres objets dans l'environnement autres que l'étiquette radiofréquence.
  5. Système selon la revendication 1, dans lequel le signal de rétroaction est obtenu à partir d'un traitement choisi parmi un traitement analogique et un traitement numérique.
EP04817328.0A 2003-10-21 2004-10-21 Suppression d'echos radiofréquence en duplex integral Active EP1676373B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
US10/690,390 US8077763B2 (en) 2003-10-21 2003-10-21 Full-duplex radio frequency echo cancellation
PCT/US2004/034739 WO2005041425A2 (fr) 2003-10-21 2004-10-21 Suppression d'echos radiofrequence en duplex integral

Publications (3)

Publication Number Publication Date
EP1676373A2 EP1676373A2 (fr) 2006-07-05
EP1676373A4 EP1676373A4 (fr) 2009-12-09
EP1676373B1 true EP1676373B1 (fr) 2017-11-29

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EP04817328.0A Active EP1676373B1 (fr) 2003-10-21 2004-10-21 Suppression d'echos radiofréquence en duplex integral

Country Status (5)

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US (2) US8077763B2 (fr)
EP (1) EP1676373B1 (fr)
JP (1) JP2007512728A (fr)
CA (1) CA2542983C (fr)
WO (1) WO2005041425A2 (fr)

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Also Published As

Publication number Publication date
CA2542983C (fr) 2012-11-27
JP2007512728A (ja) 2007-05-17
EP1676373A4 (fr) 2009-12-09
US20120051411A1 (en) 2012-03-01
CA2542983A1 (fr) 2005-05-06
EP1676373A2 (fr) 2006-07-05
WO2005041425A3 (fr) 2006-08-03
WO2005041425A2 (fr) 2005-05-06
US20050084003A1 (en) 2005-04-21
US8077763B2 (en) 2011-12-13

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