EP1516470B1 - Procede d'egalisation et de demodulation d'un signal de donnees transmis par l'intermediaire d'un canal variable dans le temps - Google Patents

Procede d'egalisation et de demodulation d'un signal de donnees transmis par l'intermediaire d'un canal variable dans le temps Download PDF

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Publication number
EP1516470B1
EP1516470B1 EP03760586A EP03760586A EP1516470B1 EP 1516470 B1 EP1516470 B1 EP 1516470B1 EP 03760586 A EP03760586 A EP 03760586A EP 03760586 A EP03760586 A EP 03760586A EP 1516470 B1 EP1516470 B1 EP 1516470B1
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Prior art keywords
data
scatterer
scatterer coefficients
measurement
coefficients
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German (de)
English (en)
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EP1516470A1 (fr
Inventor
Rainer Bott
Ulrich Sorger
Snjezana Gligorevic
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Rohde and Schwarz GmbH and Co KG
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Rohde and Schwarz GmbH and Co KG
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    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00Baseband systems
    • H04L25/02Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006Arrangements for removing intersymbol interference
    • H04L25/03178Arrangements involving sequence estimation techniques
    • H04L25/03248Arrangements for operating in conjunction with other apparatus
    • H04L25/03292Arrangements for operating in conjunction with other apparatus with channel estimation circuitry
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00Modulated-carrier systems
    • H04L27/26Systems using multi-frequency codes
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00Baseband systems
    • H04L25/02Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202Channel estimation
    • H04L25/0224Channel estimation using sounding signals
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00Modulated-carrier systems
    • H04L27/01Equalisers
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00Modulated-carrier systems
    • H04L27/18Phase-modulated carrier systems, i.e. using phase-shift keying
    • H04L27/22Demodulator circuits; Receiver circuits
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00Baseband systems
    • H04L25/02Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006Arrangements for removing intersymbol interference
    • H04L2025/0335Arrangements for removing intersymbol interference characterised by the type of transmission
    • H04L2025/03375Passband transmission
    • H04L2025/03414Multicarrier
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00Baseband systems
    • H04L25/02Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006Arrangements for removing intersymbol interference
    • H04L2025/03433Arrangements for removing intersymbol interference characterised by equaliser structure
    • H04L2025/03439Fixed structures
    • H04L2025/03445Time domain
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00Baseband systems
    • H04L25/02Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006Arrangements for removing intersymbol interference
    • H04L2025/03433Arrangements for removing intersymbol interference characterised by equaliser structure
    • H04L2025/03439Fixed structures
    • H04L2025/03522Frequency domain
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00Baseband systems
    • H04L25/02Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202Channel estimation
    • H04L25/024Channel estimation channel estimation algorithms
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00Baseband systems
    • H04L25/02Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006Arrangements for removing intersymbol interference
    • H04L25/03178Arrangements involving sequence estimation techniques
    • H04L25/03248Arrangements for operating in conjunction with other apparatus
    • H04L25/03286Arrangements for operating in conjunction with other apparatus with channel-decoding circuitry

Definitions

  • the invention relates to a method for equalization and for demodulating a via a time-varying channel transmitted to a receiver data signal.
  • ISI Intersymbol interference
  • ICI Interchannel Interference
  • a method for the equalization of DVB-T on the The basis of the assumption of constancy is, for example, in Burow-R; Fazel-K; Hoeher-P; Klank-O; Kussmann-H; Pogrzeba-P; Robertson-P; Ruf-M-J "On the performance of the DVB-T system in mobile environments "IEEE GLOBECOM 1998 described.
  • the method according to the invention is no longer the Channel impulse response used for the channel estimation, but rather the so-called scatterer coefficients, namely the complex valued attenuation, the delay and the Doppler shift in the port.
  • the so-called spreader (Scatterer) caused reflections between a transmitter and receiver radiated signal are the cause of the quality of the transmission channel, like this for example, is described in the book of Raymond Steele, "Mobile Radio Communications", Pentech Press, London, 1992, section 2.3.1.
  • Such scatterers as Buildings or vehicles distort that between transmitter and Receiver transmitted data signal.
  • On the distorted Data signal can in the receiver this on the scatterer ascertained Scatterer coefficients which then equalizes the distorted data signal and finally demodulated.
  • According to the Invention thus become the channel properties through this Scatterer coefficients defined in the sense of following description in a simple manner from the received distorted data signals are determined can.
  • Equation 1 shows, on the basis of a two-dimensional field, the discretization of the Doppler frequency f d and the delay ⁇ in the transmission channel for different scatterers.
  • This graph can be directly converted into a scatterer matrix S having the scattering coefficients S (m, k) as used in equations (1) to (4) below.
  • the coefficients of the matrix S represent the complex-valued attenuation values (amplitude and phase).
  • the quantization in the delay direction ⁇ and in the Doppler shift direction f d depends on the channel and data transmission method.
  • the maximum values K for the discrete normalized Doppler shift and M for the discrete normalized deceleration are given by the physical parameters of the channel.
  • Fig. 1 Five scatterers are shown, whose indices correspond to the position in the scatter matrix; the Numbering starts here with 1.
  • This physical model thus takes into account the geometry of the propagation model of the channel rather than the impulse responses.
  • This geometry and thus the delay ⁇ and Doppler shift f d associated with the respective scatterer, remains practically constant for sufficiently long times, since transmitters and / or receivers can not move as fast as desired or can perform arbitrarily fast changes in movement.
  • the impulse response of the channel can, in principle, vary arbitrarily within the permissible physical limits.
  • the discrete impulse response is calculated from the complex scatterer coefficients S (m, k)
  • K is the maximum occurring Doppler frequency
  • m is the running index for the delay
  • i is the discrete running variable for the time.
  • h (i) is the resulting discrete temporal impulse response of the channel. It is considered over the length N.
  • the maximum likelihood approach for the determination of the scatterer coefficients matrix S in the time domain yields by minimizing the subsequent expression after the scatterer coefficients.
  • the data symbols are either known directly as Training sequence provided or they will be out of the received signal through the following Method determined.
  • the estimation of the scatterer coefficients in the time domain is preferably used in data transmission methods used, which work in the time domain. Such procedures are e.g. single carrier method with PSK or QAM modulation.
  • the modulation method can be considered in equation (2) be borne by the data symbols d (i-m) the respective signal form of the modulation type used wear, if necessary with partial response pulse shaping.
  • channels with great memory, i. with long pulse duration can by the appropriate choice of the maximum delay M be equalized. This will naturally also the Observation duration N be correspondingly long.
  • the estimate of the scatterer coefficients in the Frequency range is preferably at Data transfer method used in the Frequency range work. Such methods are e.g. Multicarriermaschine like OFDM with the DVB-T procedure.
  • the data symbol D (n-k) is the waveform of the type of modulation used wear, shown here in the frequency domain.
  • the estimation is done via N samples in Time domain or N spectral components in Frequency range.
  • the estimation of the scatterer coefficients is preferably carried out by means of a recursive Kalman or an RLS algorithm, in which, after the initialization by the known symbol sequence, the channel is tracked even if the sequence is initially unknown.
  • a recursive Kalman or an RLS algorithm, in which, after the initialization by the known symbol sequence, the channel is tracked even if the sequence is initially unknown.
  • K (i) is the Kalman gain
  • P is the prediction state Covariance matrix
  • D is the data matrix resulting from (2) or (3)
  • W gives the noise covariance matrix
  • S Vector of the estimated scatter coefficients going through arranging the scatterers into a linear vector the matrix S is created.
  • r (i) is the received sampled Signal value (time or frequency range), i the index in Time or frequency direction.
  • Tree search methods are used. This is where starting from the channel estimated by the training sequence, for each of the potentially possible data sequences of Receiver built a path within a tree. For each of these paths will have a channel estimation with the Estimation of the scatterers performed and a metric according to (2) or (3) calculated. The data sequence with the Best metric is received as the most likely output. Due to the ML approach, the metric is one ML-metric.
  • This tree search method is schematically shown in FIG. 2 for represented binary symbols, ⁇ (x, ... y) denotes the metric for the assumed symbols x..y, S and the matrix of for the respective path determined scatterers.
  • the number of Indices indicates the depth of the tree, in the example up to a maximum of three.
  • the additionally marked path identifies the best path currently selected via the metric.
  • the described algorithm is a soft output algorithm, the next to the demodulated data also a measure of quality for the demodulation in the form of the metric can spend. Accordingly, it is possible not only the as to output the most likely ascertained data sequence, but even less likely. Hereby can downstream processing stages in the receiver, e.g. Decoders, get additional information based on Quality of reception.
  • the method can be further advantageous with a Convolution or block code as sole or inner Combine code of a concatenated code structure. It is known that convolution and block codes in the form of Display tree structures. A code affects the o.a. Tree structure so that not all paths, the if the code were ignored, too really exist. Therefore, such a tree is added Taking into account code information not all paths include.
  • FIG. Fig. 3 A tree derived from the example of FIG. 2 is shown in FIG Fig. 3 shown. By comparing the two trees will be clear that certain paths are not through the code existent.
  • the method according to the invention avoids this Disadvantages are not a priori.
  • the channel with Help the scatterer is modeled can by identifying the relevant scatterer the maximum occurring Delay and thus the dimension of the scatter matrix be determined. While in known methods this maximum length must always be taken into account inventive method adaptive to the maximum Delay of the channel received and the necessary Delay in demodulation and decoding be adjusted accordingly. Therefore, only in special channels, where significant Scatterer at high delays occur, the big extra Delay in demodulation and coding necessary become. Since the geometry of the scatterers is not Abrupt changes can occur when a scatterer occurs with great delay the dimension of the scatter matrix be increased adaptively. Conversely, it is also possible that the disappearance of such a scatterer the dimension the matrix is adaptively reduced.
  • L is the necessary delay. The minimum is determined via all possible data hypotheses d and all possible scatterers S.
  • the transmitted data can only be ISI in Cause time direction, i. in the past sent data affects later sent.
  • the described method can also without the Initialization work through training sequences.
  • processing is done with default values initialized, e.g. the matrix P becomes (4) as Unit matrix defaulted and the Scatterervektor S and Zero initialized.
  • the algorithm is then usually converge more slowly.
  • all possible Initial configurations for the data sequences are taken into account become.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Power Engineering (AREA)
  • Cable Transmission Systems, Equalization Of Radio And Reduction Of Echo (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
  • Communication Control (AREA)
  • Error Detection And Correction (AREA)
  • Radio Transmission System (AREA)
  • Mobile Radio Communication Systems (AREA)

Claims (28)

  1. Procédé d'égalisation et de démodulation d'un signal de données transmis à un récepteur par l'intermédiaire d'un canal variable dans le temps selon un procédé de transmission de données de monoporteuse ou de multiporteuse,
       caractérisé en ce que
       dans le récepteur, on détermine à partir du signal de données reçu les coefficients de diffuseurs amortissement, temporisation et fréquence de Doppler des diffuseurs qui entraínent les distorsions de signal dans la voie, et le signal de données est égalisé et ensuite démodulé avec ces coefficients de diffuseurs ainsi calculés.
  2. Procédé selon la revendication 1,
       caractérisé en ce que
       le calcul des coefficients de diffuseurs et l'égalisation du signal de données s'effectuent dans la plage de temps.
  3. Procédé selon la revendication 2,
       caractérisé par
       son application avec les procédés de transmission de données de monoporteuse.
  4. Procédé selon la revendication 2,
       caractérisé par
       son application avec des procédés de transmission de données de multiporteuse en cas de réception de séquences de données connues.
  5. Procédé selon la revendication 1,
       caractérisé en ce que
       le calcul des coefficients de diffuseurs et l'égalisation du signal de données s'effectuent dans la plage de fréquence.
  6. Procédé selon la revendication 5,
       caractérisé par
       son application avec des procédés de transmission de données de multiporteuse.
  7. Procédé selon l'une quelconque des revendications précédentes,
       caractérisé en ce que
       les coefficients de diffuseurs sont déterminés au moyen d'un critère de la plus grande vraisemblance.
  8. Procédé selon la revendication 7,
       caractérisé en ce que
       les coefficients de diffuseurs sont déterminés en tant que minimum de la distance euclidienne entre le signal de réception et les données, démodulés dans le récepteur, du signal de réception et de tous les coefficients de diffuseurs possibles (formules 2 et 3).
  9. Procédé selon l'une quelconque des revendications précédentes,
       caractérisé en ce que
       un premier calcul des coefficients de diffuseurs est effectué à l'aide d'une séquence de données connue.
  10. Procédé selon la revendication 9,
       caractérisé en ce que
       le premier calcul des coefficients de diffuseurs est effectué par bloc au moyen d'une séquence de données globale.
  11. Procédé selon l'une quelconque des revendications précédentes 1 à 6 ainsi que 9 et 10,
       caractérisé en ce que
       un algorithme de Kalman est utilisé de façon itérative pour le calcul des coefficients de diffuseurs.
  12. Procédé selon l'une quelconque des revendications précédentes 1 à 6 ainsi que 9 et 10,
       caractérisé en ce que
       un algorithme de recursive-least-square est utilisé de façon itérative pour le calcul des coefficients de diffuseurs.
  13. Procédé selon la revendication 9 ou 10,
       caractérisé en ce que
       les coefficients de diffuseur calculés lors du premier calcul sont utilisés pour la réception consécutive de données utiles, les données étant égalisées et démodulées par bloc au moyen d'une séquence de données globale et les coefficients de diffuseurs calculés lors du premier calcul étant corrigés avec les données ainsi égalisées et démodulées par bloc.
  14. Procédé selon la revendication 9 ou 10,
       caractérisé en ce que
       les coefficients de diffuseurs calculés lors du premier calcul sont utilisés pour la réception ultérieure de données utiles, les coefficients de diffuseur calculés lors du premier calcul étant corrigés avec les données égalisées et démodulées selon un algorithme de Kalman ou de recursive-least-square.
  15. Procédé selon la revendication 13 ou 14,
       caractérisé en ce que
       pour la correction des coefficients de diffuseurs ainsi que pour la démodulation de données, on utilise un procédé de recherche d'arbre dans lequel, pour toutes les séquences de données possibles, on détermine respectivement les coefficients de diffuseurs et les métriques et on sélectionne ensuite à partir de la structure d'arbre les séquences de données qui présentent la meilleure métrique de la plus grande vraisemblance.
  16. Procédé selon la revendication 15,
       caractérisé en ce que
       les coefficients de diffuseurs correspondants aux meilleures séquences de données sélectionnées sont utilisés ultérieurement pour l'égalisation et la démodulation.
  17. Procédé selon la revendication 15 ou 16,
       caractérisé en ce que
       le choix des séquences de données s'effectue par bloc pour l'ensemble de la séquence de données considérée.
  18. Procédé selon la revendication 15 ou 16,
       caractérisé en ce que
       le choix des séquences de données est effectué après avoir atteint une profondeur de chemin prédéfinie de l'arbre.
  19. Procédé selon les revendications 15 à 18,
       caractérisé en ce que
       on utilise un algorithme de Metric-First avec le procédé de la recherche d'arbre.
  20. Procédé selon les revendications 15 à 18,
       caractérisé en ce que
       on utilise un algorithme de Breadth-First avec le procédé de recherche d'arbre.
  21. Procédé selon les revendications 15 à 18,
       caractérisé en ce que
       on utilise un algorithme de Depth-First avec le procédé de recherche d'arbre.
  22. Procédé selon les revendications 15 à 21,
       caractérisé en ce que
       avec le procédé de recherche d'arbre, la profondeur de chemin et le nombre de chemins sont modifiés de façon adaptative selon les coefficients de diffuseurs calculés.
  23. Procédé selon l'une quelconque des revendications 15 à 22,
       caractérisé en ce que
       la valeur de métrique est éditée également lors de l'édition de la séquence de données démodulée.
  24. Procédé selon les revendications 15 à 22,
       caractérisé en ce que
       en supplément de la séquence de données, on édite avec la meilleure métrique de la plus grande vraisemblance également d'autres prochaines séquences de données optimales avec une prochaine métrique optimale de la plus grande vraisemblance.
  25. Procédé selon l'une quelconque des revendications 15 à 24,
       caractérisé en ce que
       lors de la réception de signaux de données codés selon un code avec le procédé de la recherche d'arbre, on prend en compte seulement les séquences de données correspondant à des mots de code valables.
  26. Procédé selon la revendication 25,
       caractérisé en ce que
       avec le procédé de recherche d'arbre, on utilise en supplément un algorithme de Viterbi ou un algorithme APP en tenant compte du code.
  27. Procédé selon l'une quelconque des revendications précédentes,
       caractérisé en ce que
       le premier calcul des coefficients de diffuseurs n'est effectué qu'avec des séquences inconnues de données utiles et en ce que, lors de l'initialisation des algorithmes, on utilise des valeurs par défaut au lieu de séquences d'entraínement et de synchronisation.
  28. Procédé selon l'une quelconque des revendications 7 à 10,
       caractérisé en ce que
       le nombre maximal des coefficients de diffuseurs à prendre en compte est adapté dans les algorithmes à l'aide des coefficients de diffuseurs calculés respectivement auparavant.
EP03760586A 2002-06-24 2003-05-14 Procede d'egalisation et de demodulation d'un signal de donnees transmis par l'intermediaire d'un canal variable dans le temps Expired - Lifetime EP1516470B1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
DE10228159A DE10228159A1 (de) 2002-06-24 2002-06-24 Verfahren zur Entzerrung und Demodulation eines über einen zeitveränderlichen Kanal übertragenen Datensignals
DE10228159 2002-06-24
PCT/EP2003/005068 WO2004002099A1 (fr) 2002-06-24 2003-05-14 Procede d'egalisation et de demodulation d'un signal de donnees transmis par l'intermediaire d'un canal variable dans le temps

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EP1516470B1 true EP1516470B1 (fr) 2005-10-05

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US (1) US20050220231A1 (fr)
EP (1) EP1516470B1 (fr)
KR (1) KR20050007432A (fr)
CN (1) CN1663212A (fr)
AT (1) ATE306166T1 (fr)
AU (1) AU2003232774B2 (fr)
BR (1) BR0307433A (fr)
CA (1) CA2474559A1 (fr)
DE (2) DE10228159A1 (fr)
DK (1) DK1516470T3 (fr)
ES (1) ES2249733T3 (fr)
HU (1) HU225835B1 (fr)
IL (1) IL165903A0 (fr)
MX (1) MXPA04010997A (fr)
NO (1) NO20050321L (fr)
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ZA (1) ZA200404576B (fr)

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DE102006014064A1 (de) * 2005-12-23 2007-06-28 Rohde & Schwarz Gmbh & Co. Kg Verfahren und Entzerrer zur Entzerrung einer über einen zeitveränderlichen Übertragungskanal empfangenen Datensymbol-Sequenz
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IL165903A0 (en) 2006-01-15
CN1663212A (zh) 2005-08-31
HUP0500020A2 (hu) 2005-05-30
ES2249733T3 (es) 2006-04-01
NO20050321L (no) 2005-01-20
US20050220231A1 (en) 2005-10-06
CA2474559A1 (fr) 2003-12-31
MXPA04010997A (es) 2005-05-27
AU2003232774A1 (en) 2004-01-06
HU225835B1 (en) 2007-10-29
ZA200404576B (en) 2005-06-09
AU2003232774B2 (en) 2007-05-10
DE10228159A1 (de) 2004-01-22
DK1516470T3 (da) 2006-02-20
DE50301325D1 (de) 2005-11-10
ATE306166T1 (de) 2005-10-15
WO2004002099A1 (fr) 2003-12-31
KR20050007432A (ko) 2005-01-18
BR0307433A (pt) 2004-12-28
EP1516470A1 (fr) 2005-03-23

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