EP0793361B1 - Circuit pour décoder des informations supplémentaires dans une transmission de radiodiffusion - Google Patents

Circuit pour décoder des informations supplémentaires dans une transmission de radiodiffusion Download PDF

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Publication number
EP0793361B1
EP0793361B1 EP96102902A EP96102902A EP0793361B1 EP 0793361 B1 EP0793361 B1 EP 0793361B1 EP 96102902 A EP96102902 A EP 96102902A EP 96102902 A EP96102902 A EP 96102902A EP 0793361 B1 EP0793361 B1 EP 0793361B1
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EP
European Patent Office
Prior art keywords
signal
filter
characteristic
auxiliary data
quality characteristic
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP96102902A
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German (de)
English (en)
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EP0793361A1 (fr
Inventor
Thomas Dipl.-Ing. Hilpert
Stefan Dipl.-Ing. Müller
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
TDK Micronas GmbH
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TDK Micronas GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by TDK Micronas GmbH filed Critical TDK Micronas GmbH
Priority to DE59611437T priority Critical patent/DE59611437D1/de
Priority to EP96102902A priority patent/EP0793361B1/fr
Priority to US08/805,767 priority patent/US5978037A/en
Publication of EP0793361A1 publication Critical patent/EP0793361A1/fr
Application granted granted Critical
Publication of EP0793361B1 publication Critical patent/EP0793361B1/fr
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04H—BROADCAST COMMUNICATION
    • H04H40/00—Arrangements specially adapted for receiving broadcast information
    • H04H40/18—Arrangements characterised by circuits or components specially adapted for receiving
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04H—BROADCAST COMMUNICATION
    • H04H20/00—Arrangements for broadcast or for distribution combined with broadcast
    • H04H20/28—Arrangements for simultaneous broadcast of plural pieces of information
    • H04H20/33—Arrangements for simultaneous broadcast of plural pieces of information by plural channels
    • H04H20/34—Arrangements for simultaneous broadcast of plural pieces of information by plural channels using an out-of-band subcarrier signal

Definitions

  • the invention relates to a circuit for decoding additional information in a signal mixture.
  • Such circuits serve to obtain additional information from the received signals of the audio or video consumption area. These are usually auxiliary information that allows the user to facilitate the operation of the respective receiving device. For example, for the motorist, the identifier of a received station as an auto information station is an important indicator. Similar additional information is also available for television signals which transmit a digital identifier for audio playback, whether the respective audio channel is a mono, stereo or multi-tone signal is.
  • this information is additionally inserted as AM or FM signal into the existing signal mixture.
  • the decoding of this additional information is usually easy to implement with known analog or after an analog / digital conversion with digital circuits.
  • the rapid change and the constant re-introduction of such additional information there are also difficulties, because under certain circumstances, the controlled by the additional information switching by adjacent channels and poor reception conditions are very disturbed and lead to false evaluations of additional information.
  • a signal quality characteristic value is formed from the received signal, which intervenes in the detection device of the respective reproduction mode controlled by an identification signal and thus forms an adaptive decoding device for the identification signal.
  • the signal quality characteristic is derived predominantly from the received field strength, but also from the broadband noise content of the received signal, which is detected by means of an FM detector or by means of an existing anyway noise reduction circuit.
  • time constants for the reproduction switching are influenced in such a way that erroneous switching over due to generally poor signal conditions or short-term disturbances is largely ruled out.
  • a simple influencing of thresholds and hystereses in the identification signal recognition device is also indicated, as a result of which the faulty switching over in the event of disturbed reception conditions is likewise reduced.
  • US 4,737,993 also describes an adaptive decoder for the respective playback mode, which is also adapted via a signal quality characteristic to the respective reception conditions, but the signal quality characteristic is determined only as a function of the reception field strength at the antenna input.
  • the sub-signal is attenuated differently depending on the signal quality characteristic before further processing in the matrix.
  • a further development consists in influencing the possibly also attenuated sub-signal before further processing in the matrix by means of a voltage-controlled filter in the frequency characteristic.
  • the upper frequency components of the sub signal are attenuated differently.
  • the solution of the problem has the advantage that existing circuit concepts can basically be used further and the improvements can be achieved via simple additional circuits. Since the signal processing is generally purely digital, it is unimportant for the processing whether additional circuits are used for the additional functions or whether the additional functions are realized via additional program steps by means of already existing processors. Here, the effort is only in a modified program.
  • the signal quality characteristic which is a measure of the quality of the received signal, can be determined at different points in the signal mixture. Of course, this depends on the type of signal mix.
  • the advantage of digital processing is that the signals are generally available as normalized signals whose value range lies within the numerical values -1 and +1. About the defined level of the carrier and its noise-induced amplitude fluctuations can then easily be determined such a quality value.
  • the general noise can be advantageously determined or a disturbing external signal.
  • Such signal ranges can be found in particular in the specified signal mixtures of the consumption range, because for compatibility reasons, the individual signal ranges usually do not overlap.
  • the additional information is coupled with different carriers, which in the frequency spectrum so are arranged so that their modulation ranges do not overlap. There should be no signal in the intermediate areas if the signal is good or the reception conditions are good.
  • About the determination of the respective noise value in these areas can, for. B. by a complementation or quotient a signal quality characteristic can be determined.
  • the improved with the Signalgütekennwert evaluation of additional information has the advantage that the filter cost can remain relatively low.
  • the increased safety in the evaluation of the disturbed additional information does not result from a higher quality of the filter. This is possible because, as it were, the interference component and not the useful signal component is detected and evaluated.
  • the determination of a relatively high noise component - a low interference component is of no interest because it does not cause false decoding - generally does not require narrow-band filters for the present signals. For blanking the useful signal range, therefore, simple notch filters or band-pass filters whose blocking range is set so that the respective useful or additional signal is largely suppressed.
  • the block diagram of Fig. 1 shows a receiving means 10 for a composite signal sf ', which is a stereo multiplex signal for the embodiment.
  • the conversion of the high-frequency transmitted signal mixture takes place in the baseband, which is shown schematically for the example given in FIG.
  • the baseband signal mixture sf is digitized and is supplied to a signal processing device 20 for audio signals, which generates the desired output signals R, L via further mixers 22 and sound processing stages 24.
  • the signals sf are further supplied to a mixer device 32, with which the additional information fz in the signal mixture sf is converted into a lower frequency position, in particular into a baseband position.
  • the individual components ki can be separated from one another by means of simple filter devices 35, 36, 37.
  • the separated components ki are then supplied to a decoder 40 to form the individual identification signals kz, for example, a mono / stereo switching signal u or an auto-radio information (ARI) signal supplied to the sound processing stage 24 and the receiving means 10, respectively.
  • a decoder 40 to form the individual identification signals kz, for example, a mono / stereo switching signal u or an auto-radio information (ARI) signal supplied to the sound processing stage 24 and the receiving means 10, respectively.
  • the processing frequencies are previously reduced by means of decimation devices in order to reduce the circuit complexity for the filters.
  • a signal-free frequency section is further detected by means of a bandpass filter 38, a signal-free frequency section to determine therefrom by means of a device 50 a signal quality characteristic kg.
  • This signal quality characteristic kg is fed to the decoder 40, which can thereby adapitively adapt to the respective reception conditions.
  • FIG. 2 shows the frequency scheme of a stereo multiplex signal sf which contains a subcarrier at 57 kHz which is modulated with additional information fz, for example an ARI identification signal.
  • the invention can also increase the reliability of the pilot signal recognition at 19 kHz. whereby the automatic stereo switching is less disturbed.
  • the signal mixture sf refers to a standardized television signal with a first and second sound carrier FM1, FM2, wherein the sound carrier FM2 contains additional information fz 'via an AM modulation. Since the additional information fz 'is in the range of the carrier FM2, the preceding processing steps for prefiltering and frequency conversion are not shown in FIG. 3 for the sake of clarity, but instead a source 310 for this preprocessed signal fz' is indicated in the preprocessing device 300.
  • the carrier FM2 is therefore no longer at the frequency 54 kHz, but at a lower frequency, for example between 8 kHz and 10 kHz.
  • the video signal, the R + L signal at the carrier FM1 and the R signal at the carrier FM2 are no longer or only as residues.
  • the output signal fz 'of the source 310 thus contains only the carrier FM2 and optionally a frequency line k1 at 171.5 Hz or a frequency line k2 at a distance of 274.1 Hz as the upper and lower sideband Frequency lines are encoded as to whether the respective audio channel contains a stereo or bilingual signal.
  • the source 310 is followed by a preprocessing device 320 for the additional information area fb (see Fig. 4), which essentially contains a decimation device with a decimation filter. Possible DC components are suppressed by a DC voltage suppression circuit 330.
  • the filtered additional signal fz is supplied to an adaptive decoding device 400 whose output supplies the desired identification signals M, S, B for monaural, stereo or double-voice operation.
  • the adaptive decoder 400 contains in the input an absolute value generator 405 serving as a signal rectifier for demodulating the AM-modulated signal fz, followed by a decimation stage 410, with which the clock frequency is reduced from 32 kHz to 2 kHz.
  • an absolute value generator 405 serving as a signal rectifier for demodulating the AM-modulated signal fz, followed by a decimation stage 410, with which the clock frequency is reduced from 32 kHz to 2 kHz.
  • a bandpass 415 and an absolute value generator 420 the amplitude of the signal k1 is determined at 171 Hz and fed to the minuend input of a subtracter 425.
  • a bandpass 430 and an absolute value generator 435 the amplitude of the signal k2 is determined at 274 Hz and fed to the subtrahend input of the subtractor 425. From the difference, a resultant characteristic value ka is formed by means of a low-pass filter 440.
  • the wanted identification signals kz or M, S, B could be determined from this characteristic value ka as in a non-adaptive decoding device.
  • a range of values from +0.2 to +1 would correspond to the stereo identification signal S
  • a range from -0.2 to +0.2 would correspond to the mono identification signal M
  • a range from -1 to -0.2 would correspond to the dual-language identity signal B.
  • the resulting characteristic ka is modified by means of the signal quality characteristic kg.
  • the switching thresholds for the modified characteristic value km are predetermined by a threshold value recognition circuit 445, wherein the threshold value position can be identical to the non-adaptive circuit.
  • the additional circuit 500 contains in its input a bandpass filter 550 which is fed with the filtered additional signal fz.
  • the middle position of this filter is expediently chosen so that the lower selection edge does not or only slightly detects the carrier FM2 with the first or second identification signal k1, k2, cf. Fig. 5.
  • the overlying frequency components should be transmitted as possible without attenuation.
  • the preceding filter 320 must therefore not come too close to the carrier FM2 with its upper selection edge, because otherwise the filter 320 already suppresses these frequencies and the bandpass filter 550 no longer finds a frequency range to be evaluated.
  • the noise or noise components at the output of the bandpass 550 are rectified by means of a squarer 555.
  • the squaring effect at the same time Weighting of the measured signal values.
  • a low-pass filter 560 smoothes the signal curve and by means of a decimator 565 the clock frequency is reduced from 32 kHz to 2 kHz.
  • the output signal of the decimator 565 corresponds to an interference characteristic value ks which lies between the values 0 and +1 and increases or decreases in parallel with the measured interference content.
  • the signal quality parameter kg is formed from this value ks by subtracting the interference parameter ks from the numerical value +1.
  • the adaptive action of the signal quality parameter kg on the original characteristic value ka is effected by means of a multiplier 575 whose output signal is a modified or adaptive characteristic value km, which supplies the desired identification signals kz or M, S, B by means of the threshold value recognition device 445.
  • the signal quality parameter kg assumes the value +1, whereby the original characteristic value ka is not changed. However, if the noise component in the filtered additional signal fz increases, then the signal quality parameter kg becomes smaller and drops, for example, to the value 0.5. The value of the original characteristics ka is thereby halved, whereby the tendency for the mono-identification signal M is increased. Individual signal outliers, which are caused by noise or foreign signals are thus prevented - for example, in mono mode or when receiving a signal without the carrier FM2 - wrong to switch the receiver. This is especially important for safe mono operation when the received signal contains neither a stereo nor a bilingual signal. As a result of the invention, however, an unsafe reception is possible only with unique identification signals k1, k2 or ka in unsecure reception conditions.
  • the digital low-pass filter 560 may also include non-linear stages or counters that are differently charged or discharged to further enhance noise suppression. It should be noted that the embodiment of Fig. 3 represents only an advantageous embodiment of the invention. Advantageous developments of individual functional units or entire functional groups are set at the discretion of the person skilled in the art.
  • FIG. 4 schematically shows the frequency scheme of a standardized television signal mix sf.
  • the frequency-modulated audio signal range with the first carrier FM1 at 5.5 MHz follows the video signal range from 0 Hz to about 5 MHz.
  • the R + L signal is transmitted in a stereo signal, which also represents the mono signal. In a multi-tone transmission, this area contains the first sound signal.
  • the second carrier FM2 which contains in frequency modulation the 2R signal or the second audio signal. From the R + L signal and the 2R signal, the R and L signals are known to be formed by means of a stereo matrix. However, there are many TV channels that do not yet broadcast this second carrier FM2.
  • the additional identifier with respect to the mono, stereo or multi-tone operation is superimposed on the carrier FM2 by means of the multiply described, very low-frequency and thus inaudible amplitude modulation.
  • FIG. 5 schematically shows the frequency scheme of the signal fz after the preprocessing device 300. So that a digital signal processing can be done at 32 kHz, the carrier FM2 has been implemented in the stage 300 from 54 kHz to 9 kHz. The signal fz no longer contains any audio information, but solely the possibly amplitude-modulated carrier FM2. The upper and lower sidebands contain either the frequency line k1 or the frequency line k2. Both are as indicated close to the carrier FM2.
  • the signal region fb separated in the preprocessing device 300 which is to contain the additional information fz and a signal-free region of the signal mixture sf, is shown schematically.
  • the associated passband of the bandpass filter 550 schematically shows the dashed line 550, which essentially detects the signal-free region in the separated signal range fb. It is irrelevant if a small proportion of the carrier FM2 is still included. Furthermore, it is irrelevant how far the passband exceeds the separated signal range fb, if it is ensured that there are no more signal components. As a result, the requirements for the filter 550 are very low and it is easy to implement with digital means.

Claims (6)

  1. Circuit de décodage d'une information supplémentaire (fz) dans un signal complet (sf) comprenant :
    - une installation de filtre (34, 300) pour séparer une plage de signal ((fb)) dans le signal complet (sf) et qui contient l'information supplémentaire (fz) sous forme codée,
    - un décodeur adaptatif (40, 400) qui décode l'information supplémentaire (fz) dans la plage de signal séparé ((fb)) en tenant compte d'un signal de qualité de caractéristique (kg) et
    - une installation (50, 500) pour déterminer le signal de qualité de caractéristique
    caractérisé en ce que
    l'installation (50, 500) définit le signal de qualité de caractéristique (kg) du signal complet (sf) à partir du signal de bruit contenu, à l'aide d'un filtre (38, 550),
    la plage de fréquence du signal complet servant à déterminer le signal de qualité de caractéristique étant convertie dans une position de bande de base et elle ne comporte pas de contenu de signal utile dans le cas d'un signal complet normalisé.
  2. Circuit selon la revendication 1,
    caractérisé en ce que
    le décodeur adaptatif (40, 400) modifie au moins une valeur de caractéristique (ki, ka) et/ ou au moins un seuil d'évaluation.
  3. Circuit selon la revendication 1,
    caractérisé en ce que
    le filtre (38, 550) est réalisé pour que sa plage passante saisisse principalement la plage de signal séparé (fb), l'information supplémentaire (fz) se situant dans la plage bloquée, ou éliminée par d'autres filtres.
  4. Circuit selon la revendication 3,
    caractérisé en ce que
    le filtre (38, 550) comporte un filtre à encoches ou un filtre passe-bande dont la plage d'encoches ou de blocage élimine l'information supplémentaire (fz).
  5. Circuit selon la revendication 3 ou 4,
    caractérisé en ce que
    le signal de sortie du filtre (38, 550) est élevé au carré et est filtré par un filtre passe-bande dans les étages suivants (550, 560) pour représenter une caractéristique de perturbation (ks) que l'on retranche d'un nombre prédéfini dans un soustracteur (575), la valeur de sortie du soustracteur (575) étant le signal de qualité de caractéristique (kg).
  6. Circuit selon l'une des revendications 1 à 5,
    caractérisé en ce que
    dans le décodeur adaptatif (40, 400) on multiplie au moins une caractéristique (ki, ka) avec le signal de qualité de caractéristique (kg).
EP96102902A 1996-02-27 1996-02-27 Circuit pour décoder des informations supplémentaires dans une transmission de radiodiffusion Expired - Lifetime EP0793361B1 (fr)

Priority Applications (3)

Application Number Priority Date Filing Date Title
DE59611437T DE59611437D1 (de) 1996-02-27 1996-02-27 Schaltung zur Dekodierung einer Zusatzinformation in einer Rundfunkübertragung
EP96102902A EP0793361B1 (fr) 1996-02-27 1996-02-27 Circuit pour décoder des informations supplémentaires dans une transmission de radiodiffusion
US08/805,767 US5978037A (en) 1996-02-27 1997-02-25 Circuit for decoding additional information in a composite signal

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
EP96102902A EP0793361B1 (fr) 1996-02-27 1996-02-27 Circuit pour décoder des informations supplémentaires dans une transmission de radiodiffusion

Publications (2)

Publication Number Publication Date
EP0793361A1 EP0793361A1 (fr) 1997-09-03
EP0793361B1 true EP0793361B1 (fr) 2007-07-11

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EP96102902A Expired - Lifetime EP0793361B1 (fr) 1996-02-27 1996-02-27 Circuit pour décoder des informations supplémentaires dans une transmission de radiodiffusion

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EP (1) EP0793361B1 (fr)
DE (1) DE59611437D1 (fr)

Families Citing this family (8)

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US7877290B1 (en) 1999-03-29 2011-01-25 The Directv Group, Inc. System and method for transmitting, receiving and displaying advertisements
US7552458B1 (en) * 1999-03-29 2009-06-23 The Directv Group, Inc. Method and apparatus for transmission receipt and display of advertisements
EP1158706A1 (fr) * 2000-05-23 2001-11-28 Sony International (Europe) GmbH Décodeur RDS pour réduire l'influence de pointes de bruit en utilisant un dispositif d'élimination de bruit
US7085529B1 (en) 2001-10-24 2006-08-01 The Directv Group, Inc. Method and apparatus for determining a direct-to-home satellite receiver multi-switch type
JP4859412B2 (ja) * 2005-08-26 2012-01-25 クラリオン株式会社 ディジタル放送受信装置、ディジタル放送受信方法、およびプログラム
US8775319B2 (en) 2006-05-15 2014-07-08 The Directv Group, Inc. Secure content transfer systems and methods to operate the same
US8687947B2 (en) 2012-02-20 2014-04-01 Rr Donnelley & Sons Company Systems and methods for variable video production, distribution and presentation
US8826316B2 (en) 2012-10-22 2014-09-02 The Nielsen Company (Us), Llc Systems and methods for configuring media devices utilizing audio codes or signatures

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DE59611437D1 (de) 2007-08-23
EP0793361A1 (fr) 1997-09-03
US5978037A (en) 1999-11-02

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