EP0725481B1 - Treiberschaltung mit Ladungspumpe für einen Leistungstransistor - Google Patents

Treiberschaltung mit Ladungspumpe für einen Leistungstransistor Download PDF

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Publication number
EP0725481B1
EP0725481B1 EP95830026A EP95830026A EP0725481B1 EP 0725481 B1 EP0725481 B1 EP 0725481B1 EP 95830026 A EP95830026 A EP 95830026A EP 95830026 A EP95830026 A EP 95830026A EP 0725481 B1 EP0725481 B1 EP 0725481B1
Authority
EP
European Patent Office
Prior art keywords
input terminal
control circuit
driver circuit
control
power transistor
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP95830026A
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English (en)
French (fr)
Other versions
EP0725481A1 (de
Inventor
Angelo Alzati
Aldo Novelli
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
STMicroelectronics SRL
Original Assignee
STMicroelectronics SRL
SGS Thomson Microelectronics SRL
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by STMicroelectronics SRL, SGS Thomson Microelectronics SRL filed Critical STMicroelectronics SRL
Priority to DE69529331T priority Critical patent/DE69529331T2/de
Priority to EP95830026A priority patent/EP0725481B1/de
Priority to US08/594,707 priority patent/US5770967A/en
Priority to JP8016103A priority patent/JPH08288809A/ja
Publication of EP0725481A1 publication Critical patent/EP0725481A1/de
Application granted granted Critical
Publication of EP0725481B1 publication Critical patent/EP0725481B1/de
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors
    • H03K17/6871—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors the output circuit comprising more than one controlled field-effect transistor
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/06—Modifications for ensuring a fully conducting state
    • H03K17/063—Modifications for ensuring a fully conducting state in field-effect transistor switches

Definitions

  • This invention relates to a power transistor control circuit of the charge pump type which includes a device for checking the charged state of the pump capacitor.
  • the invention concerns a charge pump control circuit for a power transistor which comprises a driver circuit connected to a first supply voltage reference through a diode and to a second voltage reference through a load, said driver circuit being connected to the power transistor, and the power transistor, linked to a pump capacitor, is connected between a further supply voltage reference and the load.
  • control circuits of the charge pump type are generally used in high-voltage applications that employ power transistors of the MOS type. Such circuits can provide, across the pump capacitor, a higher voltage than the supply voltage.
  • a basic requirement for proper operation of the circuit is that the pump capacitor Cb should be sufficiently charged before the driver circuit is turned on.
  • FIG. 1 Shown in this Figure 1 is a prior art control circuit which comprises a driver circuit PIL connected to a first supply voltage Vcc through a diode D' and to a ground reference voltage GND through a load resistance RL'.
  • a driver circuit PIL connected to a first supply voltage Vcc through a diode D' and to a ground reference voltage GND through a load resistance RL'.
  • the driver circuit PIL is input with a control signal Si, and has an output connected to a power transistor MP'.
  • the power transistor MP' is connected between a second supply voltage VH and the load resistance RL', in parallel with a pump capacitor Cb'.
  • This resistance RL' By providing the load resistance RL', a low impedance toward ground can be achieved. This resistance RL', therefore, performs its charging function by virtue of a current, designated Ic' in the Figure, being flowed therethrough.
  • circuit of Figure 1 cannot provide for the capacitor Cb' to become sufficiently charged before any enable signal is applied to the input of the driver circuit PIL.
  • This documents relates to a charge pump circuit for driving a power MOS transistor half-bridge including two power transistors M1 and M2 allowing to obtain a voltage Vp variable between to values higher than the supply voltage Vs.
  • a charge pump circuit CPC including a charge pump capacitor, supplies the required voltage to two driving stages of said power transistors M1 and M2.
  • the underlying technical problem of this invention is to provide a control circuit for power transistors, which has appropriate structural and functional features to measure the charged state of the capacitor Cb' and correctly drive the driver circuit, thereby overcoming the limitations and drawbacks with which prior art circuits are beset.
  • the solutive idea on which this invention stands is one of making the charge signal of the pump capacitor dominant over any other circuit enable signals.
  • control circuit With reference in particular to the example shown in Figure 2, generally denoted by the reference CC is a control circuit according to the invention.
  • the control circuit CC comprises a driver stage 1 connected between a first supply voltage Vcc and a second voltage reference, such as a signal ground GND.
  • the driver stage 1 is connected to the first supply voltage reference Vcc through a diode D, and to ground GND through a load represented by a resistance RL.
  • the driver stage 1 is also connected to a power transistor MP of the MOS type.
  • the power transistor MP being linked to a pump capacitor Cb, is connected between a second supply voltage VH and the load resistance RL.
  • a switch 3 linked to a control logic 2 is connected between the driver circuit 1 and the load resistance RL.
  • This control logic 2 is connected between the first supply voltage Vcc and ground GND, and linked to the driver circuit 1 and to a circuit 4 for checking the charged state of the pump capacitor Cb, to be described.
  • the switch 3 comprises a transistor M1 of the MOS type.
  • the transistor M1 has its source terminal S1 connected to the driver circuit 1 and to a common node X between the power transistor MP and the pump capacitor Cb.
  • the drain terminal D1 of the transistor M1 is connected to ground GND through the load resistance RL, while the gate terminal G1 thereof is connected to an output 9u of the control logic 2.
  • the control logic 2 comprises a first logic gate 5 of the AND type having its output connected to the driver circuit 1.
  • the first logic gate 5 receives, on a first input 6, a control signal Si for the driver circuit 1.
  • this control signal Si is basically a square wave.
  • the control logic 2 further comprises a flip-flop 9, said flip-flop having its output terminal Q connected to a second input terminal 7 of the first logic gate 5 and to the gate terminal G1.
  • the input terminals S and R of the flip-flop 9 are connected to respective outputs 14 and 14' of first and second comparators A1 and A2.
  • the first A1 and second comparators A2 have respective first input terminals 12 and 12' connected to the first supply voltage Vcc, and respective second input terminals 13 and 13' connected to respective generators of reference voltage VR1 and VR2.
  • the comparator A2 is connected to the input terminal R of the flip-flop 9 through a second logic gate 8 of the AND type. Specifically, the comparator A2 is connected to a first input terminal 11 of the second logic gate 8 connected, in turn, with its output to the input terminal R of the flip-flop 9.
  • the second input terminal 10 of the logic gate 8 is connected to an additional comparator A3 which is incorporated to the circuit 4 for checking the charged state of the capacitor Cb.
  • the comparator A3 has a first input terminal 14 connected to the drain terminal D1 of the transistor M1 and a second input terminal 15 connected to a generator of a reference voltage VR3.
  • the reference voltage VR1 of the first comparator A1 is less than the reference voltage VR2 of the second comparator A2.
  • the output of the second comparator A2 goes to a low logic value LL0.
  • This low logic value is applied to the input terminal 11 of the AND logic gate 8 and holds a low logic value LL0 at the output terminal of that gate 8. Accordingly, the comparator A2 is called an under-voltage lockout comparator.
  • the high logic value LL1 is applied to the input terminal S (SET input) of the flip-flop 9, while the low logic value LL0 is applied to the input terminal R (RESET input) of that flip-flop 9.
  • the output terminal Q of the flip-flop 9 is in a high logic state LL1, and the MOS transistor M1, being driven by that high logic value LL1, closes the charging circuit of the pump capacitor Cb.
  • the power transistor MP is held in the off state.
  • the output of the AND logic gate 5 which controls the driver stage 1 has a low logic value LL0, due to the output Q of the flip-flop 9 being inverted to the input 7 of the AND logic gate 5.
  • I c Vcc - V D R *e -t/RCb
  • Vc Vcc - V D * (1 - e -t/RCb )
  • VR3 the reference voltage
  • the output signal 11 from the comparator A2 switches to a high logic level LL1.
  • the terminal R of the flip-flop 9 goes to a high logic value LL1.
  • the signal at the output Q of the flip-flop 9 achieves a low logic level LL0.
  • This low logic level LL0 is inverted at the input 7 of the AND logic gate 5 to re-enable the driver circuit 1 and disable the transistor M1.
  • the circuit of this invention may also be used with supply voltages Vcc higher than 500V. High supply voltage values are suitable to drive inductive loads that would require, however, a mechanism for preventing that parasitic bipolar transistors are turned on.
  • circuit of this invention can be modified as shown in Figure 4.
  • a second diode D2 is connected between the driver circuit 1 and the source terminal S1 of the transistor M1 included in the switch 3.
  • the parasitic transistor Tp is of the NPN type, and has its emitter terminal Ep connected to the source terminal S1 of the transistor M1, and its base terminal Bp connected to ground GND.
  • the diode D2 inhibits current backflow through that parasitic transistor Tp, thereby preventing that it is turned on.
  • control circuit of this invention allows the charging of the pump capacitor Cb to be completed before the driver circuit 1 is enabled.
  • the charged state of the pump capacitor Cb is, in fact, dominant over any other enable signals.
  • control circuit of this invention will ensure that the power transistor MP is properly powered at all times, by preventing that it is turned on whenever the operating conditions are not correct (e.g., an underthreshold condition).
  • the circuit of this invention also prevents, in an alternative embodiment thereof, that any parasitic transistors in parallel with the load are turned on.

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  • Dc-Dc Converters (AREA)
  • Electronic Switches (AREA)

Claims (10)

  1. Ladungspumpensteuerschaltung für einen Leistungstransistor mit einer Treiberschaltung (1), die mit einer ersten Versorgungsspannungsreferenz (Vcc) über eine Diode (D) und mit einer zweiten Spannungsreferenz (GND) über eine Last (RL) verbunden ist, wobei die Treiberschaltung (1) mit dem Leistungstransistor (MP) verbunden ist und der Leistungstransistor, verbunden mit einem Pumpkondensator (Cb), zwischen eine weitere Versorgungsspannungsreferenz (VH) und die Last (RL) geschaltet ist, und mit einer Steuerlogik (2), die zwischen die erste Versorgungsspannungsreferenz (Vcc) und die zweite Spannungsreferenz (GND) geschaltet und mit der Treiberschaltung (1) verbunden ist, gekennzeichnet durch einen Schalter (3), der zwischen den Leistungstransistor (MP) und die Last (RL) geschaltet und außerdem mit der Treiberschaltung (1) verbunden ist, und einen Schaltungsteil (4) zum Überprüfen des Ladungszustandes des Pumpkondensators (CB) mit einem Eingangsanschluß (14), der mit der Last (RL) verbunden ist, und einem Ausgangsanschluß, der verbunden ist mit der Steuerlogik (2), die das vollständige Laden des Pumpkondensators (CB) vor der Freigabe der Treiberschaltung (1) erlaubt.
  2. Steuerschaltung nach Anspruch 1, dadurch gekennzeichnet, daß die Steuerlogik (2) wenigstens ein erstes Logikgate (15) des UND-Typs aufweist, das dazu in der Lage ist, an einem ersten Eingangsanschluß (6) ein Steuersignal (Si) für die Treiberschaltung (1) zu empfangen.
  3. Steuerschaltung nach Anspruch 2, dadurch gekennzeichnet, daß das Steuersignal (Si) ein Rechteckwellensignal ist.
  4. Steuerschaltung nach Anspruch 2, dadurch gekennzeichnet, daß die Steuerlogik (2) aufweist: einen ersten Komparator (A1) und einen zweiten Komparator (A2) in Parallelschaltung, ein zweites Logikgate (8) des UND-Typs und ein Flipflop (9), wobei das Flipflop (9) einen Ausgangsanschluß (Q) aufweist, der mit einem zweiten Einganganschluß (7) des ersten Logikgates (5) verbunden ist.
  5. Steuerschaltung nach Anspruch 4, dadurch gekennzeichnet, daß das Flipflop (9) einen ersten Eingangsanschluß (S) und einen zweiten Eingangsanschluß (R) aufweist, wobei der erste Eingangsanschluß (S) mit dem Ausgang des ersten Komparators (A1) und der zweite Eingangsanschluß (R) mit dem Ausgang des zweiten Komparators (A2) über das zweite Logikgate (8) verbunden sind.
  6. Steuerschaltung nach Anspruch 4, dadurch gekennzeichnet, daß das zweite Logikgate (8) einen ersten Eingangsanschluß (10), der mit der den Ladungszustand überprüfenden Schaltung (4) verbunden ist, und einen zweiten Eingangsanschluß (11), der mit dem zweiten Komparator (A2) verbunden ist, aufweist.
  7. Steuerschaltung nach Anspruch 6, dadurch gekennzeichnet, daß der erste Komparator (A1) und der zweite Komparator (A2) je einen ersten Eingangsanschluß (12, 12'), der mit der ersten Versorgungsspannung (Vcc) verbunden ist, und je einen zweiten Eingangsanschluß (13, 13'), der mit entsprechenden für eine Referenzspannungsgeneratoren (VR1, VR2) verbunden sind, aufweisen.
  8. Steuerschaltung nach Anspruch 1, dadurch gekennzeichnet, daß der Schalter (3) einen Transistor (M1) des MOS-Typs umfasst, aufweisend einen Sourceanschluß (1), der mit der Treiberschaltung (1) und mit einem gemeinsamen Knoten (X) zwischen dem Leistungstransistor (MP) und dem Pumpkondensator (Cb) verbunden ist, einen mit der Steuerlogik (1) verbundenen Gateanschluß (G1) und einen mit der Last (RL) verbundenen Drainanschluß (D1).
  9. Steuerschaltung nach Anspruch 1, dadurch gekennzeichnet, daß die Schaltung (4) zum Überprüfen des Ladungszustandes einen Komparator (A3) mit einem mit der Last (RL) verbundenen ersten Eingangsanschluß (14) und einem mit einem einer Referenzspannungsgenerator(VR3) verbundenen zweiten Eingangsanschluß (15) aufweist.
  10. Steuerschaltung nach Anspruch 8, dadurch gekennzeichnet, daß der Schalter (3) außerdem eine Diode (D2) aufweist, die zwischen den MOS-Transistor (M1) und die Treiberschaltung (1) geschaltet ist.
EP95830026A 1995-01-31 1995-01-31 Treiberschaltung mit Ladungspumpe für einen Leistungstransistor Expired - Lifetime EP0725481B1 (de)

Priority Applications (4)

Application Number Priority Date Filing Date Title
DE69529331T DE69529331T2 (de) 1995-01-31 1995-01-31 Treiberschaltung mit Ladungspumpe für einen Leistungstransistor
EP95830026A EP0725481B1 (de) 1995-01-31 1995-01-31 Treiberschaltung mit Ladungspumpe für einen Leistungstransistor
US08/594,707 US5770967A (en) 1995-01-31 1996-01-31 Device and method for controlling a power switch
JP8016103A JPH08288809A (ja) 1995-01-31 1996-01-31 パワー・トランジスタ用チャージ・ポンプ制御回路

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
EP95830026A EP0725481B1 (de) 1995-01-31 1995-01-31 Treiberschaltung mit Ladungspumpe für einen Leistungstransistor

Publications (2)

Publication Number Publication Date
EP0725481A1 EP0725481A1 (de) 1996-08-07
EP0725481B1 true EP0725481B1 (de) 2003-01-08

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Application Number Title Priority Date Filing Date
EP95830026A Expired - Lifetime EP0725481B1 (de) 1995-01-31 1995-01-31 Treiberschaltung mit Ladungspumpe für einen Leistungstransistor

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US (1) US5770967A (de)
EP (1) EP0725481B1 (de)
JP (1) JPH08288809A (de)
DE (1) DE69529331T2 (de)

Families Citing this family (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE19721499C1 (de) * 1997-05-22 1998-06-18 Siemens Ag Schaltungsanordnung zur Ansteuerung eines FET
US6275074B1 (en) * 1998-01-06 2001-08-14 Texas Instruments Incorporated System for propagating a digital signal through a slew-rate limited node and method of operation
JP3639189B2 (ja) * 2000-06-22 2005-04-20 株式会社デンソー 負荷駆動回路
US6392446B1 (en) * 2001-06-01 2002-05-21 Hewlett-Packard Company Device and method for reducing a time constant of a data bus during a voltage transition
JP4300058B2 (ja) * 2003-05-15 2009-07-22 パナソニック株式会社 電圧発生装置、電荷転送装置、固体撮像素子、固体撮像システムおよび電圧発生方法
DE602006002507D1 (de) 2006-07-04 2008-10-09 Infineon Technologies Ag Ladungspumpe und Bootstrap-Kondensator
US10365833B2 (en) 2016-01-22 2019-07-30 Micron Technology, Inc. Apparatuses and methods for encoding and decoding of signal lines for multi-level communication architectures
US10283187B2 (en) * 2017-07-19 2019-05-07 Micron Technology, Inc. Apparatuses and methods for providing additional drive to multilevel signals representing data
US11469669B2 (en) * 2020-01-31 2022-10-11 Texas Instruments Incorporated Methods and circuitry to detect PFM mode entry in wide duty range DC converter

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
IT1227430B (it) * 1988-07-22 1991-04-11 Sgs Thomson Microelectronics Circuito a pompa di carica a induttanza e capacita' per il pilotaggio di ponti a transistori mos di potenza.
IT1228509B (it) * 1988-10-28 1991-06-19 Sgs Thomson Microelectronics Dispositivo per generare una tensione di alimentazione flottante per un circuito bootstrap capacitivo
US5365118A (en) * 1992-06-04 1994-11-15 Linear Technology Corp. Circuit for driving two power mosfets in a half-bridge configuration
JP3330746B2 (ja) * 1994-09-09 2002-09-30 新日本製鐵株式会社 ブートストラップ回路

Also Published As

Publication number Publication date
DE69529331T2 (de) 2003-10-23
US5770967A (en) 1998-06-23
EP0725481A1 (de) 1996-08-07
JPH08288809A (ja) 1996-11-01
DE69529331D1 (de) 2003-02-13

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