EP0716561A1 - Appareil à rayons X comportant une unité pour l'alimentation en puissance d'un tube à rayons X - Google Patents

Appareil à rayons X comportant une unité pour l'alimentation en puissance d'un tube à rayons X Download PDF

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Publication number
EP0716561A1
EP0716561A1 EP95203284A EP95203284A EP0716561A1 EP 0716561 A1 EP0716561 A1 EP 0716561A1 EP 95203284 A EP95203284 A EP 95203284A EP 95203284 A EP95203284 A EP 95203284A EP 0716561 A1 EP0716561 A1 EP 0716561A1
Authority
EP
European Patent Office
Prior art keywords
inverters
voltage
primary
ray device
windings
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP95203284A
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German (de)
English (en)
Other versions
EP0716561B1 (fr
Inventor
Heinz Dr. Ing. Van Der Broeck
Christoph Loef
Hans Negle
Bernhard Wagner
Martin Wimmer
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Philips Intellectual Property and Standards GmbH
Koninklijke Philips NV
Original Assignee
Philips Corporate Intellectual Property GmbH
Philips Patentverwaltung GmbH
Koninklijke Philips Electronics NV
Philips Electronics NV
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Publication date
Application filed by Philips Corporate Intellectual Property GmbH, Philips Patentverwaltung GmbH, Koninklijke Philips Electronics NV, Philips Electronics NV filed Critical Philips Corporate Intellectual Property GmbH
Publication of EP0716561A1 publication Critical patent/EP0716561A1/fr
Application granted granted Critical
Publication of EP0716561B1 publication Critical patent/EP0716561B1/fr
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05G—X-RAY TECHNIQUE
    • H05G1/00—X-ray apparatus involving X-ray tubes; Circuits therefor
    • H05G1/08—Electrical details
    • H05G1/10—Power supply arrangements for feeding the X-ray tube
    • H05G1/20—Power supply arrangements for feeding the X-ray tube with high-frequency ac; with pulse trains

Definitions

  • the invention relates to an X-ray device with a power unit for feeding an X-ray tube, with a high-voltage transformer with two groups of primary and secondary windings located on the same transformer core, the primary windings from different groups having a weaker coupling to one another than the primary belonging to the same group - And secondary windings and the primary windings of the two groups are connected to two inverters operated at the same frequency.
  • Such an X-ray device is known from DE-OS 32 18 535.
  • X-ray tubes with a metal piston could also be fed symmetrically, in which the cathode current is greater than the anode current. This presupposes an asymmetrical power distribution between the two inverters, which would lead to disturbing compensating currents in the transformer if this were not prevented by the fact that windings from different groups are weakly coupled in the transformer compared to windings from the same group.
  • the known X-ray device allows the asymmetrical power distribution by delayed switching on of the switching elements from the two inverters.
  • the power is changed by changing the frequency with which the two Inverters are operated.
  • the power supplied must be able to be changed by several powers of ten, which requires a correspondingly large change in frequency.
  • the X-ray device is operated in the hearing frequency range, which leads to audible and disruptive operating noises and, moreover, results in an undesirably high ripple in the output voltage.
  • Another disadvantage is that when different voltages are set, the inverters are loaded by different switching currents, which results in a power restriction for this mode of operation.
  • the object of the present invention is to further improve an arrangement of the type mentioned at the outset.
  • This object is achieved in that means are provided for operating the inverters with a fixed frequency and independently controllable duty cycle.
  • the duty cycle is the ratio of the pulse duration of the voltage pulses supplied by the inverters to the primary windings to the period of the fixed frequency with which the inverters are switched. Operation with a fixed frequency has the advantage that this frequency can be chosen so that it lies above the hearing frequency range, so that no disturbing operating noises occur.
  • the power setting by changing the duty cycle has the advantage that there is a largely linear relationship between the output voltage (at the secondary windings) and the duty cycle at a working point with a constant current of the consumer, which is favorable for a higher-level control.
  • the compensating currents are reduced. With an unfavorable course of the voltage pulses, however, considerable compensating currents can still arise.
  • These compensating currents can be reduced in a further embodiment of the invention in that the means for operating the inverters are designed such that the voltage pulses generated by the two inverters overlap in time so that the shorter of the two voltage pulses occurs during the longer voltage pulse , and that the two voltage pulses in the transformer core cause the same temporal changes in the magnetic flux in the transformer core.
  • the duty cycle of the two inverters can still be controlled independently of one another, but the voltage pulses are synchronized to some extent. In principle, it would then be possible, for example, to let the leading edges of the two voltage pulses or the trailing edges coincide. However, equalizing currents can also occur here, which would result in the inverter generating the shorter pulse being loaded by a higher switching current than the other inverter, and a large reactive power would be exchanged between the inverters.
  • a preferred development of the invention provides that the means for operating the inverters are designed such that that the centers of the voltage pulses supplied by the two inverters coincide in time. In this case, the voltage pulses generated by the two inverters are symmetrical in time with one another. Voltage pulses of different lengths only result in a small exchange of reactive power between the two inverters, the switching currents in the two inverters having approximately the same maximum value.
  • each inverter comprises four switches 11 interconnected to form a full bridge in a manner known per se. . . 14 or 21. . . 24 of the IGBT type or other power semiconductors that can be switched off.
  • the connection point of the switches 11, 12 comprising a bridge branch is connected via the series connection of a capacitor 15 and a primary winding 16 of the transformer 3 belonging to a first winding group to the connection point of the switches 13, 14 of the other bridge branch.
  • connection point of the switches 21 and 22 is connected to the connection point of the switches 23 and 24 via the series connection of a capacitor 25 and a primary winding 26 of the transformer 3 belonging to a second winding group.
  • the secondary side of the transformer 3 is formed by two identically constructed secondary windings 31 and 32, which belong to the first and the second winding group.
  • the series resonance frequency of the circuits 15, 16 and 25, 26 is determined by the capacitance of the capacitor 15 and 25 and the leakage inductance of the identically constructed primary windings 16, 26 and the secondary windings 31, 32 of the transformer; in principle, an additional inductance is not required.
  • the winding capacitances 91, 92 of the secondary windings can be used as part of the series resonant circuit.
  • Switches 11 ... 14 and 21 ... 21 of inverters 1 and 2 are operated with the same, constant switching frequency that corresponds to the series resonance frequency.
  • a rectifier 6 or 7 is connected to the secondary windings 31 or 32, the output voltage of which is smoothed by a capacitor 61 or 71.
  • the two secondary windings are subdivided for insulation reasons, with each partial winding being given its own rectifier.
  • the rectifiers 6 and 7 are connected in series and the smoothed output voltage is supplied to the cathode or the anode of the X-ray tube 4. Due to the series connection the secondary windings 31 and 32, the rectifiers 6 and 7 and the capacitors 61 and 71 can only be designed for half the maximum value of the high voltage on the X-ray tube.
  • the x-ray tube 4 can have a grounded metal piston, as indicated schematically in the drawing.
  • part of the cathode current flows to the anode and another part flows to earth via the metal piston, so that the cathode current is greater than the anode current.
  • the cathode voltage would be lower than the anode voltage in a high-voltage generator in which the inverters would generate voltage pulses with an identical time profile. This would result in a low voltage between the anode and cathode, in particular, that the cathode current would be limited by space charge effects in the X-ray tube, so that its thermal load capacity for low anode voltages could no longer be fully utilized.
  • An operation is desirable in which, at least at high tube voltages, the voltage between the anode and earth is the same magnitude as the voltage between the cathode and earth.
  • the cathode voltage With a low tube voltage, it could even be expedient to make the cathode voltage greater than the anode voltage, so that the space charge effects mentioned could be avoided and the thermal load capacity of the X-ray tube could be better utilized.
  • the effect of the equalizing currents can be explained on the basis of the simplified equivalent circuit diagram according to FIG. 2, the transformer being replaced by the inductors L 12 , L 1s , L 2s and L h .
  • the inductors L 1s and L 2s represent the leakage inductance of the primary windings 16 and 26 with respect to the secondary side, and the inductance L 12 represents the leakage inductance between the two primary windings, by means of which the outputs of the inverters 1, 2 are coupled to one another.
  • L h is the main inductance, which is large compared to the aforementioned inductors.
  • the inductance L 12 would be small compared to the inductances L 1s , L 2s . If the voltages supplied by the inverters 1, 2 then differ in time due to different switching times for the switches 11 ... 14 on the one hand and 21 ... 24 on the other hand, the output voltage of the inverter 1 would initially be completely at the inductor L 12 apply and cause a differential current, the rate of change would correspond to the quotient of this voltage and the inductance L 12 .
  • the coupling of the two primary windings 16, 26 to one another is made smaller than the coupling between each of these primary windings and the secondary winding as a whole (ie the series connection between the windings 31 and 32) or between the relevant primary winding 16 or 26 and that belonging to the same winding group Partial winding 31 or 32.
  • This is achieved by the construction of the transformer shown schematically in FIG. 3.
  • the primary windings 16 and 26 are arranged side by side and at a distance from one another on a transformer core 30, e.g. a cutting tape core.
  • the primary windings 16 and 26 are enclosed by the secondary windings 31 and 32, respectively.
  • This design means that the magnetic or inductive coupling between the primary windings 16 and 26, but also between the secondary windings 31 and 32, is significantly weaker than the coupling between one of the primary windings (e.g. 16) and the secondary winding (31) surrounding it.
  • the leakage inductance between the two windings is proportional to the factor (1 - k 2 ).
  • L 12 is greater than L 1s or L 2s . If the coupling factor between the primary windings is 0.973, for example, and between a primary winding and the secondary winding is 0.993, then L 12 is approximately four times as large as L 1s and L 2s . Then only a reduced equalizing current flows, the frequency of which is generally not increased.
  • the coupling of the primary windings with one another and the secondary windings with one another can be reduced further by not arranging the primary windings with the secondary windings surrounding them on the same leg, but on opposite legs. However, this results in different dimensions of the transformer core.
  • the leading edges of the two voltage pulses or the trailing edges could coincide.
  • equalizing currents can also occur here, which would result in the inverter generating the shorter pulse being loaded by a higher switching current than the other inverter, and a large reactive power would be exchanged between the inverters. This can be avoided by a time-symmetrical course of the output voltages.
  • a suitable circuit results from FIG. 4.
  • the voltage between anode and earth is measured by a high-voltage measuring divider consisting of resistors 201 and 202, while the voltage between cathode and earth is measured by a high-voltage measuring divider consisting of resistors 101 and 102 .
  • the measuring voltages at the taps of the high-voltage measuring dividers are fed to a control arrangement 50, which compares the two measuring voltages, if necessary also their sum, with target values which depend on the predetermined target value of the voltage on the X-ray tube, but also on the control strategy.
  • the control circuit 50 supplies a first control signal for controlling a pulse width modulator 103 at a first output and a second control signal for controlling a pulse width modulator 203 at a second output
  • Pulse width modulators 103 and 203 deliver pulses with a fixed frequency and a duty cycle or a pulse duration, which depends on the control signal at the input of the relevant pulse width modulator. These pulses, which are temporally symmetrical to one another, are converted into a switching pulse pattern for the four switches 11 ... 14 or 21 ...
  • the pulse width modulators 103 and 203 are supplied with a symmetrical triangular voltage U d generated by a function generator 53.
  • the frequency of the delta voltage U d is twice as high as the series resonance frequency of the circuits 15, 16 and 25, 26 of the inverters 1 and 2.
  • the function generator 53 also delivers Clock signals for the blocks 104 and 204, as indicated by dashed lines in FIG. 4.
  • the pulse width modulators 103 and 203 the triangular voltage U d with the -.
  • control signals S 1 and S 2 are compared, and the output of the pulse width modulators pulses PWM 1 and PWM 2 are produced, the leading edge of the Crossing and whose trailing edge coincides with the falling below the control signals S 1 or S 2 by the delta voltage U d .
  • inverter voltages U 1 and U 2 After converting the pulse width modulated pulses PWM 1 and PWM 2 into switching pulses for the switches 11 ... 14 and 21 ... 24 of the inverters 1 ... 2, inverter voltages U 1 and U 2 with the one shown in FIG. 5 result pulse-shaped time course (U 1 and U 2 each represent the voltage at the series circuit 15, 16 and 25, 26).
  • U 1 and U 2 differ from PWM 1 and PWM 2 in that the polarity of every second pulse is inverted, so that the fundamental oscillation contained in the output voltages U 1 and U 2 has a frequency which is half as large as that Frequency of the triangular wave U d . Since the frequency of the triangular oscillation is twice as large as the series resonance frequency of the inverters 1, 2, the frequency of this fundamental oscillation corresponds to the series resonance frequency. It can be seen from FIG. 5 that the voltage pulses U 1 and U 2 are symmetrical in time with respect to one another, ie the time centers of these pulses coincide. The voltage pulses from U 1 and U 2 each have the same polarity - if the primary windings 16 and 26 have the same winding sense. If the primary windings 16 and 26 have the opposite direction of winding, the pulses must each have the opposite polarity.
  • the compensation currents are minimal and only a small reactive power is exchanged between the windings.
  • the currents I 1 and I 2 flowing in the primary windings 16 and 26 have almost the same maximum value, ie the current load in the switches 11 ... 14 is approximately the same as in FIG the switches 21 ... 24, although the duty cycle of U 1 is approximately twice as high as the duty cycle of U 2 , so that the cathode voltage derived from U 1 is also approximately twice as large as the anode voltage derived from U 2 .
  • the cathode voltage or the anode voltage largely depend on an operating point with a constant tube current linearly from the duty cycle or the pulse duration of the pulse width modulated signals PWM 1 and PWM 2 .
  • the linear dependence of the high voltage on the duty cycle is favorable for the control behavior.
  • the pulse width modulators 103 and 203 are explained as circuits with an analog effect. However, it is also possible to carry out the pulse width modulation - and possibly also the switching pulse generation by the blocks 104 and 204 - with the aid of programmable controller blocks.
  • the invention has been explained above using the example of an X-ray device or X-ray generator. However, it can also be used in other arrangements for supplying power to a consumer, which are concerned with controlling the voltage at the consumer in a specifiable manner.

Landscapes

  • X-Ray Techniques (AREA)
  • Dc-Dc Converters (AREA)
  • Inverter Devices (AREA)
EP95203284A 1994-12-07 1995-11-29 Appareil à rayons X comportant une unité pour l'alimentation en puissance d'un tube à rayons X Expired - Lifetime EP0716561B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE4443551 1994-12-07
DE4443551A DE4443551A1 (de) 1994-12-07 1994-12-07 Anordnung zur Leistungsversorgung eines elektrischen Verbrauchers, insbesondere Röntgen-Apparat

Publications (2)

Publication Number Publication Date
EP0716561A1 true EP0716561A1 (fr) 1996-06-12
EP0716561B1 EP0716561B1 (fr) 2004-02-18

Family

ID=6535157

Family Applications (1)

Application Number Title Priority Date Filing Date
EP95203284A Expired - Lifetime EP0716561B1 (fr) 1994-12-07 1995-11-29 Appareil à rayons X comportant une unité pour l'alimentation en puissance d'un tube à rayons X

Country Status (4)

Country Link
US (1) US5731968A (fr)
EP (1) EP0716561B1 (fr)
JP (1) JP3683318B2 (fr)
DE (2) DE4443551A1 (fr)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2002097957A2 (fr) * 2001-05-29 2002-12-05 Koninklijke Philips Electronics N.V. Systeme d'alimentation electrique

Families Citing this family (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE19724931A1 (de) * 1997-06-12 1998-12-17 Philips Patentverwaltung Leistungsversorgungseinheit mit einem pulsdauermodulierten Wechselrichter, insbesondere für einen Röntgengenerator
DE19940137A1 (de) * 1999-08-24 2001-03-01 Philips Corp Intellectual Pty Serienresonanter Konverter mit einer Regelschaltung
US6178098B1 (en) * 1999-09-22 2001-01-23 Lucent Technologies Inc. Phase-shifted post-regulator, method of operation thereof and power converter employing the same
US6738275B1 (en) 1999-11-10 2004-05-18 Electromed Internationale Ltee. High-voltage x-ray generator
DE10159897A1 (de) * 2001-12-06 2003-06-26 Philips Intellectual Property Spannungsversorgung für Röntgengenerator
JP4306209B2 (ja) * 2002-09-09 2009-07-29 株式会社日立メディコ 中性点接地方式のｘ線発生装置及びこれを用いたｘ線ｃｔ装置
JP4392746B2 (ja) * 2003-05-23 2010-01-06 株式会社日立メディコ Ｘ線高電圧装置
KR101254550B1 (ko) * 2005-04-22 2013-04-19 가부시키가이샤 다이후쿠 무접촉 급전 설비의 2차측 수전 회로 장치
DE102007032199A1 (de) * 2007-07-11 2009-01-15 Sms Elotherm Gmbh Betreiben von Schwingkreis-Wechselrichtern
WO2009147574A1 (fr) * 2008-06-02 2009-12-10 Philips Intellectual Property & Standards Gmbh Transformateur de puissance tournant destiné à être utilisé dans un circuit de génération de haute-tension afin de transmettre par induction au moins deux tensions d'alimentation pouvant être commandées de façon indépendante aux bornes d'alimentation d'une charge
US8861681B2 (en) * 2010-12-17 2014-10-14 General Electric Company Method and system for active resonant voltage switching
US10305385B2 (en) * 2016-09-27 2019-05-28 Texas Instruments Incorporated Interleaved resonant converter
US11103207B1 (en) * 2017-12-28 2021-08-31 Radiation Monitorng Devices, Inc. Double-pulsed X-ray source and applications
JP2022134597A (ja) * 2021-03-03 2022-09-15 富士フイルム株式会社 放射線管及び放射線源

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GB2100480A (en) * 1981-06-12 1982-12-22 Gen Equip Med Sa Semiconductor voltage regulator circuit
FR2527035A1 (fr) * 1982-05-17 1983-11-18 Philips Nv Generateur de haute tension, destine en particulier a alimenter un tube de rontgen
EP0180750A1 (fr) * 1984-10-09 1986-05-14 Siemens Aktiengesellschaft Générateur de rayons X fonctionnant à moyenne fréquence
EP0315336A2 (fr) * 1987-11-05 1989-05-10 Picker International, Inc. Circuits de commande pour tubes radiographiques
EP0347322A1 (fr) * 1988-06-17 1989-12-20 General Electric Cgr S.A. Alimentation stabilisée à taux d'ondulation réduit
EP0496679A2 (fr) * 1991-01-25 1992-07-29 General Electric Cgr S.A. Dispositif pour obtenir une tension continue à faible ondulation résiduelle
US5272612A (en) * 1989-06-30 1993-12-21 Kabushiki Kaisha Toshiba X-ray power supply utilizing A.C. frequency conversion to generate a high D.C. voltage

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US4504895A (en) * 1982-11-03 1985-03-12 General Electric Company Regulated dc-dc converter using a resonating transformer
US4574340A (en) * 1984-06-22 1986-03-04 Westinghouse Electric Corp. Inverter with constant voltage to frequency ratio output capability
US4797908A (en) * 1984-09-14 1989-01-10 Kabushiki Kaisha Toshiba Voltage-resonance type power supply circuit for X-ray tube
JPS61158698A (ja) * 1984-12-28 1986-07-18 Hitachi Medical Corp インバ−タ式ｘ線装置
DE3929888A1 (de) * 1989-09-08 1991-03-14 Philips Patentverwaltung Roentgengenerator zum betrieb einer roentgenroehre mit an masse angeschlossenen roehrenteilen
DE59003559D1 (de) * 1990-11-27 1993-12-23 Siemens Ag Hochfrequenz-Röntgengenerator.
US5602897A (en) * 1995-06-29 1997-02-11 Picker International, Inc. High-voltage power supply for x-ray tubes

Patent Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2100480A (en) * 1981-06-12 1982-12-22 Gen Equip Med Sa Semiconductor voltage regulator circuit
FR2527035A1 (fr) * 1982-05-17 1983-11-18 Philips Nv Generateur de haute tension, destine en particulier a alimenter un tube de rontgen
EP0180750A1 (fr) * 1984-10-09 1986-05-14 Siemens Aktiengesellschaft Générateur de rayons X fonctionnant à moyenne fréquence
EP0315336A2 (fr) * 1987-11-05 1989-05-10 Picker International, Inc. Circuits de commande pour tubes radiographiques
EP0347322A1 (fr) * 1988-06-17 1989-12-20 General Electric Cgr S.A. Alimentation stabilisée à taux d'ondulation réduit
US5272612A (en) * 1989-06-30 1993-12-21 Kabushiki Kaisha Toshiba X-ray power supply utilizing A.C. frequency conversion to generate a high D.C. voltage
EP0496679A2 (fr) * 1991-01-25 1992-07-29 General Electric Cgr S.A. Dispositif pour obtenir une tension continue à faible ondulation résiduelle

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2002097957A2 (fr) * 2001-05-29 2002-12-05 Koninklijke Philips Electronics N.V. Systeme d'alimentation electrique
WO2002097957A3 (fr) * 2001-05-29 2003-04-17 Koninkl Philips Electronics Nv Systeme d'alimentation electrique

Also Published As

Publication number Publication date
EP0716561B1 (fr) 2004-02-18
JPH08255694A (ja) 1996-10-01
US5731968A (en) 1998-03-24
DE4443551A1 (de) 1996-06-20
JP3683318B2 (ja) 2005-08-17
DE59510860D1 (de) 2004-03-25

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