EP0633621B1 - Antenna-filter-combiner - Google Patents
Antenna-filter-combiner Download PDFInfo
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- EP0633621B1 EP0633621B1 EP94110380A EP94110380A EP0633621B1 EP 0633621 B1 EP0633621 B1 EP 0633621B1 EP 94110380 A EP94110380 A EP 94110380A EP 94110380 A EP94110380 A EP 94110380A EP 0633621 B1 EP0633621 B1 EP 0633621B1
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- European Patent Office
- Prior art keywords
- accordance
- antenna
- waveguide
- filters
- filter combiner
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/213—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies
- H01P1/2138—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies using hollow waveguide filters
Definitions
- the invention relates to an antenna filter combiner for connecting a variety of frequency channels a transmitting antenna.
- the base stations of mobile radio systems must be very narrow-band and high-powered frequency channels reactively interconnected and the transmitting antenna be fed.
- the number of frequency channels generally according to the respective expansion stage be modularly expandable and on the other hand every transmission filter on any agreed without loss of quality during operation Channel frequency can be changed at short notice.
- Waveguide branching points such as those made of the essay “Computer-Aided Design of Waveguide Multiplexers” by A.E. Atia, published in “IEEE Transactions on Microwave Theory and Techniques ", March 1974, pages 332 to 336 are known to have been used in satellite and microwave technology proven.
- the partial filters are sent to an am End short-circuited waveguide coupled, however the distances between the coupling levels of the filters from whose frequency positions depend, thus electrically significant and with the filter retuning in the switch as well would have to assume other values.
- the waveguide dimensions for those currently located at 0.9 GHz and 1.8 GHz Mobile radio systems are relatively large and compact Do not allow switch setup.
- the duct switch chains used especially in directional radio technology with circulators such as those from the Essay "Channel Branching Filters for Wideband Radio Relay Systems "by G. Ensslin, H. Herder, R. Schuster in telcom-report 10 (1987), special "Radio Communication", Pages 146 to 151 are known, offer good options of the modular structure.
- An arrangement is also from EP 0 262 391 A2 with several circulators for switching on one each Sender / receiver pairs known.
- the invention has for its object for an antenna filter combiner of the type described at the beginning Solution for a simple setup with low loss transmission filters specify.
- Figure 1 shows a modular antenna filter combiner for a retroactive combination of maximum n ⁇ m transmit frequency channels in the block diagram.
- the direction of signal flow the circulators Z is used so that in the course of Waveguide W1 on local circulators 1 ... ( ⁇ -1) already fed frequency channels at the crossover of the ⁇ .circulator at least approximately totally reflected and possibly with additional crossovers wired circulators ( ⁇ + 1) ... n in the direction of the antenna Ant can be forwarded.
- the waveguide W1 is at its end in front of the first circulator Z1 the resistor R is properly terminated.
- the ⁇ > 2 sub-filters TF of each crossover FW are more advantageous High Q resonators, e.g. Coaxial resonators, helix resonators, hollow tube resonators, dielectric resonators, HTSL resonators. If available the resonators can meet the physical requirements operate with two or more modes, e.g. orthogonal Modes in the hollow tube or dielectric resonator.
- High Q resonators e.g. Coaxial resonators, helix resonators, hollow tube resonators, dielectric resonators, HTSL resonators.
- the ⁇ partial filter TF are concentric and, based on the Resonator axes, parallel to the axis of the apex of the Crossover forming second waveguide W2 arranged.
- the other end of the second waveguide W2 is as Connector prepared or designed so that an immediate, optimally short connection with the third gate one in the first waveguide W1 circulator Z is possible.
- the second waveguide W2 consists of one modified coaxial line. A more detailed constructive The arrangement is shown in FIGS. 6 and 7 shown and will be discussed later in connection with this description of the figures explained in more detail.
- two partial filters TF1, TF2 are provided, which in one case run with their central axes in one plane with the inner conductor of the central coaxial line arranged between them (second waveguide W2), while in the other case the second waveguide W2 is arranged symmetrically to the two sub-filters outside the plane mentioned.
- the radius of the filter resonators is r
- the radius of the outer conductor of the second waveguide is r K.
- the resonators In the area directly opposite the second waveguide W2, the resonators have a filter coupling FA.
- the electrically effective length from the filter coupling FA to the inner conductor of the second waveguide (crossover vertex WS) is designated by x.
- x 2 r K + s, where s is the material thickness between the filter resonator and the second waveguide W2.
- the filter couplings are not shown in the illustrations in FIGS. 2 to 5.
- Figures 6 and 7 show a three-channel crossover in the antenna filter combiner in two sectional views. This represents a particularly favorable solution in terms of Economics and the electrically critical length of the Filter outputs to the switch crest.
- the 3-channel crossovers are implemented in such a way that in a metal block or a metallized plastic block, three blind bores as resonator housing 1 are circumferentially symmetrical to a continuous central bore 3, which represents the outer conductor of a coaxial line forming the second waveguide, in such a way that the minimum wall thickness between the resonators each assumes a small, mechanically expedient value.
- the dielectric resonators DR1, DR2, DR3 are each fixed centrally on thin-walled tube sections 5 made of a suitable microwave insulation material.
- the conductors of the filter decouplings A1, A2, A3 run insulated through bores in the wall between the resonator housing 1 and the central bore 3 and form the physical apex of the crossover at the connection point WS with the inner conductor 4 of the central coaxial line.
- the filter couplings E1, E2, E3 are offset by 90 ° relative to the couplings on the circumference of the resonator housing.
- Asymmetry screws K1, K2, K3 are arranged at 135 ° to the filter coupling and decoupling, with which the bandwidth of the filter is set.
- the central coaxial line has at one end a connection 6 for a circulator with the channels SK1, 2, 3, while on the other side as a residual error compensation at the apex WS (connection point of the filter output lines and the inner conductor of the coaxial line) one shorted at the end without additional space requirement Coaxial line is continued.
- the inner conductor 7 is designed to avoid temperature-related mechanical stresses at the end as a slightly bent wire 8 and connected to a cover 9 covering the entire switch unit, for example by clamping.
- the two-circuit sub- filters of the crossover implemented in this case with dielectric resonators DR are operated with orthogonal HE 11 ⁇ modes.
- the respective blocking filter over the Connection lines between the filter outputs and the second one Waveguide (switch vertex) largely balanced.
- the manufacture of the housing brings electrical advantages Switch arrangement from a single metal block or metallized Plastic block through short and defined connection paths and a minimal number of connection points. Mechanical advantages are a compact and space-saving Construction, the accommodation of the compensation means without additional space requirements and in defined and low tolerance connections.
- the one operated with orthogonal modes dielectric resonator as a highly selective dual circuit filter is particularly advantageous from a high point of view Quality and climate requirements, the desired compactness and the excellent economy in the crossovers current mobile radio systems.
- any sub-filter of the filter combiner to all agreed channel frequencies within the system frequency band is without impermissible Deformation of the filter properties (e.g. by serious Loss of quality or the occurrence of fault modes) achieved that the dielectric resonator DR by two Resonators about half the thickness (in the axial direction) and about is replaced with the same external dimensions, whereby defines at least one of the two resonator halves, e.g. by means of a system-controlled stepper motor, in axial Movable direction and the strength of the Air gap 10 between the two resonator halves ultimately the Center frequency of the two-circuit filter determined.
- This Movability is shown in Figure 6 by the two-way arrow indicated.
Description
Die Erfindung bezieht sich auf einen Antennen-Filter-Combiner zur Anschaltung einer Vielzahl von Frequenzkanälen an eine Sendeantenne.The invention relates to an antenna filter combiner for connecting a variety of frequency channels a transmitting antenna.
In den Basisstationen von Mobilfunksystemen müssen sehr schmalbandige und mit großer Leistung beaufschlagte Frequenzkanäle rückwirkungsfrei zusammengeschaltet und der Sendeantenne zugeführt werden. Dabei soll die Anzahl der Frequenzkanäle der jeweiligen Ausbaustufe entsprechend generell modular erweiterbar sein und andererseits jedes Sendefilter ohne Qualitätseinbuße während des Betriebs auf jede vereinbarte Kanalfrequenz kurzfristig umstimmbar sein.In the base stations of mobile radio systems must be very narrow-band and high-powered frequency channels reactively interconnected and the transmitting antenna be fed. The number of frequency channels generally according to the respective expansion stage be modularly expandable and on the other hand every transmission filter on any agreed without loss of quality during operation Channel frequency can be changed at short notice.
Wegen der Frequenz lagen aktueller Mobilfunksysteme im GHz-Bereich und wegen der sehr geringen Kanalbandbreiten sind für die Realisierung von verlustarmen Sendefiltern High-Q-Resonatoren als besonders günstig anzusehen. Deren räumliche Ausdehnung läßt jedoch die im Sinne einer Frequenzweiche erwünschte, elektrisch ideale Zusammenschaltung der Sendefilter unmittelbar und punktförmig an deren Ausgängen nur mit zum Teil erheblichen Störungen zu.Because of the frequency, current mobile radio systems were in the GHz range and because of the very small channel bandwidths are for the implementation of low-loss transmission filters High-Q resonators can be regarded as particularly cheap. Their spatial expansion leaves however in the sense of a crossover Desired, electrically ideal interconnection the transmission filter directly and punctiform at their outputs only with some significant disruptions.
Bekannte Lösungen für Frequenzweichen im Mikrowellenfrequenzbereich lösen aus jeweils verschiedenen Gründen das aufgezeigte Problem nicht optimal. So wird beispielsweise in dem Artikel "Base Station Multicoupler Design for UK Cellular Radio Systems" von S. Kazeminejad, D. Howson, G. Hamer, erschienen in "Electronic Letters", 16. Juli 1987, Vol. 23, Nr. 15, Seite 812 vorgeschlagen, die Anschaltepunkte von zwei Sendefiltern an die Antennenleitung im Abstand von einer halben Wellenlänge vorzusehen. Dieser Abstand ist fix und hängt von der Frequenzlage der Filter ab. Er müßte sich in einer nicht realisierbaren Weise bei der Umstimmung der Filter entsprechend ändern. Bei der Zusammenschaltung von mehreren Sendefiltern in diesem Sinne ist die eindeutige Funktion der Frequenzweiche deshalb nicht gewährleistet. Darüberhinaus ist der Aufbau sperrig und eine modulare Erweiterbarkeit fraglich.Known solutions for crossovers in the microwave frequency range solve that for different reasons problem shown is not optimal. For example, in the article "Base Station Multicoupler Design for UK Cellular Radio Systems "by S. Kazeminejad, D. Howson, G. Hamer, published in "Electronic Letters", July 16, 1987, vol. 23, No. 15, page 812 suggested the connection points of two transmit filters to the antenna line at a distance of half a wavelength. This distance is fixed and depends on the frequency of the filters. He would have to in an unrealizable way in retuning the Change the filter accordingly. When interconnecting several transmission filters in this sense is the unique one Crossover function therefore not guaranteed. In addition, the structure is bulky and modular expandability questionable.
Hohlleiter-Verzweigungsweichen, wie sie beispielsweise aus dem Aufsatz "Computer-Aided Design of Waveguide Multiplexers" von A.E. Atia, erschienen in "IEEE Transactions on Microwave Theory and Techniques", März 1974, Seiten 332 bis 336 bekannt sind, haben sich in der Satelliten- und Richtfunktechnik bewährt. Dabei werden die Teilfilter an einen am Ende kurzgeschlossenen Hohlleiter angekoppelt, wobei jedoch die Abstände zwischen den Ankoppelebenen der Filter von deren Frequenzlagen abhängen, somit elektrisch signifikant sind und bei der Filterumstimmung in der Weiche ebenfalls andere Werte annehmen müßten. Hinzu kommt, daß die Hohlleiterabmessungen für die aktuell bei 0,9 GHz und 1,8 GHz angesiedelten Mobilfunksysteme relativ groß sind und einen kompakten Weichenaufbau nicht zulassen.Waveguide branching points, such as those made of the essay "Computer-Aided Design of Waveguide Multiplexers" by A.E. Atia, published in "IEEE Transactions on Microwave Theory and Techniques ", March 1974, pages 332 to 336 are known to have been used in satellite and microwave technology proven. The partial filters are sent to an am End short-circuited waveguide coupled, however the distances between the coupling levels of the filters from whose frequency positions depend, thus electrically significant and with the filter retuning in the switch as well would have to assume other values. In addition, the waveguide dimensions for those currently located at 0.9 GHz and 1.8 GHz Mobile radio systems are relatively large and compact Do not allow switch setup.
Die besonders in der Richtfunktechnik eingesetzten Kanalweichenketten mit Zirkulatoren, wie sie beispielsweise aus dem Aufsatz "Channel Branching Filters for Wideband Radio Relay Systems" von G. Ensslin, H. Herder, R. Schuster, erschienen in telcom-report 10(1987), Special "Radio Communication", Seiten 146 bis 151 bekannt sind, bieten gute Möglichkeiten des modularen Aufbaus. Auch aus EP 0 262 391 A2 ist eine Anordnung mit mehreren Zirkulatoren zum Anschalten je eines Sender/Empfängerpaars bekannt. Wegen der relativ großen Anzahl von Zirkulatoren - jedem einzelnen Filter ist dabei ein Zirkulator zuzuordnen - ergeben sich einerseits für jeden einzelnen Frequenzkanal entsprechend der mechanischen Anordnung in der Kanalweichenkette viele Zirkulatordurchläufe und damit hohe Dämpfungen, und andererseits hohe Kosten für die Zirkulatoren, so daß auch diese Lösung nicht als optimal für Mobilfunkzwecke angesehen werden kann. Weiterhin ist aus FR-A-1 158 914 ein Filter zum Verbinden mehrerer Sendekanäle mit einer gemeinsamen Antenne bekannt.The duct switch chains used especially in directional radio technology with circulators, such as those from the Essay "Channel Branching Filters for Wideband Radio Relay Systems "by G. Ensslin, H. Herder, R. Schuster in telcom-report 10 (1987), special "Radio Communication", Pages 146 to 151 are known, offer good options of the modular structure. An arrangement is also from EP 0 262 391 A2 with several circulators for switching on one each Sender / receiver pairs known. Because of the relatively large number of circulators - every single filter is one Assign circulator - arise on the one hand for everyone individual frequency channel according to the mechanical arrangement many circulator passes and thus high damping, and on the other hand high costs for the Circulators, so this solution is not considered optimal for Cellular purposes can be viewed. Furthermore from FR-A-1 158 914 a filter for connecting several transmission channels known with a common antenna.
Der Erfindung liegt die Aufgabe zugrunde, für einen Antennen-Filter-Combiner der eingangs beschriebenen Art eine Lösung für einen einfachen Aufbau mit verlustarmen Sendefiltern anzugeben.The invention has for its object for an antenna filter combiner of the type described at the beginning Solution for a simple setup with low loss transmission filters specify.
Diese Aufgabe wird gemäß der Erfindung gelöst durch n in
eine zur Antenne führende Wellenleitung geschaltete Zirkulatoren,
in deren jeweils drittes Tor über eine aus µ<=m zusammengeschalteten
Teilfiltern bestehende Frequenzweiche
jeweils µ Sendekanäle eingespeist werden und die Signalflußrichtung
der Zirkulatoren so ausgenutzt wird, daß die im
Zuge der Wellenleitung an örtlich vorausliegenden Zirkulatoren
1...(β-1) bereits eingespeisten Frequenzkanäle an der
Frequenzweiche des β.Zirkulators wenigstens näherungsweise
total reflektiert und über eventuell weitere mit Frequenzweichen
beschaltete Zirkulatoren (β+1)...n in Richtung auf
die Antenne weitergeleitet werden. This object is achieved according to the invention by n in
a circulator connected to the antenna,
in their third port via an interconnected µ <= m
Partial filters existing crossover
µ transmission channels are fed and the signal flow direction
the circulators is used in such a way that the
In the course of the waveguide at
Vorteilhafte Ausgestaltungen und Weiterbildungen des Erfindungsgegenstandes sind in den Unteransprüchen angegeben. Advantageous refinements and developments of the subject matter of the invention are specified in the subclaims.
Nachstehend wird die Erfindung anhand von in der Zeichnung dargestellten Ausführungsbeispielen näher erläutert.The invention based on in the drawing illustrated embodiments explained in more detail.
Es zeigen:
Figur 1- einen Antennen-Filter-Combiner im Blockschaltbild,
Figuren 2 bis 5- verschiedene Varianten der Anordnung von Teilfiltern in einer Frequenzweiche und
- Figuren 6 und 7
- in zwei Schnittdarstellungen den konstruktiven Aufbau einer dreikanaligen Frequenzweiche.
- Figure 1
- an antenna filter combiner in the block diagram,
- Figures 2 to 5
- different variants of the arrangement of partial filters in a crossover and
- Figures 6 and 7
- in two sectional views the construction of a three-channel crossover.
Figur 1 zeigt einen modular aufbaubaren Antennen-Filter-Combiner
zur rückwirkungsfreien Kombination von maximal
n · m Sende-Frequenzkanälen im Blockschaltbild. Dabei sind in
eine Wellenleitung W1, die vorzugsweise aus einer Koaxialleitung
besteht, n Zirkulatoren Z1, Z2...Zn geschaltet, in
deren jeweils drittes Tor über eine aus µ<=m zusammengeschalteten
Teilfiltern TF bestehende Frequenzweiche FW (für
Zirkulator Z2 strichpunktiert umrandet gezeichnet) jeweils µ
Sendekanäle SK eingespeist werden. Die Signalflußrichtung
der Zirkulatoren Z wird so ausgenutzt, daß die im Zuge der
Wellenleitung W1 an örtlich vorausliegenden Zirkulatoren
1...(β-1) bereits eingespeisten Frequenzkanäle an der Frequenzweiche
des β.Zirkulators wenigstens näherungsweise
total reflektiert und über eventuell weitere mit Frequenzweichen
beschaltete Zirkulatoren (β+1)...n in Richtung auf
die Antenne Ant weitergeleitet werden. Die Wellenleitung W1
ist an ihrem vor dem ersten Zirkulator Z1 liegenden Ende mit
dem Widerstand R wellenwiderstandsrichtig abgeschlossen.Figure 1 shows a modular antenna filter combiner
for a retroactive combination of maximum
n · m transmit frequency channels in the block diagram. Here are in
a waveguide W1, which preferably consists of a coaxial line
exists, n circulators Z1, Z2 ... Zn switched, in
the third gate of which is interconnected from µ <= m
Partial filters TF existing crossover FW (for
Circulator Z2 drawn with dash-dotted lines) each µ
Transmission channels SK can be fed. The direction of signal flow
the circulators Z is used so that in the course of
Waveguide W1 on
Die µ>=2 Teilfilter TF jeder Frequenzweiche FW sind in vorteilhafter Weise aus High-Q-Resonatoren aufgebaut, z.B. Koaxial-Resonatoren, Helix-Resonatoren, Hohlrohr-Resonatoren, dielektrische Resonatoren, HTSL-Resonatoren. Bei Vorliegen der physikalischen Voraussetzungen können die Resonatoren mit zwei oder mehr Moden betrieben werden, z.B. orthogonale Moden im Hohlrohr- bzw. dielektrischen Resonator.The µ> = 2 sub-filters TF of each crossover FW are more advantageous High Q resonators, e.g. Coaxial resonators, helix resonators, hollow tube resonators, dielectric resonators, HTSL resonators. If available the resonators can meet the physical requirements operate with two or more modes, e.g. orthogonal Modes in the hollow tube or dielectric resonator.
Die µ Teilfilter TF sind konzentrisch und, bezogen auf die Resonatorachsen, achsenparallel um eine den Scheitel der Frequenzweiche bildende zweite Wellenleitung W2 angeordnet. Die Figuren 2 bis 5 zeigen in schematischer Darstellung verschiedene Anordnungen mit unterschiedlich großer Anzahl von Teilfiltern (m=2...4). Diese Anordnung der Teilfilter geschieht mit dem Zweck, die Filterausgänge auf dem elektrisch kürzesten Weg - und damit störungsarm und im Sinne einer Mittenfrequenzumstimmung der Filter weitestgehend frequenzunabhängig - dieser zweiten Wellenleitung W2 zuzuführen. Das andere Ende der zweiten Wellenleitung W2 ist als Connector so vorbereitet oder ausgestaltet, daB eine unmittelbare, optimal kurze Verbindung mit dem dritten Tor eines in die erste Wellenleitung W1 geschalteten Zirkulators Z möglich ist. Die zweite Wellenleitung W2 besteht aus einer modifizierten Koaxialleitung. Eine detailliertere konstruktive Ausführung der Anordnung ist in den Figuren 6 und 7 dargestellt und wird an späterer Stelle im Zusammenhang mit dieser Figurenbeschreibung näher erläutert. The µ partial filter TF are concentric and, based on the Resonator axes, parallel to the axis of the apex of the Crossover forming second waveguide W2 arranged. Figures 2 to 5 show various schematic representations Arrangements with different numbers of Partial filters (m = 2 ... 4). This arrangement of the sub-filters happens with the purpose of the filter outputs on the electrical shortest route - and therefore with little interference and in the sense of Center frequency tuning of the filters largely independent of frequency - To feed this second waveguide W2. The other end of the second waveguide W2 is as Connector prepared or designed so that an immediate, optimally short connection with the third gate one in the first waveguide W1 circulator Z is possible. The second waveguide W2 consists of one modified coaxial line. A more detailed constructive The arrangement is shown in FIGS. 6 and 7 shown and will be discussed later in connection with this description of the figures explained in more detail.
Die Figuren 2 bis 5 zeigen verschiedene Varianten der Anordnung von Teilfiltern in einer Frequenzweiche mit m=2,3,4 Teilfiltern. Bei den Ausführungsformen nach Figur 2 und 3 sind zwei Teilfilter TF1, TF2 vorgesehen, die im einen Fall mit ihren Mittelachsen in einer Ebene verlaufen mit dem Innenleiter der zwischen ihnen angeordneten zentralen Koaxialleitung (zweite Wellenleitung W2), während im anderen Fall der zweite Wellenleiter W2 außerhalb der genannten Ebene symmetrisch zu den beiden Teilfiltern angeordnet ist. Der Radius der Filter-Resonatoren beträgt r, der Radius des Außenleiters der zweiten Wellenleitung ist rK. In dem dem zweiten Wellenleiter W2 unmittelbar gegenüberliegenden Bereich weisen die Resonatoren eine Filterauskopplung FA auf. Die elektrisch wirksame Länge von der Filterauskopplung FA bis zum Innenleiter der zweiten Wellenleitung (Weichenscheitel WS) ist mit x bezeichnet. Für die Frequenzweichen mit zwei Filtern beträgt x2=rK+s, wobei mit s die Materialstärke zwischen Filter-Resonator und zweiter Wellenleitung W2 bezeichnet ist. Die Filtereinkopplungen sind in den Darstellungen der Figuren 2 bis 5 nicht eingezeichnet.Figures 2 to 5 show different variants of the arrangement of sub-filters in a crossover network with m = 2,3,4 sub-filters. In the embodiments according to FIGS. 2 and 3, two partial filters TF1, TF2 are provided, which in one case run with their central axes in one plane with the inner conductor of the central coaxial line arranged between them (second waveguide W2), while in the other case the second waveguide W2 is arranged symmetrically to the two sub-filters outside the plane mentioned. The radius of the filter resonators is r, the radius of the outer conductor of the second waveguide is r K. In the area directly opposite the second waveguide W2, the resonators have a filter coupling FA. The electrically effective length from the filter coupling FA to the inner conductor of the second waveguide (crossover vertex WS) is designated by x. For the crossovers with two filters, x 2 = r K + s, where s is the material thickness between the filter resonator and the second waveguide W2. The filter couplings are not shown in the illustrations in FIGS. 2 to 5.
Bei den Figuren 4 und 5 sind m=3 bzw. m=4 Teilfilter in
gleichmäßiger zirkularer Verteilung um den zweiten Wellenleiter
W2 angeordnet. Dies bedeutet, daß die Filter um 120°
bzw. 90° zueinander versetzt angeordnet sind, wenn sich der
zweite Wellenleiter W2 mittig unter jeweils gleichen Abständen
zwischen den Teilfilter befindet. Für die elektrisch
wirksame Länge von der Filterauskopplung bis zum Innenleiter
der zentralen zweiten Wellenleitung W2 gilt allgemein die
Gleichung
Die Figuren 6 und 7 zeigen eine dreikanalige Frequenzweiche im Antennen-Filter-Combiner in zwei Schnittdarstellung. Diese stellt eine besonders günstige Lösung hinsichtlich Wirtschaftlichkeit und der elektrisch kritischen Länge der Filterausgänge zum Weichenscheitel dar.Figures 6 and 7 show a three-channel crossover in the antenna filter combiner in two sectional views. This represents a particularly favorable solution in terms of Economics and the electrically critical length of the Filter outputs to the switch crest.
Die Realisierung der 3-Kanal-Frequenzweichen erfolgt in der
Weise, daß in einem Metallblock bzw. einem metallisierten
Kunststoffblock drei Sackbohrungen als Resonatorgehäuse 1
umfangsymmetrisch zu einer durchgehenden Zentralbohrung 3,
die den AuBenleiter einer die zweite Wellenleitung bildenden
Koaxialleitung darstellt, so vorgesehen sind, daß die minimale
Wandstärke zwischen den Resonatoren jeweils einen kleinen,
mechanisch zweckmäßigen Wert annimmt. In den großen
Resonatorgehäusebohrungen 2 sind jeweils zentrisch auf
dünnwandigen Rohrabschnitten 5 aus einem geeigneten Mikrowellen-Isolationsstoff
die dielektrischen Resonatoren DR1,
DR2, DR3 fixiert. Die Leiter der Filterauskopplungen A1, A2,
A3 verlaufen isoliert durch Bohrungen in der Wand zwischen
Resonatorgehäuse 1 und Zentralbohrung 3 und bilden im Vereinigungspunkt
WS mit dem Innenleiter 4 der zentralen Koaxialleitung
den physikalischen Scheitel der Frequenzweiche.
Die Filtereinkopplungen E1, E2, E3 sind relativ zu den Auskopplungen
um 90° auf dem Umfang des Resonatorgehäuses
versetzt. Jeweils 135° zu den Filterein- und -auskopplungen
orientiert sind Unsymmetrieschrauben K1, K2, K3 angeordnet,
mit denen die Bandbreite der Filter eingestellt wird. Die
zentrale Koaxialleitung weist an einem Ende einen Anschluß 6
für einen Zirkulator mit den Kanälen SK1, 2, 3 auf, während
auf der anderen Seite als Restfehlerkompensation am Weichenscheitel
WS (Verbindungspunkt der Filterausgangsleitungen
und des Innenleiters der Koaxialleitung) ohne zusätzlichen
Platzbedarf eine am Ende kurzgeschlossene Koaxialleitung
weitergeführt ist. Deren Innenleiter 7 ist zur Vermeidung
von temperaturbedingten mechanischen Spannungen am Ende als
leicht gebogener Draht 8 ausgeführt und mit einem die ganze
Weicheneinheit abdeckenden Deckel 9 z.B. durch Einklemmen
verbunden. Die in diesem Fall mit dielektrischen Resonatoren
DR realisierten zweikreisigen Teilfilter der Frequenzweiche
werden mit orthogonalen HE11δ-Moden betrieben. Die Durchlaßdämpfung
eines Teilfilters beträgt etwa a0 = 2,5 dB, wenn
Resonatoren mit einer Verlustgüte von Q ≥ 20000 Anwendung
finden.The 3-channel crossovers are implemented in such a way that in a metal block or a metallized plastic block, three blind bores as
Durch die in der zweiten Wellenleitung, um die die Teilfilter konzentrisch angeordnet sind, auf der dem Zirkulator abgewandten Seite vorgesehenen Kompensationsmittel werden die Störungen des jeweils durchlassenden Filters, verursacht durch die unerwünschte Transformation des hochohmigen Eingangswiderstandes der jeweils sperrenden Filter über die AnschluBleitungen zwischen den Filterausgängen und dem zweiten Wellenleiter (Weichenscheitel) weitgehend ausgeglichen. Elektrische Vorteile bringt die Fertigung des Gehäuses der Weichenanordnung aus einem einzigen Metallblock bzw. metallisierten Kunststoffblock durch kurze und definierte Verbindungswege sowie eine minimale Anzahl von Verbindungsstellen. Mechanische Vorteile bestehen in einer kompakten und platzsparenden Bauweise, der Unterbringung der Kompensationsmittel ohne zusätzlichen Platzbedarf sowie in definierten und toleranzarmen Anschlüssen. Der mit orthogonalen Moden betriebene dielektrische Resonator als hochselektives Zweikreisfilter ist besonders vorteilhaft aus Sicht der hohen Güte- und Klimaanforderungen, der erwünschten Kompaktheit und der ausgezeichneten Wirtschaftlichkeit in den Frequenzweichen aktueller Mobilfunksysteme.By the in the second waveguide around which the sub-filter are arranged concentrically on the circulator Compensation means provided on the opposite side the interference of the filter passing through due to the undesired transformation of the high-resistance input resistance the respective blocking filter over the Connection lines between the filter outputs and the second one Waveguide (switch vertex) largely balanced. The manufacture of the housing brings electrical advantages Switch arrangement from a single metal block or metallized Plastic block through short and defined connection paths and a minimal number of connection points. Mechanical advantages are a compact and space-saving Construction, the accommodation of the compensation means without additional space requirements and in defined and low tolerance connections. The one operated with orthogonal modes dielectric resonator as a highly selective dual circuit filter is particularly advantageous from a high point of view Quality and climate requirements, the desired compactness and the excellent economy in the crossovers current mobile radio systems.
Die gewünschte Umstimmbarkeit jedes beliebigen Teilfilters
des Filter-Combiners auf alle vereinbarten Kanalfrequenzen
innerhalb des System-Frequenzbandes wird ohne unzulässige
Deformation der Filtereigenschaften (etwa durch gravierende
Güteeinbußen oder durch das Auftreten von Störmoden) dadurch
erreicht, daß der dielektrische Resonator DR durch zwei
Resonatoren etwa der halben Dicke (in Achsrichtung) und etwa
mit den gleichen äußeren Abmessungen ersetzt wird, wobei
wenigstens eine der beiden Resonatorhälften definiert, z.B.
mittels eines systemgesteuerten Schrittmotors, in axialer
Richtung verschiebbar ausgeführt ist und die Stärke des
Luftspalts 10 zwischen beiden Resonatorhälften letztlich die
Mittelfrequenz des Zweikreisfilters bestimmt. Diese
Verschiebbarkeit ist in Figur 6 durch den Zwei-Richtungspfeil
angedeutet.The desired retune of any sub-filter
of the filter combiner to all agreed channel frequencies
within the system frequency band is without impermissible
Deformation of the filter properties (e.g. by serious
Loss of quality or the occurrence of fault modes)
achieved that the dielectric resonator DR by two
Resonators about half the thickness (in the axial direction) and about
is replaced with the same external dimensions, whereby
defines at least one of the two resonator halves, e.g.
by means of a system-controlled stepper motor, in axial
Movable direction and the strength of the
Claims (15)
- Antenna filter combiner for connecting a number of frequency channels to one transmitting antenna (Ant), with n circulators (Z1, Z2, Zn) connected into a waveguide (W1) leading to the antenna (Ant), whereby the direction of the signal flow of the circulators (Z1, Z2, Zn) is utilized in such a way that frequency channels already fed in at the diplexer of the β. circulator (Z2) are totally reflected, at least approximately, at the circulators 1 ... (β-1)(Z1) located ahead in the line of the waveguide (W1) and passed on in the direction of the antenna (Ant) via any further circulators (β+1) ... n(Z2),
characterized in that µ transmitting channels (SK) are fed in through the third gate of the circulators (Z1, Z2, Zn) in each case via a diplexer (FW) consisting of µ < = m combined part-filters (TF). - Antenna filter combiner in accordance with claim 1, characterized in that the part-filters (µ > = 2) (TF) of each diplexer (FW) consist of high-Q resonators (DR1, DR2, DR3).
- Antenna filter combiner in accordance with claim 2, characterized in that the resonators (DR1, DR2, DR3) are operated with two or more modes.
- Antenna filter combiner in accordance with claim 2 or 3, characterized in that the part-filters (TF1, TF2, TF3, (TF4)) are arranged concentrically and, relative to the resonator axes, axially parallel about a second waveguide (W2) forming the crest of the diplexer (FW) for carrying the filter outputs (FA) on the shortest electrical path to the second waveguide (W2) whose end is formed as a connector for a direct, optimally short connection to the third gate of a circulator (Z1, Z2, Zn) connected in the first waveguide (W1).
- Antenna filter combiner in accordance with claim 4, characterized in that the second waveguide (W2) is a modified coaxial cable (7).
- Antenna filter combiner in accordance with claim 4 or 5, characterized in that compensating elements (K1, K2, K3) are provided in the second waveguide (W2) on the side away from the circulator (Z1, Z2, Zn) and used to compensate for the interference caused by the blocking transmitter combining filters in the pass-band of the transmitting channel (SK).
- Antenna filter combiner in accordance with claim 6, characterized in that in the formation of the second waveguide (W2) as a coaxial cable, a further coaxial cable (8) which is attached at the connecting point of the filter output cables and of the inner conductor (7) of the coaxial cable and short-circuited at the end is provided as a compensating element (K1, K2, K3).
- Antenna filter combiner in accordance with claim 7, characterized in that the short-circuited end of the inner conductor (7) is formed as a slightly bent wire (8).
- Antenna filter combiner in accordance with one of claims 4 to 8, characterized in that the housing (1) of the diplexer arrangement consists of a single metal block or metallized plastic block.
- Antenna filter combiner in accordance with one of claims 3 to 9, characterized in that a dielectric resonator (DR1, DR2, DR3) operated with orthogonal modes is designed as a highly-selective two-circuit filter.
- Antenna filter combiner in accordance with claim 10, characterized in that for retuning any of the part-filters (TF) to all agreed channel frequencies within a system frequency band, the dielectric resonator (DR1, DR2, DR3) is replaced by two resonators of approximately half the thickness (in the axial direction) and with approximately the same external dimensions, of which at least one resonator half is designed to be moved in the axial direction.
- Antenna filter combiner in accordance with claim 11, characterized in that the axial movement of the resonator half is system-controlled using a stepper motor.
- Antenna filter combiner in accordance with one of claims 1 to 12, characterized by a diplexer (FW) consisting of three part-filters (TF1, TF2, TF3).
- Antenna filter combiner in accordance with one of claims 1 to 12, characterized by a diplexer (FW) consisting of two part-filters (TF1, TF2).
- Antenna filter combiner in accordance with one of claims 1 to 12, characterized by a diplexer (FW) consisting of four part-filters (TF1, TF2, TF3, TF4).
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| DE4322843 | 1993-07-08 | ||
| DE4322843 | 1993-07-08 |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| EP0633621A1 EP0633621A1 (en) | 1995-01-11 |
| EP0633621B1 true EP0633621B1 (en) | 1999-09-22 |
Family
ID=6492312
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| EP94110380A Expired - Lifetime EP0633621B1 (en) | 1993-07-08 | 1994-07-04 | Antenna-filter-combiner |
Country Status (4)
| Country | Link |
|---|---|
| US (1) | US5546057A (en) |
| EP (1) | EP0633621B1 (en) |
| DE (1) | DE59408762D1 (en) |
| FI (1) | FI943265A (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE102004054370B3 (en) * | 2004-11-10 | 2006-04-20 | Siemens Ag | Arrangement for switching on at least one transmitting unit to a transmitting-receiving antenna |
Families Citing this family (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH0955606A (en) * | 1995-08-11 | 1997-02-25 | Fujitsu Ltd | Filter for radio equipment, dielectric arrangement jig for the filter for radio equipment and dielectric body arrangement method for filter for radio equipment using the jig |
| US5881371A (en) * | 1995-10-27 | 1999-03-09 | Trimble Navigation Limited | Antenna switching technique for improved data throughput in communication networks |
| US6252461B1 (en) | 1997-08-25 | 2001-06-26 | Frederick Herbert Raab | Technique for wideband operation of power amplifiers |
| US6201949B1 (en) * | 1998-05-22 | 2001-03-13 | Rolf Kich | Multiplexer/demultiplexer structures and methods |
| EP2124289A1 (en) * | 2008-05-20 | 2009-11-25 | CommScope, Inc. of North Carolina | Resonator system |
Family Cites Families (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE974386C (en) * | 1942-10-18 | 1960-12-08 | Dehydag Gmbh | Plasticizing and elasticizing agents for polyvinyl chloride |
| DE973386C (en) * | 1952-04-05 | 1960-02-04 | Telefunken Gmbh | Coupling arrangement for high frequency circuits |
| FR1158914A (en) * | 1956-09-28 | 1958-06-20 | Sadir Carpentier | Improvements to coupling systems |
| US3435358A (en) * | 1966-06-08 | 1969-03-25 | Anaconda Electronics Co | Cable television amplifier powering |
| DE2213962C3 (en) * | 1972-03-22 | 1979-01-18 | Siemens Ag, 1000 Berlin Und 8000 Muenchen | Radio field in a radio relay system |
| DE3632984A1 (en) * | 1986-09-29 | 1988-04-07 | Ant Nachrichtentech | ARRANGEMENT FOR CONNECTING SEVERAL TRANSMITTERS AND RECEIVERS TO AN ANTENNA |
| DE4024480A1 (en) * | 1990-08-02 | 1992-02-06 | Ant Nachrichtentech | Frequency switching device using parallel filters - has inductance in coupling line section between common supply line and each filter |
| JPH0529806A (en) * | 1991-07-19 | 1993-02-05 | Nec Corp | Branching and synthesizing device |
-
1994
- 1994-07-04 EP EP94110380A patent/EP0633621B1/en not_active Expired - Lifetime
- 1994-07-04 DE DE59408762T patent/DE59408762D1/en not_active Expired - Fee Related
- 1994-07-08 FI FI943265A patent/FI943265A/en not_active Application Discontinuation
-
1995
- 1995-03-16 US US08/405,445 patent/US5546057A/en not_active Expired - Fee Related
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE102004054370B3 (en) * | 2004-11-10 | 2006-04-20 | Siemens Ag | Arrangement for switching on at least one transmitting unit to a transmitting-receiving antenna |
Also Published As
| Publication number | Publication date |
|---|---|
| US5546057A (en) | 1996-08-13 |
| EP0633621A1 (en) | 1995-01-11 |
| FI943265A0 (en) | 1994-07-08 |
| FI943265A (en) | 1995-01-09 |
| DE59408762D1 (en) | 1999-10-28 |
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