EP0059064B1 - Anordnung zum Starten und Betreiben von Lampen - Google Patents

Anordnung zum Starten und Betreiben von Lampen Download PDF

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Publication number
EP0059064B1
EP0059064B1 EP82300787A EP82300787A EP0059064B1 EP 0059064 B1 EP0059064 B1 EP 0059064B1 EP 82300787 A EP82300787 A EP 82300787A EP 82300787 A EP82300787 A EP 82300787A EP 0059064 B1 EP0059064 B1 EP 0059064B1
Authority
EP
European Patent Office
Prior art keywords
lamp
frequency
voltage
driver circuit
circuit according
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired
Application number
EP82300787A
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English (en)
French (fr)
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EP0059064A1 (de
Inventor
Stephen Paul Webster
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Thorn EMI PLC
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Thorn EMI PLC
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Filing date
Publication date
Application filed by Thorn EMI PLC filed Critical Thorn EMI PLC
Publication of EP0059064A1 publication Critical patent/EP0059064A1/de
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Publication of EP0059064B1 publication Critical patent/EP0059064B1/de
Expired legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/36—Controlling
    • H05B41/38—Controlling the intensity of light
    • H05B41/39—Controlling the intensity of light continuously
    • H05B41/392—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions

Definitions

  • the present invention relates to circuits for activating discharge lamps and in particular circuits for activating fluorescent lamps.
  • the lamp cathode To avoid cold-striking such a lamp, the lamp cathode must be heated to emission before a high voltage is applied to strike the arc.
  • Such an electro-mechanical device has a limited life and is not suited to inclusion in an electronic ballast.
  • Electronic starter switches have emerged recently as replacements for the conventional 'glow-starters' but these are thyristor circuits which, at least at present, will not work with the large dv/dt conditions at high frequencies.
  • SRS semi- resonant start
  • circuit series resonance provides pre-heating current through the cathodes and at the same time, a high voltage across the lamp by resonant magnification.
  • German Offenlegungsschrift No. 27 21 253 there is disclosed a starting and operating system for fluorescent lamps which seeks to avoid the problem of cold starting.
  • That circuit includes a transistor inverter for supplying preheat current and delayed starting voltage to the lamp for that purpose.
  • Leakage inductance of the output transformer serves as a ballast at the operating . frequency of 20 kHz with the lamp running and the inverter frequency is 7 kHz prior to running.
  • starting is delayed with a switch until a sufficient time for preheating has occurred.
  • a suitable delay has to be devised for all conceivable operating conditions which we do not believe can be the most efficient for all circumstances. We do not, therefore, believe that this proposal can be a sufficiently satisfatory solution to the problem.
  • a lamp driver circuit for at least one discharge lamp comprising
  • the converter means may desirably be arranged to draw power from the low frequency AC supply with unity power factor.
  • the inverter may also comprise a series arrangement of two switching means, one of which is in parallel with the lamp driven, means for defining desired instants at which one switching means is to become non-conductive and the other conductive and vice versa, means for indicating when the switching means actually become non-conducting, and means responsive to the defining and indicating means for causing the other switching means to become conductive only when the said one switching means is non-conductive and vice versa.
  • a switched mode power supply 11 operates to derive reasonably constant DC from an AC supply, whilst maintaining unity power factor.
  • An inverter 12 receives the DC output of supply 11, and provides high frequency AC to a fluorescent lamp 13, via a DC blocking capacitor C23 and a ballast inductance L2.
  • a frequency control circuit 14 controls the frequency of the output of the inverter 12.
  • the circuit 14 of Figure 1 is arranged to sweep the frequency of the output during ignition of the lamp 13.
  • capacitor C25 is connected across the lamp 13, and the output of the inverter is connected to the lamp via the ballast inductance L2 and the DC blocking capacitor C23.
  • Capacitor C25 and inductance L2 are chosen to form a resonant circuit which resonates, in this example, at less than 28 kHz.
  • the frequency control circuit is to set to operate the inverter at a frequency much higher than the reasonant frequency, for example 50 kHz. At this high frequency, the capacitor shunts the lamp 13 and the filaments of it are heated.
  • the frequency control reduces the frequency toward resonance, magnifying the voltage across the lamp 13 until it strikes.
  • the capacitor C25 is shunted by the lamp, damping the resonance.
  • the sweep of frequency then continues down until it stops at a preset lower operating frequency, in this example 28 kHz, consistent with the required current.
  • the resonance frequency is less than the running frequency it may be advantageous for resonance to be higher than the running frequency as long as it is at a lower frequency than that at which the lamp is expected to strike.
  • the frequency control circuit ensures the lamp filaments are heated before the lamp strikes, to help increase lamp life, and the lamp is protected from large voltages and currents.
  • the sweep of frequency in this example from 50 kHz towards 28 kHz, is caused by sweep control circuit 15 which controls the frequency of oscillation of a clock 16 which defines the operating frequency of the inverter.
  • the circuit 14 also controls the mean operating frequency of the inverter to limit the maximum pre-strike voltage supplied to the lamp.
  • the circuit 14 comprises a comparator 17 which compares a reference voltage V ref with a voltage representing the actual lamp voltage. If the voltage representing the actual lamp voltage exceeds the reference the frequency of the inverter is increased, the action of the sweep control 15 being at least partly overridden, to maintain the frequency away from resonance. Thus if the lamp does not strike, the lamp voltage is held at the maximum safe level (defined by the. reference voltage) indefinitely.
  • the voltage representing the actual lamp voltage is derived from a secondary winding L2S of a transformer, of which inductance L2 forms the primary, by a full wave rectifier 201.
  • the rectifier 201 is also connected to a series regulator circuit 202 which supplies smoothed DC (LT+) to operate the oscillator 16, sweep control 15, and driver circuit 8 of the switched mode power supply 11, and all active circuits of the circuit of Figure 1 which require a low tension supply LT+. In this way it is ensured that if the lamp 13 fails or is not connected in the circuit, the circuit ceases to operate because the low tension supply is ultimately derived in dependence upon power flow to the lamp.
  • LT+ smoothed DC
  • Figure 1 also includes an arrangement for dimming lamp 13 by increasing the source frequency.
  • a differential current transformer DCT1 monitors the lamp current and produces a voltage representative thereof in an "AC to average circuit" 203. It is then compared with a voltage reference obtained from a dimming control potentiometer P1 in an error amplifier (comparator) 17'. The output of 17' is added to that of 17 to control the frequency similarly but to the different and opposing purpose of dimming. It will be appreciated that this method of dimming is insensitive to changes in supply voltage. Further the increase in cathode heating current as the supply frequency increases is also an aid to successful dimming to low levels.
  • the inverter 12 of Figure 1 comprises two switching transistors VT8 and VT9 connected in series, and controlled by a driver and logic circuit 25. It is essential that both transistors are never simultaneously conductive. Each transistor is, however, subject to charge storage effects whereby charge stored in it when it is conductive continues to flow for a short time after the base voltage controlling its conduction has changed to turn it off.
  • the circuit 25 is arranged to ensure that the transistors VT8 and VT9 are never both simultaneously conductive despite the variable frequency of operation of the inverter.
  • Figure 2 shows the inverter 12 and its driver and logic circuit 25 in more detail.
  • the example shown in Figure 2 has two fluorescent lamps 13 and 13' connected in parallel (although two other discharge lamps could be used) and two load inductors L2 and L2' connected in parallel.
  • the two load inductors are coupled via the DC blocking capacitor C23 to the centre tap of a series arrangement of the two switching transistors VT8 and VT9 connected across the output of the switched mode power supply 11.
  • the collector- emitter paths of the transistors VT8 and VT9 are, shunted by diodes D20 and D21 and the bases of the transistors are connected to the secondary transformers T2 and T3 across which resistors R52 and R53 are connected.
  • the primary of the transformer T2 is connected in series with a driver transistor VT6 and the primary of transformer T3 is connected in series with a driver transistor VT7.
  • the two series arrangements of primaries and transistors are in turn connected in parallel between ground and a point X which is connected to the low tension supply via a resistor R48.
  • connection is by a circuit, not shown, which does not connect the supply when the lamp has not started.
  • the bases of the driver transistors VT6 and VT7 are connected by coupling circuits 26 and 27 to logic circuits 29 and 30 which control their conduction.
  • the circuits 26 and 27 convert the logic gate outputs into a form suitable fortransis- tor base drive.
  • the logic circuits 29 and 30 are arranged to ensure that transistors VT8 and VT9 are never both conductive at the same time despite the charge storage effects and their variable frequency of operation.
  • the circuits have a clock input for receiving a clock signal CK defining nominal switching times for the transistors VT8 and VT9, and a further input coupled to the centre tap of the transistors VT8, VT9 via a coupling circuit 28 to receive a signal VCT indicative of whether or not transistor VT8 or VT9 is non-conductive.
  • the circuits 29 and 30 have outputs T and B connected to the bases of the transistors VT6 and VT7.
  • transistor VT8 is conductive (ON) the current through L2 or L2' rises and the voltage across the inductor L2 or L2' is such that the voltage at the centre tap CT is the positive potential of terminal 3+ of the power supply 11, +400 V say.
  • the voltage at the centre tap indicates the state of transistors VT8 and VT9.
  • the clock signal CK is as shown at CK in Figure 3 and defines the nominal switching times NST of the transistors VT8 and VT9. It is applied to a bistable (JKflip-flop) which derives from it signals Q and Q, of which only Q is shown in Figure 3.
  • VT8 and VT9 do actually alternately conduct even for a short time, so the logic circuits 29 and 30 provide short turn on pulses P in response to CK at the end of the desired conduction periods of the transistors VT8 and VT9.
  • FIG. 4 shows in detail the frequency control circuit 15 and the clock circuit 16 of the lamp circuit of Figure 1.
  • the clock circuit 16 comprises a 555 timer 34, the clock period of which is defined by a capacitor C18 and the (variable) resistance of a field effect transistor FET2 and fixed resistors R41, R42 and R43.
  • the resistance of the FET2 is in turn determined by the voltage across a capacitor C17 connected between the gate and the source 2 of FET2.
  • the frequency control circuit comprises a comparator which compares a reference voltage defined by a zener diode DZR, with a voltage representing the actual lamp voltage of the lamps 13 and 13'. This actual voltage is derived via the rectifier 201 from the secondaries L2S and L2S' of the load inductances of the inverter 12, the voltage on the primaries being related to the lamp voltage.
  • the output of the comparator is connected to the gate of the FET2.
  • the effect of the circuit 15 is to modulate the charge on capacitor C17 and thus the clock frequency in dependence upon the voltage of the lamp or lamps.
  • the Q factor of the series resonant circuit comprising C23, L2 and the lamp cathodes is so high that operation at or near resonance has to be avoided because of the large voltages and currents which result.
  • the method is to limit the maximum pre-strike lamp voltage by feedback control of the inverter frequency.
  • the low tension windings of L2 are used to represent the voltage on L2 primary and this in turn is related to lamp voltage. If the secondary voltage attempts to exceed the reference value of zener diode DZR fed to comparator 17 the frequency of circuit 16 is increased or'pulled back' against the action of the sweep circuit so that in the event a lamp does not strike the lamp voltage is held at the maximum level indefinitely and the circuit remains safe. If the lamp does strike, however, the resulting (large) drop in lamp voltage and hence L2 secondary voltage turns comparator 17 off and sweep is allowed to continue, reducing frequency to the (lower) desired operating point (e.g. 28 kHz) defined by R42 - Cl 8.
  • the (lower) desired operating point e.g. 28 kHz
  • the switch mode power supply 11 is shown in more detail in Figure 5, (also described in our co-pending published application No. EP-A-59 053 "Switched Mode Power Supply", claiming the same priority date).
  • it comprises a step-up converter formed by inductor L1, diode D1 and switching transistor VT1, fed with full wave rectified AC by a rectifier 1.
  • a comparator 7 with hysteresis compares the input voltage sensed by a potentiometer 6 (R2, R3) with the input current sensed by resistor R1.
  • the comparator 7 causes the transistor VT1 to switch so as to keep the instantaneous value of the input current within a fixed range of the instantaneous value of a proportion of the input voltage.
  • the transistor is controlled by the comparator 7 via a drive circuit 8.
  • the series arrangement of capacitors C1' and C1" connected across the output is chosen to provide a constant DC output for a given range of load variation, the power supply 11 operating to keep the capacitors charged.
  • the supply 11 may also comprise a circuit 10 which senses when the output voltage across capacitors C1' and C1" exceeds a preset limit, and turns off the transistor VT1. It also comprises a circuit 9 which varies the voltage dividing ratio of the potentiometer 6 via an FET, FET1, to keep the output constant despite slow variations in the supply voltage.
  • a start-up circuit 21 is provided.
  • Circuit 21 also forms a relaxation oscillator of period, for example, 3 s, so that the circuit will 'test' for a lamp in circuit every 3 s. If no lamp (or no 'healthy' lamp) is in the circuit the input power remains practically zero.

Claims (10)

1. Eine Lampen-Treiberschaltung für wenigstens eine Entladungslampe, umfassend
Umsetzer-Mittel (11) zur Erzeugung eines Gleichstrom-Ausgangs aus einer Einspeisung eines Wechselstroms mit niedriger Frequenz,
einen Umsetzer (12) zur Erzeugung eines Wechselstroms mit hoher Frequenz aus dem Gleichstrom-Ausgang,
eine Reihenschaltung aus einer Induktivität (L2) und einem Kondensator (C25) zum Empfang des Wechselstrom-Ausgangs, wobei die Induktivität so angeordnet ist, daß sie als induktiver Ballast für eine parallel mit dem Kondensator zu verbindende Entladungslampe (13) wirkt, wobei die Induktivität und der Kondensator so gewählt sind, daß sie eine Resonanzschaltung bilden, und
Steuermittel (14), die bewirken, daß der Umsetzer mit einer Frequenz oberhalb der Resonanzfrequenz der Resonanzschaltung arbeitet, wenn die Lampen-Treiberschaltung anfänglich eingeschaltet wird, und daß dann die Betriebsfrequenz in Richtung auf Resonanz verringert wird, bis die Lampe zündet.
2. Eine Lampen-Treiberschaltung nach Anspruch 1, bei der die Steuermittel (14) so angeordnet sind, daß sie die Frequenz, nachdem die Lampe gezündet hat, weiter in Richtung auf Resonanz ändern, bis eine vorgegebene Betriebsfrequenz zwischen der Zündfrequenz und der Resonanzfrequenz erreicht ist.
3. Eine Lampen-Treiberschaltung nach einem der vorhergehenden Ansprüche, die Mittel zur Begrenzung der der Lampe zugeführten Spannung einschließt, wenn die Lampe nicht zündet.
4. Eine Lampen-Treiberschaltung nach Anspruch 3, bei der die Mittel zur Begrenzung der Spannung Mittel enthalten, die auf die Spannung ansprechen, die die Steuermittel veranlaßt, die Frequenz in Abhängigkeit von der genannten Spannung zu steuern.
5. Eine Lampen-Treiberschaltung nach Anspruch 4, bei der die Mittel zur Begrenzung der Spannung Mittel (17) enthalten, die eine weitere, die Lampenspannung darstellende Spannung mit einer Bezugsspannung (V ref) vergleichen, und, wenn die weitere Spannung den Bezug übersteigt, die Änderung der genannten Frequenz außer Kraft setzen, um die Frequenz von der Resonanzfrequenz fernzuhalten.
6. Eine Lampen-Treiberschaltung nach einem der vorhergehenden Ansprüche, umfassend Mittel (P1, 17') zur Steuerung der Betriebsfrequenz der Lampe, um die dieser zugeführte Leistung zu steuern.
7. Eine Lampen-Treiberschaltung , nach Anspruch 6, umfassend Mittel (203, 17') zur Überwachung des Stroms in der Lampe und zum Vergleich eines diesen Strom darstellenden Signals mit einer variablen Bezugsspannung (P1), um eine Abdunkelung der Lampe in Abhängigkeit der Änderung des genannten Bezugs zu bewirken.
8. Eine Lampen-Treiberschaltung nach Anspruch 6, die so ausgebildet ist, daß die der Lampe zugeführte Leistung auf einem etwa konstanten Pegel gehalten wird.
9. Eine Lampen-Treiberschaltung nach einem der vorhergehenden Ansprüche, bei der der Umsetzer (12) zwei in Reihe geschaltete Schaltermittel (VT8, VT9) enthält, von denen eines (VT9) parallel zur gespeisten Lampe (13) liegt, wobei die Schaltung ferner Mittel (Q) zur Definition gewünschter Augenblicke enthält, bei denen ein Schaltermittel nicht-leitend und das andere leitend werden soll und umgekehrt, sowie Mittel (28) zur Anzeige, wenn die Schaltermittel tatsächlich nicht-leitend werden, und Mittel (29, 30), die auf die Definitions- und Anzeigemittel ansprechen, um zu bewirken, daß die anderen Schaltermittel nur leitend werden, wenn das eine Schaltermittel nicht leitend ist und umgekehrt.
10. Eine Lampen-Treiberschaltung nach einem der vorhergehenden Ansprüche, bei der wenigstens eine Entladungslampe (13) eine Leuchtstofflampe ist.
EP82300787A 1981-02-21 1982-02-16 Anordnung zum Starten und Betreiben von Lampen Expired EP0059064B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
GB8105551 1981-02-21
GB8105551 1981-02-21

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EP0059064A1 EP0059064A1 (de) 1982-09-01
EP0059064B1 true EP0059064B1 (de) 1985-10-02

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Cited By (42)

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EP0357285A2 (de) * 1988-08-29 1990-03-07 Gardenamerica Corporation Leistungsversorgung für Aussenbeleuchtung
EP0359860A1 (de) * 1988-09-23 1990-03-28 Siemens Aktiengesellschaft Verfahren und Vorrichtung zum Betreiben mindestens einer Gasentladungslampe
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DE3338464A1 (de) * 1983-10-22 1985-05-15 Plankenhorn Kapitalverwaltungs-KG, 7208 Spaichingen Hochfrequenz-helligkeitssteuerung fuer leuchtstofflampen
US4763239A (en) * 1985-06-04 1988-08-09 Thorn Emi Lighting (Nz) Limited Switched mode power supplies
GB2180418A (en) * 1985-09-14 1987-03-25 Contrology Limited Fluorescent lamp supply circuit
GB2208980B (en) * 1987-08-21 1991-09-11 Transtar Limited Ballast for fluorescent lamp
EP0396621A1 (de) * 1988-01-19 1990-11-14 Etta Industries, Inc. Dimmerschaltung mit schwingungskreisumrichter für leuchtstoffentladungslampen
EP0396621A4 (en) * 1988-01-19 1992-01-15 Etta Industries, Inc. Fluorescent dimming ballast utilizing a resonant sine wave power converter
WO1989010679A1 (en) * 1988-04-25 1989-11-02 Active Lighting Controls Limited Electronic ballast circuit for gas discharge lamp
GB2236921B (en) * 1988-04-25 1992-02-05 Active Lighting Controls Electronic ballast circuit for gas discharge lamp
GB2236921A (en) * 1988-04-25 1991-04-17 Active Lighting Controls Electronic ballast circuit for gas discharge lamp
EP0351012A2 (de) * 1988-07-15 1990-01-17 Koninklijke Philips Electronics N.V. Steuerungsschaltungen für Leuchtstofflampen
EP0351012A3 (de) * 1988-07-15 1990-08-29 Koninklijke Philips Electronics N.V. Steuerungsschaltungen für Leuchtstofflampen
US5111118A (en) * 1988-07-15 1992-05-05 North American Philips Corporation Fluorescent lamp controllers
EP0357285A2 (de) * 1988-08-29 1990-03-07 Gardenamerica Corporation Leistungsversorgung für Aussenbeleuchtung
EP0357285A3 (de) * 1988-08-29 1990-06-06 Gardenamerica Corporation Leistungsversorgung für Aussenbeleuchtung
GB2224170A (en) * 1988-09-21 1990-04-25 W J Parry Electronic ballast circuit for discharge lamps
EP0359860A1 (de) * 1988-09-23 1990-03-28 Siemens Aktiengesellschaft Verfahren und Vorrichtung zum Betreiben mindestens einer Gasentladungslampe
US5049790A (en) * 1988-09-23 1991-09-17 Siemens Aktiengesellschaft Method and apparatus for operating at least one gas discharge lamp
GB2226463A (en) * 1988-12-21 1990-06-27 Sirous Yazdanian Control of fluorescent lights
WO1990011005A1 (fr) * 1989-03-10 1990-09-20 Harel Jean Claude Dispositif electronique de demarrage et d'alimentation pour tubes fluorescents a electrodes prechauffables
FR2644314A1 (fr) * 1989-03-10 1990-09-14 Harel Jean Claude Dispositif electronique de demarrage et d'alimentation pour tubes fluorescents a electrodes prechauffables
EP0389847A2 (de) * 1989-03-16 1990-10-03 Korte, Heinrich Schaltungsanordnung
EP0389847A3 (de) * 1989-03-16 1992-03-04 Korte, Heinrich Schaltungsanordnung
WO1990013988A1 (en) * 1989-05-11 1990-11-15 Zetetic Design Ltd Electronic ballast for discharge lamps
US5089751A (en) * 1989-05-26 1992-02-18 North American Philips Corporation Fluorescent lamp controllers with dimming control
EP0399613A2 (de) * 1989-05-26 1990-11-28 Philips Electronics North America Corporation Steuerschaltungen für Leuchtstofflampen mit Dimmersteuerung
EP0399613A3 (de) * 1989-05-26 1992-07-22 Philips Electronics North America Corporation Steuerschaltungen für Leuchtstofflampen mit Dimmersteuerung
EP0405611A1 (de) * 1989-06-30 1991-01-02 Kabushiki Kaisha Toshiba Kochstelle mit Induktionserwärmung
US5248866A (en) * 1989-06-30 1993-09-28 Kabushiki Kaisha Toshiba Induction heating cooker with phase difference control
US5075602A (en) * 1989-11-29 1991-12-24 U.S. Philips Corporation Discharge lamp control circuit arrangement
EP0430358A1 (de) * 1989-11-29 1991-06-05 Koninklijke Philips Electronics N.V. Schaltanordnung
EP0430357A1 (de) * 1989-11-29 1991-06-05 Koninklijke Philips Electronics N.V. Schaltungsanordnung
EP0439240A3 (en) * 1990-01-20 1992-08-19 Semperlux Gmbh, Lichttechnisches Werk Electronic ballast
EP0439240A2 (de) * 1990-01-20 1991-07-31 SEMPERLUX GmbH, LICHTTECHNISCHES WERK Elektronisches Vorschaltgerät
EP0440244A2 (de) * 1990-01-31 1991-08-07 Toshiba Lighting & Technology Corporation Apparat zum Betreiben einer Entladungslampe
EP0440244A3 (en) * 1990-01-31 1993-01-07 Toshiba Lighting & Technology Corporation Discharge lamp lighting apparatus
EP0461441A1 (de) * 1990-06-06 1991-12-18 Zumtobel Aktiengesellschaft Verfahren und Schaltungsanordnung zur Regelung der Helligkeit (Dimmen) von Gasentladungslampen
EP0482705A3 (en) * 1990-10-25 1992-11-19 N.V. Philips' Gloeilampenfabrieken Circuit arrangement
EP0482705A2 (de) * 1990-10-25 1992-04-29 Koninklijke Philips Electronics N.V. Schaltungsanordnung
EP0490329A1 (de) * 1990-12-07 1992-06-17 Tridonic Bauelemente GmbH System zur Steuerung der Helligkeit und des Betriebsverhaltens von Gasentladungslampen
EP0490330A1 (de) * 1990-12-07 1992-06-17 Tridonic Bauelemente GmbH Schaltungsanordnung zur Steuerung von Gasentladungslampen
EP0495571A2 (de) * 1991-01-16 1992-07-22 Intent Patents A.G. Vielseitiges elektronisches Vorschaltgerät
EP0495571A3 (en) * 1991-01-16 1992-09-02 Intent Patents A.G. Universal electronic ballast system
US5334915A (en) * 1991-09-30 1994-08-02 Toshiba Lighting & Technology Corporation Operating circuit arrangement for a discharge lamp
EP0535911A1 (de) * 1991-09-30 1993-04-07 Toshiba Lighting & Technology Corporation Steuerungsschaltung für eine Entladungslampe
GB2261332A (en) * 1991-11-06 1993-05-12 Horizon Fabrications Ltd Driving circuits for discharge devices
GB2261332B (en) * 1991-11-06 1996-05-08 Horizon Fabrications Ltd Driving circuit for electrical discharge devices
US5493182A (en) * 1994-02-24 1996-02-20 Patent-Treuhand-Gesellschaft F. Elektrische Gluehlampen Mbh Fluorescent lamp operating circuit, permitting dimming of the lamp
US5563477A (en) * 1994-04-15 1996-10-08 Knobel Ag Lichttechnische Komponenten Method for operating a ballast for discharge lamps
US5623188A (en) * 1994-06-15 1997-04-22 Sgs-Thomson Microelectronics S.A. Method and apparatus for controlling an oscillating circuit of a low pressure fluorescent lamp
US5754012A (en) * 1995-01-25 1998-05-19 Micro Linear Corporation Primary side lamp current sensing for minature cold cathode fluorescent lamp system
US5652479A (en) * 1995-01-25 1997-07-29 Micro Linear Corporation Lamp out detection for miniature cold cathode fluorescent lamp system
US5844378A (en) * 1995-01-25 1998-12-01 Micro Linear Corp High side driver technique for miniature cold cathode fluorescent lamp system
US5818669A (en) * 1996-07-30 1998-10-06 Micro Linear Corporation Zener diode power dissipation limiting circuit
US5896015A (en) * 1996-07-30 1999-04-20 Micro Linear Corporation Method and circuit for forming pulses centered about zero crossings of a sinusoid
US5965989A (en) * 1996-07-30 1999-10-12 Micro Linear Corporation Transformer primary side lamp current sense circuit
EP0831678A2 (de) * 1996-09-19 1998-03-25 General Electric Company IC gesteuerte Halbbrückenschaltung für Gasentladungslampe
EP0835044A2 (de) * 1996-10-01 1998-04-08 General Electric Company Verschaltgerät mit Kathodenvorheizungsfunktion
US6541923B1 (en) 1998-11-18 2003-04-01 Microlights Limited Electronic ballasts
US6344980B1 (en) 1999-01-14 2002-02-05 Fairchild Semiconductor Corporation Universal pulse width modulating power converter
US6469914B1 (en) 1999-01-14 2002-10-22 Fairchild Semiconductor Corporation Universal pulse width modulating power converter
WO2012004697A1 (en) * 2010-07-08 2012-01-12 Koninklijke Philips Electronics N.V. Lamp driver

Also Published As

Publication number Publication date
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EP0059064A1 (de) 1982-09-01

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