CN115220512B - Automatic phase-locking constant current source circuit and method for driving tunable laser - Google Patents
Automatic phase-locking constant current source circuit and method for driving tunable laser Download PDFInfo
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Abstract
The application discloses an automatic phase-locking constant current source circuit and a method for driving a tunable laser, comprising a phase hysteresis circuit, a phase-locking loop, an adder and a voltage-controlled constant current source which are sequentially connected, wherein the output end of the voltage-controlled constant current source is connected with a high-pass filter, and the high-pass filter is connected with the phase-locking loop; the input voltage is input into the phase lag circuit, the phase lag circuit can carry out phase lag on the input voltage, the input voltage is input into the phase-locked loop, the phase-locked loop multiplies the phase-lag voltage by the feedback voltage to obtain the superposition voltage, the superposition voltage is filtered and oscillated and then is input into the adder, the adder adds the oscillation voltage and the direct-current offset voltage and then inputs the oscillation voltage into the voltage-controlled constant current source, and the output voltage of the voltage-controlled constant current source enters the high-pass filter to carry out high-pass filtration and then inputs the feedback voltage into the phase-locked loop. The output current is automatically locked to the input voltage, the output current of the voltage-controlled constant current source and the input voltage are guaranteed to be in the same frequency and phase, and the phase difference of the output current lagging behind the input voltage is eliminated.
Description
Technical Field
The application relates to the technical field of constant current sources, in particular to an automatic phase-locking constant current source circuit and method for driving a tunable laser.
Background
The statements in this section merely provide background information related to the present disclosure and may not necessarily constitute prior art.
The fiber bragg grating (Fiber Bragg Grating, FBG) is a wavelength-modulated fiber optic sensor, abbreviated as fiber bragg grating, whose wavelength reflects the information being measured, and therefore requires accurate demodulation of its wavelength. The commonly used fiber bragg grating demodulation methods include an edge filter method, a tunable laser method and the like, wherein the fiber bragg grating wavelength demodulation method based on the tunable laser has the advantages of high demodulation speed, high stability, low cost and the like, and becomes a research hot spot in recent years. The tunable laser needs to be driven by a high-precision current source, the driving current range is generally 0-30 mA, the common precision current driving mode is a current output type digital-to-analog conversion chip (DAC), however, the output current range is generally 0-20 mA, and the driving current range of the tunable laser cannot be covered, so that the driving of the laser is realized by a scheme of matching a voltage output type DAC with a voltage-controlled constant current source circuit. The voltage output type DAC technical scheme is mature, and the voltage-controlled constant current source circuit is a key for realizing laser driving.
As shown in fig. 1 and 2, the output current signal is delayed in phase with the increase of the input voltage signal frequency, and the higher the input voltage frequency is, the greater the output current is delayed in phase with the input voltage. Has the following disadvantages:
(1) For a high-speed fiber bragg grating demodulator, the phase lag of the output current of the voltage-controlled constant current source can cause the system demodulation speed to be reduced;
(2) Since the lag phase is difficult to determine, it is difficult to determine whether the voltage-controlled constant current source outputs a desired current when the high-frequency voltage signal is input, resulting in a decrease in the demodulation accuracy of the system.
Disclosure of Invention
In order to solve the problems, the application provides an automatic phase-locking constant current source circuit and a method for driving a tunable laser, which utilize a phase-locking loop to realize automatic locking of output current to input voltage, ensure that the output current of a voltage-controlled constant current source is in phase with the same frequency as the input voltage, eliminate the phase difference of the output current lagging behind the input voltage, and greatly improve the demodulation speed of a high-speed fiber bragg grating demodulator.
In order to achieve the above purpose, the application adopts the following technical scheme:
in a first aspect, an automatic phase-locking constant current source circuit for driving a tunable laser is provided, which comprises a phase hysteresis circuit, a phase-locked loop, an adder and a voltage-controlled constant current source in sequence, wherein the output end of the voltage-controlled constant current source is connected with a high-pass filter, and the high-pass filter is connected with the phase-locked loop;
the phase hysteresis circuit can input the input voltage after phase hysteresis into the phase-locked loop, the phase-locked loop multiplies the phase-delayed voltage and the feedback voltage to obtain the superimposed voltage, the superimposed voltage is filtered and oscillated and then input into the adder, the adder adds the oscillation voltage and the direct-current offset voltage and then inputs the added oscillation voltage and the direct-current offset voltage into the voltage-controlled constant current source, and the output voltage of the voltage-controlled constant current source enters the high-pass filter to carry out high-pass filtration and then inputs the feedback voltage into the phase-locked loop.
In a second aspect, a control method for an automatic phase-locked constant current source circuit for driving a tunable laser is provided, including:
inputting an input voltage into the phase lag circuit;
the phase lag circuit is used for leading the phase lag of the input voltage to be input into the phase-locked loop;
the phase-locked loop multiplies the phase-lag voltage and the feedback voltage to obtain a superimposed voltage, and filters and oscillates the superimposed voltage and inputs the superimposed voltage into the adder;
the adder adds the oscillating voltage and the direct-current bias voltage and inputs the added oscillating voltage and the added direct-current bias voltage into the voltage-controlled constant current source;
and after the output voltage of the voltage-controlled constant current source enters a high-pass filter for filtering, the feedback voltage is input into the phase-locked loop.
Compared with the prior art, the application has the beneficial effects that:
1. the application realizes the automatic locking of the input voltage by the output current by using the phase-locked loop, ensures the same frequency and phase of the output current and the input voltage, eliminates the phase difference of the output current lagging behind the input voltage, greatly improves the demodulation speed of the high-speed fiber grating demodulator, and solves the problem of low demodulation speed when the traditional constant current source drives the tunable laser.
2. The low-pass filter in the phase-locked loop adopts the program-controlled low-pass filter, so that different cut-off frequencies can be set for different input voltage signals, and the adaptability of the automatic phase-locked constant current source provided by the application is improved.
Additional aspects of the application will be set forth in part in the description which follows and, in part, will be obvious from the description, or may be learned by practice of the application.
Drawings
The accompanying drawings, which are included to provide a further understanding of the application and are incorporated in and constitute a part of this specification, illustrate embodiments of the application and together with the description serve to explain the application.
FIG. 1 is a circuit diagram of an example of a conventional voltage controlled constant current source;
fig. 2 is a circuit diagram of an example two-circuit diagram of a conventional voltage controlled constant current source;
FIG. 3 is a waveform diagram of an example one of a conventional voltage controlled constant current source when the input signal is 1 MHz;
FIG. 4 is cursor data of an example one of a conventional voltage controlled constant current source when the input signal is 1 MHz;
fig. 5 is a waveform diagram of an example one of a conventional voltage-controlled constant current source when an input signal is 10 MHz;
FIG. 6 is cursor data of an example one of a conventional voltage controlled constant current source when the input signal is 10 MHz;
fig. 7 is a waveform diagram of an example two of a conventional voltage-controlled constant current source when the input signal is 5 MHz;
FIG. 8 is cursor data of example two of a conventional voltage controlled constant current source when the input signal is 5 MHz;
fig. 9 is a waveform diagram of an example two of a conventional voltage-controlled constant current source when the input signal is 10 MHz;
FIG. 10 is cursor data of example two of a conventional voltage controlled constant current source when the input signal is 10 MHz;
fig. 11 is a system block diagram of an automatic phase-locked constant current source circuit disclosed in embodiment 1;
fig. 12 is a first simulation circuit diagram of the automatic phase-locked constant current source circuit disclosed in the constructed embodiment 1;
fig. 13 is a first diagram of an automatic phase-locked constant current source circuit according to embodiment 1A waveform diagram;
fig. 14 is a first diagram of an automatic phase-locked constant current source circuit according to embodiment 1And->A waveform diagram;
fig. 15 is a diagram showing first cursor data of the automatic phase-locked constant current source circuit of embodiment 1;
fig. 16 is a second simulation circuit diagram of the constructed embodiment 1 discloses an automatic phase-locked constant current source circuit;
fig. 17 is a second diagram of an automatic phase-locked constant current source circuit according to embodiment 1A waveform diagram;
fig. 18 is a second diagram of an automatic phase-locked constant current source circuit according to embodiment 1And->A waveform diagram;
fig. 19 is a diagram showing second cursor data of the automatic phase-locked constant current source circuit of embodiment 1.
Detailed Description
The application will be further described with reference to the drawings and examples.
It should be noted that the following detailed description is illustrative and is intended to provide further explanation of the application. Unless defined otherwise, all technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this application belongs.
It is noted that the terminology used herein is for the purpose of describing particular embodiments only and is not intended to be limiting of exemplary embodiments according to the present application. As used herein, the singular is also intended to include the plural unless the context clearly indicates otherwise, and furthermore, it is to be understood that the terms "comprises" and/or "comprising" when used in this specification are taken to specify the presence of stated features, steps, operations, devices, components, and/or combinations thereof.
Example 1
As shown in example one of fig. 1 and example two of fig. 2, the output current signal may have a phase lag with increasing frequency of the input voltage signal, and the higher the input voltage frequency, the greater the phase of the output current lag behind the input voltage.
The conventional voltage controlled constant current source shown in FIG. 1, note transistor Q 1 The current of the collector is the output current I o The output current acting solely on resistor R 1 Is the positive feedback voltage U fp The output current acting solely on resistor R 2 Is a negative feedback voltage U fn . Determining the positive feedback coefficient F of the circuit p The method comprises the following steps:
determining a negative feedback coefficient F of the circuit n Is that
Wherein R is 1 、R 2 、R 3 、R 4 、R 5 、R 6 、R 7 All are the resistances of the resistors in fig. 1.
Adjusting the resistance to F n >F p Ensuring that the circuit works in a negative feedback state, and obtaining the transconductance gain A of the circuit by using virtual short and virtual break iuf The method comprises the following steps:
the input voltage frequency was set to 1MHz, the graphic instrument was turned on using software simulation, and the oscilloscope waveforms were as shown in fig. 3. The A channel is an input voltage waveform, and the B channel is an output current waveform. The cursor is displayed, and the cursor 1 is automatically positioned to the maximum value of the A channel and the cursor 2 is positioned to the maximum value of the B channel by utilizing the function of 'going to the next Y-axis maximum value' of software.
Looking at the data where the cursor is positioned, as shown in FIG. 4, the output current lags the input voltage 9.0150ns, with a signal period of 1000ns, and thus the phase of the output current lags 3.2454 °.
The input voltage frequency was adjusted to 10MHz, the plotter was turned on, and the oscilloscope waveform was as shown in fig. 5. Looking at the data where the cursor is positioned, as shown in fig. 6, the output current lags the input voltage 6.2092ns, with a signal period of 100ns, and thus the phase of the output current lags 22.3531 °.
FIG. 2 shows a conventional voltage controlled constant current source, R in the circuit 1 And R is 2 Form a series current negative feedback, a recording triode Q 1 The current of the collector is the output current I o The output current acting solely on R 1 Is a negative feedback voltage U fn The negative feedback coefficient F of the circuit is obtained n The method comprises the following steps:
obtaining transconductance gain A of circuit by depth negative feedback theory iuf The method comprises the following steps:
the input voltage frequency is set to be 5MHz, the oscillograph is opened by using software simulation, the oscillograph waveform is shown in FIG. 7, the A channel is the input voltage waveform, and the B channel is the output current waveform.
Looking at the data where the cursor is positioned, as shown in FIG. 8, the output current lags the input voltage 2.0145ns, with a signal period of 200ns, and thus the phase of the output current lags 3.6261 °.
The input voltage frequency was adjusted to 10MHz, the plotter was turned on, and the oscilloscope waveforms were as shown in fig. 9. Looking at the data where the cursor is positioned, as shown in fig. 10, the output current lags the input voltage 3.1942ns, and the signal period is 100ns, so the phase of the output current lags 11.4991 °.
It can be seen from analysis of the conventional voltage-controlled constant current source shown in fig. 1 and 2 that the phase of the output current signal of the conventional voltage-controlled constant current source is delayed with the increase of the frequency of the input voltage signal, the higher the frequency of the input voltage, the greater the phase of the output current delayed from the input voltage.
In order to realize the same frequency and same phase of the output current and the input voltage and eliminate the problem that the output current lags behind the phase difference of the input voltage, the embodiment provides an automatic phase-locking constant current source circuit for driving a tunable laser, which is shown in fig. 11 and comprises a phase lag circuit, a phase-locking loop, an adder and a voltage-controlled constant current source which are sequentially connected, wherein the output end of the voltage-controlled constant current source, which is used for being connected with a load, is also connected with a high-pass filter, and the high-pass filter is connected with the phase-locking loop;
the phase hysteresis circuit can input the input voltage after phase hysteresis into the phase-locked loop, the phase-locked loop multiplies the phase-delayed voltage and the feedback voltage to obtain the superimposed voltage, the superimposed voltage is filtered and oscillated and then input into the adder, the adder adds the oscillation voltage and the direct-current offset voltage and then inputs the added oscillation voltage and the direct-current offset voltage into the voltage-controlled constant current source, and the output voltage of the voltage-controlled constant current source enters the high-pass filter to carry out high-pass filtration and then inputs the feedback voltage into the phase-locked loop.
The device also comprises a main control module and a voltage output module, wherein the main control module is connected with the voltage output module, and the voltage output module is connected with the phase hysteresis circuit to provide input voltage for the phase hysteresis circuit.
The phase-locked loop comprises a phase discriminator, a loop filter and a voltage-controlled oscillator which are sequentially connected; the phase lag circuit and the high-pass filter are both connected with the phase discriminator.
The phase discriminator comprises a multiplier and a low-pass filter which are connected in sequence; the phase lag circuit and the high-pass filter are both connected with the multiplier.
Preferably, the low-pass filter adopts a program-controlled low-pass filter, and the program-controlled low-pass filter is connected with the main control module.
The phase lag circuit adopts a 90-degree phase lag circuit, and the 90-degree phase lag circuit can lag the phase of the input voltage by 90 degrees and is formed by connecting two paths of RC low-pass filters in series.
The voltage output module adopts a voltage output type DAC.
The adder adds the oscillation voltage and the dc bias voltage, and then can raise the voltage signal above the horizontal axis.
The output current of the voltage-controlled constant current source is in the same frequency and phase with the feedback voltage input into the phase-locked loop by the high-pass filter; the high pass filter inputs the feedback voltage of the phase-locked loop in phase with the input voltage at the same frequency.
An automatic phase-locked constant current source circuit for driving a tunable laser disclosed in this embodiment will be described in detail.
The main control module firstly sends out digital signals to a voltage output DAC, and the DAC correspondingly outputs high-frequency analog voltage signalsThe input voltage of the 90 DEG phase hysteresis circuit is specifically:
wherein U is i Is an input voltage signal, namely a voltage signal output by a voltage output type DAC; omega i For inputting voltage signal U i T is time.
First, a 90 DEG phase lag circuit is passed to lead the phase lag of 90 DEG to be +.>Expressed as:
wherein, the liquid crystal display device comprises a liquid crystal display device,is the output voltage signal of the 90 deg. phase lag circuit.
Through authentication in phase-locked loopPhase shifter, first with feedback voltage +.>Multiplication is performed, influenced by the phase discrimination characteristics of the phase discriminator,>the phase of (2) will lead +.>Is expressed as:
wherein U is f The feedback voltage signal is a voltage signal output by the high-pass filter; omega o To output voltage signalIs a frequency of (a) is a frequency of (b).
Obtaining difference frequency signals and sum frequency signal superposition signalsExpressed as:
then pass through a program-controlled low-pass filter to filter out +.>The sum frequency signal of the (B) is left to obtain the difference frequency signal>Expressed as:
deviation is atWithin the range of>And->Phase deviation and->And shows positive correlation. Because of->The bandwidth of the low-pass filter needs to be correspondingly changed, so that the bandwidth of the low-pass filter needs to be program-controlled, the program-controlled low-pass filter is selected, the program-controlled low-pass filter is connected with the main control module, and the cut-off frequency of the program-controlled low-pass filter is controlled through the main control module. />Filtering high frequency components in the low frequency signal by a loop filter to obtain a small ripple direct current signal which can be used by a voltage-controlled oscillator>Due to the regulation of the negative feedback of the phase-locked loop, after feedback iteration, when the phase deviation approaches 0, the phase deviation is +.>Approaching 0, the output voltage of the loop filter +.>Approaching 0, the resulting feedback voltage +.>Phase-delayed voltage from input phase-locked loopThe same frequency. There is also->Is advanced by +.>90 DEG of the phase of (2), then->And->The same frequency is in phase.
Voltage controlled oscillator based onOscillation output frequency and->Positive correlated voltage signal-> Through the adder, the adder is also introduced with a DC offset U ref Adder is +.>Adding DC bias U ref Raising the voltage signal above the horizontal axis to obtain +.>Ensuring a constant direction of current flow through the load. />Obtaining output current through a voltage-controlled constant current sourceLoad R L The voltage at both ends, i.e. the output voltage->Since the load is a purely resistive load, the output current is +.>And output voltage +.>The same frequency is in phase. />Filtering the DC component by a high-pass filter to obtain an AC signal +.>Is fed back to the phase-locked loop because the cut-off frequency of the high-pass filter is much lower than the output voltage +.>So that the output voltage is not changed +.>Thus outputting current +.>And feedback voltage->The same frequency and the same phase, thereby finally realizing the output current +.>And input voltage of input phase lag circuit +.>The same frequency is in phase.
The simulation software is used to build a simulation circuit of the automatic phase-locked constant current source circuit disclosed in the embodiment, the simulation circuit diagram is shown in fig. 12, the main control module and the voltage output DAC are replaced by signal sources with the software, the 90-degree phase lag circuit is connected in series by using two paths of RC low-pass filters, and R is used for the automatic phase-locked constant current source circuit 1 、C 1 、R 2 、C 2 The composition, the value of RC is regulated to make the cut-off frequency equal to the frequency of the input signal, one path of RC low-pass filter can lead the phase of the input signal to lag 45 degrees, and two paths can lag 90 degrees. The phase-locked loop uses an integrated phase-locked loop pll_virtual that is self-contained in software. The adder is composed of an operational amplifier U 1 And peripheral resistor. The voltage-controlled constant current source uses the circuit shown in figure 1 and is composed of an operational amplifier U 2 Triode Q 1 And peripheral capacitor resistor. The high-pass filter is composed of C 4 And R is 14 Composition is prepared. Because the input of the phase discriminator is the phase difference of the two signals, the amplitude of the signals only affects the proportionality coefficient of the output signal of the phase discriminator, thus feeding back the voltage signalOnly need to sum the output voltage signal of the voltage-controlled constant current source>Keep the same frequency and phase, add>Is not necessary nor +.>Identical. So from the viewpoint of convenient circuit design, the high-pass filter is from R 12 The upper end is led out.
Input voltageThe frequency was set to 10MHz and the oscilloscope XSC2 was observed to show a waveform of +.>After feedback adjustment by a phase locked loop +.>Gradually approaching 0 as shown in fig. 13. Observing an oscilloscope XSC1, wherein an oscilloscope A channel is voltage output type DAC output voltage +.>The B channel is the output current +.>Is a waveform of (a). When->Approaching 0, an input voltage of +.>And output current +.>The waveform of (2) is shown in fig. 14.
Viewing the data to which the cursor is positioned, as shown in FIG. 15, at which time the voltage is inputThe maximum value is taken at 198.8270. Mu.s, and the current is outputted as well +.>A maximum value was also reached at 198.8270. Mu.s. Since the sampling period of the oscilloscope is 0.1ns, the input voltage +.>And output current->The time difference between them is less than 0.1ns, and thus the phase difference is less than 0.36 °.
The voltage-controlled constant current source shown in fig. 2 is used to build a simulation circuit diagram of the automatic phase-locked constant current source circuit disclosed in the present embodiment, as shown in fig. 16, the input voltageThe frequency was set to 10MHz and the oscilloscope XSC2 was observed to show a waveform of +.>After feedback adjustment by a phase locked loop +.>Gradually approaching 0 as shown in fig. 17.
Observing an oscilloscope XSC1, wherein an oscilloscope A channel is input voltageThe B channel is the output current +.>Is a waveform of (a). When->Approaching 0, an input voltage of +.>And output current +.>The waveform of (2) is shown in fig. 18. Viewing the data to which the cursor is positioned, as shown in FIG. 19, at which time the voltage is input +.>Maximum value is obtained at 218.5157 mu s, and the same is trueOutput current->A maximum value was also reached at 218.5157. Mu.s. Since the sampling period of the oscilloscope is 0.1ns, the input voltage +.>And output current->The time difference between them is less than 0.1ns, and thus the phase difference is less than 0.36 °.
By constructing two simulation circuits to perform simulation analysis, the automatic phase-locking constant current source circuit for driving the tunable laser disclosed by the embodiment is verified, and the output current is realized by using a phase-locked loopAutomatic locking input voltage +.>Ensure output current +.>And input voltage->Same frequency and same phase, eliminating output current +.>Hysteresis of input voltage->The demodulation speed of the high-speed fiber grating demodulator is greatly improved. The problem of the tunable laser of traditional constant current source drive, demodulation speed is slow is solved.
Since the constant current source circuit disclosed in this embodiment eliminates the output currentHysteresis of input voltage->When a high-frequency voltage signal is input, whether the expected current is output or not can be judged by synchronously measuring the output current of the constant current source circuit, so that the demodulation precision of the high-speed fiber grating demodulator is effectively improved. The problem of the tunable laser of traditional constant current source drive, demodulation accuracy is low is solved.
The low-pass filter of the phase discriminator in the phase-locked loop uses a program-controlled low-pass filter, and the program-controlled low-pass filter is connected with the main control module, so that different cut-off frequencies are set for different input voltage signals, and the adaptability is improved.
Example 2
In this embodiment, a control method of an automatic phase-locked constant current source circuit driving a tunable laser is proposed, including:
inputting an input voltage into the phase lag circuit;
the phase lag circuit is used for leading the phase lag of the input voltage to be input into the phase-locked loop;
the phase-locked loop multiplies the phase-lag voltage and the feedback voltage to obtain a superimposed voltage, and filters and oscillates the superimposed voltage and inputs the superimposed voltage into the adder;
the adder adds the oscillating voltage and the direct-current bias voltage and inputs the added oscillating voltage and the added direct-current bias voltage into the voltage-controlled constant current source;
and after the output voltage of the voltage-controlled constant current source enters a high-pass filter for filtering, the feedback voltage is input into the phase-locked loop.
Finally, it should be noted that: the above embodiments are only for illustrating the technical aspects of the present application and not for limiting the same, and although the present application has been described in detail with reference to the above embodiments, it should be understood by those of ordinary skill in the art that: modifications and equivalents may be made to the specific embodiments of the application without departing from the spirit and scope of the application, which is intended to be covered by the claims.
Claims (6)
1. The automatic phase-locking constant current source circuit for driving the tunable laser is characterized by comprising a phase hysteresis circuit, a phase-locked loop, an adder and a voltage-controlled constant current source which are sequentially connected, wherein the output end of the voltage-controlled constant current source is connected with a high-pass filter, and the high-pass filter is connected with the phase-locked loop;
the phase-locked loop comprises a phase discriminator, a loop filter and a voltage-controlled oscillator which are connected in sequence; the phase hysteresis circuit and the high-pass filter are connected with the phase discriminator;
the phase discriminator comprises a multiplier and a low-pass filter which are connected in sequence; the phase lag circuit and the high-pass filter are connected with the multiplier;
the adder adds the oscillating voltage and the input DC bias voltage and then raises the voltage signal to the upper part of the horizontal axis;
the output current of the voltage-controlled constant current source is in the same frequency and phase with the feedback voltage input into the phase-locked loop by the high-pass filter; the feedback voltage of the high-pass filter input phase-locked loop is in phase with the input voltage in the same frequency;
the input voltage is input into the phase lag circuit, the phase lag circuit can carry out phase lag on the input voltage, the input voltage is input into the phase-locked loop, the phase-locked loop multiplies the phase-lag voltage by the feedback voltage to obtain the superposition voltage, the superposition voltage is filtered and oscillated and then is input into the adder, the adder adds the oscillation voltage and the direct-current offset voltage and then inputs the oscillation voltage into the voltage-controlled constant current source, and the output voltage of the voltage-controlled constant current source enters the high-pass filter to carry out high-pass filtration and then inputs the feedback voltage into the phase-locked loop.
2. The automatic phase-locked constant current source circuit for driving a tunable laser according to claim 1, further comprising a voltage output module connected to the phase-lag circuit for providing an input voltage to the phase-lag circuit.
3. The automatic phase-locked constant current source circuit for driving a tunable laser according to claim 2, further comprising a main control module connected to the voltage output module.
4. The automatic phase-locked constant current source circuit for driving a tunable laser according to claim 1, wherein the low-pass filter is a programmable low-pass filter, and the programmable low-pass filter is connected with the main control module.
5. The automatic phase-locked constant current source circuit for driving a tunable laser according to claim 1, wherein the phase-lag circuit employs a 90 ° phase-lag circuit, and the 90 ° phase-lag circuit is capable of phase-lagging an input voltage by 90 °.
6. A control method of an automatic phase-locked constant current source circuit for driving a tunable laser according to claim 1, comprising:
inputting an input voltage into the phase lag circuit;
the phase lag circuit is used for leading the phase lag of the input voltage to be input into the phase-locked loop;
the phase-locked loop multiplies the phase-lag voltage and the feedback voltage to obtain a superimposed voltage, and filters and oscillates the superimposed voltage and inputs the superimposed voltage into the adder;
the adder adds the oscillating voltage and the direct-current bias voltage and inputs the added oscillating voltage and the added direct-current bias voltage into the voltage-controlled constant current source;
and after the output voltage of the voltage-controlled constant current source enters a high-pass filter for filtering, the feedback voltage is input into the phase-locked loop.
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| CN101719628B (en) * | 2009-11-23 | 2011-04-20 | 北京优立光太科技有限公司 | Portable semiconductor laser frequency stabilizer |
| JP5570905B2 (en) * | 2010-08-05 | 2014-08-13 | 株式会社ミツトヨ | Frequency stabilized laser light source and wavelength calibration method |
| CN104821603A (en) * | 2015-06-03 | 2015-08-05 | 郭建林 | Method for controlling wind power integration inverter for realizing same frequency and same phase, and circuit thereof |
| CN113097860B (en) * | 2021-03-10 | 2022-09-13 | 浙江大学 | Semiconductor laser driving current circuit and output frequency real-time feedback method |
| CN113572022B (en) * | 2021-06-02 | 2022-04-19 | 西安电子科技大学 | Laser frequency stabilization system based on improved double-path digital phase-locked amplifier |
| CN114628991A (en) * | 2022-03-10 | 2022-06-14 | 中国科学院半导体研究所 | Tunable semiconductor laser driving device |
| CN217008072U (en) * | 2022-04-15 | 2022-07-19 | 哈尔滨理工大学 | High-resolution arbitrary waveform laser driving source |
| CN115220512B (en) * | 2022-08-10 | 2023-10-17 | 山东大学 | Automatic phase-locking constant current source circuit and method for driving tunable laser |
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| CN101577544A (en) * | 2009-06-15 | 2009-11-11 | 华亚微电子（上海）有限公司 | Phase-locked loop with collapse protection mechanism |
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| CN110071418A (en) * | 2019-04-25 | 2019-07-30 | 电子科技大学 | A kind of differential mode-locked laser phaselocked loop |
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| WO2024031944A1 (en) | 2024-02-15 |
| CN115220512A (en) | 2022-10-21 |
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