CN115220512A - Automatic phase-locking constant current source circuit and method for driving tunable laser - Google Patents
Automatic phase-locking constant current source circuit and method for driving tunable laser Download PDFInfo
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Abstract
The invention discloses an automatic phase-locking constant current source circuit and a method for driving a tunable laser, which comprises a phase lag circuit, a phase-locked loop, an adder and a voltage-controlled constant current source which are connected in sequence, wherein the output end of the voltage-controlled constant current source is connected with a high-pass filter; the input voltage is input into the phase lag circuit, the phase lag circuit can input the input voltage into the phase-locked loop after the phase lag, the phase-locked loop multiplies the phase lag voltage and the feedback voltage to obtain a superposed voltage, the superposed voltage is input into the adder after being filtered and oscillated, the summated voltage adds the oscillating voltage and the direct current bias voltage and then inputs the voltage-controlled constant current source, the output voltage of the voltage-controlled constant current source enters the high-pass filter for high-pass filtering, and then the feedback voltage is input into the phase-locked loop. The output current is automatically locked with the input voltage, the same frequency and phase of the output current of the voltage-controlled constant current source and the input voltage are ensured, and the phase difference that the output current lags behind the input voltage is eliminated.
Description
Technical Field
The invention relates to the technical field of constant current sources, in particular to an automatic phase-locking constant current source circuit and method for driving a tunable laser.
Background
The statements in this section merely provide background information related to the present disclosure and may not necessarily constitute prior art.
A Fiber Bragg Grating (FBG) is a wavelength modulation type optical Fiber sensor, called Fiber Grating for short, and the wavelength of the Fiber Grating reflects the information to be measured, so that the wavelength of the Fiber Grating needs to be accurately demodulated. Common fiber grating demodulation methods include an edge filter method, a tunable laser method, and the like, wherein the fiber grating wavelength demodulation method based on the tunable laser has the advantages of high demodulation speed, high stability, low cost, and the like, and has recently become a research hotspot. The tunable laser needs to be driven by a high-precision current source, the driving current range is generally 0-30 mA, the common precision current driving mode is a current output type digital-to-analog conversion chip (DAC), however, the output current range is generally 0-20 mA, and the driving current range of the tunable laser cannot be covered, so that the laser driving is realized by mostly using a scheme that a voltage output type DAC is matched with a voltage-controlled constant current source circuit. The voltage output type DAC is mature in technical scheme, and the voltage-controlled constant current source circuit is the key for realizing laser driving.
In the conventional voltage-controlled constant current source, as shown in fig. 1 and 2, the output current signal has a phase lag with the increase of the frequency of the input voltage signal, and the higher the frequency of the input voltage signal is, the larger the phase lag of the output current with respect to the input voltage signal is. Has the following disadvantages:
(1) For a high-speed fiber grating demodulator, the phase lag of the output current of the voltage-controlled constant current source can cause the demodulation speed of the system to be reduced;
(2) Since the lag phase is difficult to determine, when a high-frequency voltage signal is input, it is difficult to determine whether the voltage-controlled constant current source outputs a desired current, which results in a decrease in system demodulation accuracy.
Disclosure of Invention
The invention provides an automatic phase-locking constant current source circuit and a method for driving a tunable laser, which aim to solve the problems, and utilize a phase-locked loop to realize that the output current automatically locks the input voltage, ensure that the output current of a voltage-controlled constant current source and the input voltage have the same frequency and the same phase, eliminate the phase difference that the output current lags behind the input voltage, and greatly improve the demodulation speed of a high-speed fiber grating demodulator.
In order to achieve the purpose, the invention adopts the following technical scheme:
the output end of the voltage-controlled constant current source is connected with a high-pass filter, and the high-pass filter is connected with the phase-locked loop;
the phase lag circuit can input the input voltage into the phase-locked loop after performing phase lag, the phase-locked loop multiplies the phase lag voltage and the feedback voltage to obtain a superposed voltage, the superposed voltage is input into the adder after being filtered and oscillated, the adder adds the oscillating voltage and the direct-current bias voltage and inputs the added voltage into the voltage-controlled constant-current source, and the output voltage of the voltage-controlled constant-current source enters the high-pass filter to perform high-pass filtering and then inputs the feedback voltage into the phase-locked loop.
In a second aspect, a method for controlling an automatic phase-locking constant current source circuit for driving a tunable laser is provided, including:
inputting an input voltage into a phase lag circuit;
the phase lag circuit inputs the input voltage into the phase-locked loop after lagging the phase;
the phase-locked loop multiplies the phase lag voltage and the feedback voltage to obtain a superposed voltage, and the superposed voltage is input into an adder after being filtered and oscillated;
the adder adds the oscillation voltage and the direct current bias voltage and inputs the added voltage and the added voltage into the voltage-controlled constant current source;
and after the output voltage of the voltage-controlled constant current source enters a high-pass filter for filtering, the feedback voltage is input into the phase-locked loop.
Compared with the prior art, the invention has the following beneficial effects:
1. the invention utilizes the phase-locked loop to realize the automatic locking of the output current to the input voltage, ensures the same frequency and phase of the output current and the input voltage, eliminates the phase difference that the output current lags behind the input voltage, greatly improves the demodulation speed of the high-speed fiber grating demodulator, and solves the problem of slow demodulation speed when the traditional constant current source drives the tunable laser.
2. The low-pass filter in the phase-locked loop adopts a program-controlled low-pass filter, can set different cut-off frequencies aiming at different input voltage signals, and improves the adaptability of the automatic phase-locked constant current source.
Advantages of additional aspects of the invention will be set forth in part in the description which follows, and in part will be obvious from the description, or may be learned by practice of the invention.
Drawings
The accompanying drawings, which are incorporated in and constitute a part of this application, are included to provide a further understanding of the application, and the description of the exemplary embodiments and illustrations of the application are intended to explain the application and are not intended to limit the application.
Fig. 1 is a circuit diagram of an example of a conventional voltage-controlled constant current source;
FIG. 2 is a circuit diagram of an exemplary two-stage conventional voltage-controlled constant current source;
fig. 3 is a waveform diagram of an example of a conventional voltage-controlled constant current source when an input signal is 1 MHz;
fig. 4 is cursor data of an example of a conventional voltage-controlled constant current source when an input signal is 1 MHz;
FIG. 5 is a waveform diagram of an example of a conventional voltage controlled constant current source when the input signal is 10 MHz;
fig. 6 is cursor data of an example of a conventional voltage-controlled constant current source when an input signal is 10 MHz;
fig. 7 is a waveform diagram of a second example of a conventional voltage-controlled constant current source when an input signal is 5 MHz;
fig. 8 is cursor data of a second example of a conventional voltage-controlled constant current source when an input signal is 5 MHz;
FIG. 9 is a waveform diagram of an example two of a conventional voltage controlled constant current source when the input signal is 10 MHz;
fig. 10 shows cursor data of a second example of a conventional voltage-controlled constant current source when an input signal is 10 MHz;
fig. 11 is a system block diagram of an automatic phase-locking constant current source circuit disclosed in embodiment 1;
fig. 12 is a first simulation circuit diagram of the automatic phase-locking constant current source circuit disclosed in the embodiment 1;
FIG. 13 shows a first embodiment of an auto-phase-locked constant current source circuit according to embodiment 1
A waveform diagram;
FIG. 14 is a diagram showing a first embodiment of the self-phase-locking constant current source circuit according to embodiment 1
And
a waveform diagram;
fig. 15 is first cursor data of the constant current source circuit of the automatic phase-locking disclosed in embodiment 1;
fig. 16 is a second simulation circuit diagram of the constructed automatic phase-locking constant current source circuit disclosed in embodiment 1;
FIG. 17 shows a second constant current source circuit for automatic phase locking disclosed in embodiment 1
A waveform diagram;
FIG. 18 is a diagram showing a second constant current source circuit of the automatic phase-locking disclosed in embodiment 1
And
a waveform diagram;
fig. 19 is second cursor data of the automatic phase-locking constant current source circuit disclosed in embodiment 1.
Detailed Description
The invention is further described with reference to the following figures and examples.
It should be noted that the following detailed description is exemplary and is intended to provide further explanation of the disclosure. Unless defined otherwise, all technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this application belongs.
It is noted that the terminology used herein is for the purpose of describing particular embodiments only and is not intended to be limiting of exemplary embodiments according to the present application. As used herein, the singular forms "a", "an" and "the" are intended to include the plural forms as well, and it should be understood that when the terms "comprises" and/or "comprising" are used in this specification, they specify the presence of stated features, steps, operations, devices, components, and/or combinations thereof, unless the context clearly indicates otherwise.
Example 1
In a conventional voltage-controlled constant current source, as shown in the first example of fig. 1 and the second example of fig. 2, the output current signal has a phase lag with an increase in the frequency of the input voltage signal, and the higher the frequency of the input voltage signal is, the greater the phase lag of the output current with respect to the input voltage signal is.
The conventional voltage-controlled constant current source shown in fig. 1 is a triode Q 1 The current of the collector is the output current I o With output current acting solely on resistor R 1 Is a positive feedback voltage U fp With output current acting solely on resistor R 2 Is a negative feedback voltage U fn . Determining the positive feedback factor F of the circuit p Comprises the following steps:
determining the negative feedback coefficient F of the circuit n Is composed of
Wherein R is 1 、R 2 、R 3 、R 4 、R 5 、R 6 、R 7 Are all resistance values of the resistor in fig. 1.
Adjusting the resistance value so that F n >F p Ensuring the circuit to work in negative feedback state, and calculating transconductance increase of the circuit by using ' virtual short ' and ' virtual breakYi A iuf Comprises the following steps:
the input voltage frequency was set to 1MHz, the graphic instrument was turned on using software simulation, and the oscilloscope waveform was as shown in fig. 3. The channel A is the input voltage waveform, and the channel B is the output current waveform. And displaying the cursor, and automatically positioning the cursor 1 to the maximum value of the channel A and the cursor 2 to the maximum value of the channel B by using the function of 'go to the next maximum value of the Y axis' of the software.
Looking at the data at which the cursor is positioned, as shown in FIG. 4, when the output current lags behind the input voltage by 9.0150ns, the signal period is 1000ns, so the phase of the output current lags by 3.2454.
The input voltage frequency was adjusted to 10MHz and the graphic instrument was turned on and the oscilloscope waveform was as shown in figure 5. Looking at the data at which the cursor is positioned, as shown in FIG. 6, the output current lags the input voltage by 6.2092ns, the signal period is 100ns, and thus the phase of the output current lags by 22.3531.
In the conventional voltage-controlled constant current source, R in the circuit shown in FIG. 2 1 And R 2 Form a series current negative feedback and memory triode Q 1 The current of the collector is the output current I o With output current acting solely on R 1 Is a negative feedback voltage U fn Determining a negative feedback coefficient F of the circuit n Comprises the following steps:
the transconductance gain A of the circuit is obtained by the deep negative feedback theory iuf Comprises the following steps:
the frequency of the input voltage is set to 5MHz, the graphic instrument is opened by software simulation, the waveform of the oscilloscope is shown in figure 7, the channel A is the input voltage waveform, and the channel B is the output current waveform.
Looking at the data at which the cursor is positioned, as shown in FIG. 8, the output current lags behind the input voltage by 2.0145ns, the signal period is 200ns, and thus the phase of the output current lags by 3.6261.
The input voltage frequency was adjusted to 10MHz and the graphic instrument was turned on and the oscilloscope waveform was as shown in fig. 9. Looking at the data at which the cursor is positioned, as shown in FIG. 10, the output current lags behind the input voltage by 3.1942ns, the signal period is 100ns, and thus the phase of the output current lags by 11.4991.
It can be known from the analysis of the conventional voltage-controlled constant current source shown in fig. 1 and 2 that the output current signal of the conventional voltage-controlled constant current source has a phase lag with the increase of the frequency of the input voltage signal, and the higher the frequency of the input voltage is, the larger the phase lag of the output current with respect to the input voltage is.
In order to realize the same frequency and phase of the output current and the input voltage and eliminate the problem of phase difference that the output current lags behind the input voltage, the embodiment provides an automatic phase-locking constant current source circuit for driving a tunable laser, as shown in fig. 11, the automatic phase-locking constant current source circuit comprises a phase lag circuit, a phase-locked loop, an adder and a voltage-controlled constant current source which are connected in sequence, the voltage-controlled constant current source is used for connecting the output end connected with a load and is also connected with a high-pass filter, and the high-pass filter is connected with the phase-locked loop;
the phase lag circuit can input the input voltage into the phase-locked loop after performing phase lag, the phase-locked loop multiplies the phase lag voltage and the feedback voltage to obtain a superposed voltage, the superposed voltage is input into the adder after being filtered and oscillated, the adder adds the oscillating voltage and the direct-current bias voltage and inputs the added oscillating voltage and the direct-current bias voltage into the voltage-controlled constant-current source, and the output voltage of the voltage-controlled constant-current source enters the high-pass filter to be subjected to high-pass filtering and then is input into the feedback voltage into the phase-locked loop.
The voltage control circuit further comprises a main control module and a voltage output module, wherein the main control module is connected with the voltage output module, and the voltage output module is connected with the phase lag circuit and provides input voltage for the phase lag circuit.
The phase-locked loop comprises a phase discriminator, a loop filter and a voltage-controlled oscillator which are connected in sequence; the phase lag circuit and the high-pass filter are both connected with the phase discriminator.
The phase discriminator comprises a multiplier and a low-pass filter which are connected in sequence; the phase lag circuit and the high-pass filter are both connected with the multiplier.
Preferably, the low-pass filter adopts a program-controlled low-pass filter, and the program-controlled low-pass filter is connected with the main control module.
The phase lag circuit adopts a 90-degree phase lag circuit, the 90-degree phase lag circuit can lag the phase of an input voltage by 90 degrees, and the phase lag circuit is formed by connecting two RC low-pass filters in series.
The voltage output module adopts a voltage output DAC.
The adder can raise the voltage signal to a level above the horizontal axis by adding the oscillation voltage and the dc offset voltage.
The output current of the voltage-controlled constant current source and the feedback voltage input into the phase-locked loop by the high-pass filter have the same frequency and phase; the feedback voltage of the high-pass filter input phase-locked loop is in the same frequency and phase as the input voltage.
The present embodiment discloses an automatic phase-locked constant current source circuit for driving a tunable laser.
The main control module firstly sends a digital signal to a voltage output type DAC (digital to analog converter), and the DAC correspondingly outputs a high-frequency analog voltage signal
The input voltage of the 90-degree phase lag circuit is specifically as follows:
wherein, U i Is an input voltage signal, namely a voltage signal output by a voltage output type DAC; omega i For an input voltage signal U i T is time.
wherein the content of the first and second substances,
is the output voltage signal of the 90 deg. phase lag circuit.
wherein, U f Is a feedback voltage signal, namely a voltage signal output by the high-pass filter; omega o To output a voltage signal
Of the frequency of (c).
Obtaining the difference frequency signal and the sum frequency signal superposed signal
Expressed as:
deviation in
Within the range of (A) and (B),
and
phase deviation of and between
Is in positive correlation. Because of the fact that
The frequency of the low-pass filter is different, the bandwidth of the low-pass filter also needs to be changed correspondingly, so the bandwidth of the low-pass filter needs to be programmed, the program-controlled low-pass filter is selected and connected with the main control module, and the cut-off frequency of the program-controlled low-pass filter is controlled by the main control module.
Filtering high-frequency components in the signal by a loop filter to obtain a small-ripple direct-current signal which can be used by the voltage-controlled oscillator
Due to the regulation and control of the negative feedback of the phase-locked loop, after feedback iteration, when the phase deviation approaches to 0,
close to 0, output voltage of loop filter
Approaching 0, the obtained feedback voltage
Voltage after phase lag with input phase-locked loop
And (4) carrying out same frequency. And is also provided with
Is advanced in phase with
Is 90 deg. then
And
the same frequency and the same phase.
Voltage controlled oscillator based on
Oscillation output frequency and
voltage signal in positive correlation
Through the adder, the adder is also fed with a direct current bias U ref The adder is at
Adding a DC bias U ref Raising the voltage signal above the horizontal axis to obtain
Ensuring a constant direction of current through the load.
Obtaining output current through a voltage-controlled constant current source
Load R L Voltage across, i.e. output voltage
Since the load is a purely resistive load, the current is output
And an output voltage
The same frequency and the same phase.
Filtering the DC component in the signal by a high-pass filter to obtain an AC signal
Feedback to the phase locked loop because the cut-off frequency of the high pass filter is much lower than the output voltage
So that the output voltage is not changed
So that the output current is
And a feedback voltage
Same frequency and same phase, thereby finally realizing output current
And an input voltage to the phase lag circuit
The same frequency and the same phase.
The simulation circuit of the automatic phase-locking constant current source circuit disclosed by the embodiment is built by using simulation software, the simulation circuit diagram is shown in fig. 12, the main control module and the voltage output type DAC are replaced by signal sources carried by the software, the 90-degree phase lag circuit is formed by connecting two paths of RC low-pass filters in series and is formed by R 1 、C 1 、R 2 、C 2 The RC value is adjusted to ensure that the cut-off frequency is equal to the frequency of the input signal, one path of RC low-pass filter can lead the phase of the input signal to lag 45 degrees, and two paths of RC low-pass filter can lag 90 degrees. The phase-locked loop uses an integrated phase-locked loop PLL _ VIRTUAL that is software self-contained. The adder is composed of an operational amplifier U 1 And a peripheral resistor. The voltage-controlled constant current source uses the circuit given in figure 1 and is composed of an operational amplifier U 2 Triode Q 1 And a peripheral capacitor resistor. High pass filter composed of 4 And R 14 And (4) forming. Because the input of the phase discriminator is the phase difference of two signals, the amplitude of the signals only affects the proportionality coefficient of the output signals of the phase discriminator, and therefore, voltage signals are fed back
Output voltage signal of voltage-controlled constant current source
The same frequency and the same phase are kept,
need not be equal in magnitude
Are identical. Therefore, the high-pass filter is R-pass filter from the perspective of convenient circuit design 12 The upper end is led out.
Input voltage
Setting the frequency to 10MHz, observing an oscilloscope XSC2, and displaying the waveform
After feedback adjustment of the phase locked loop, it can be observed
Gradually approaches 0 as shown in fig. 13. Observing the XSC1 of the oscilloscope, wherein the A channel of the oscilloscope is a DAC output voltage of a voltage output type
The B channel is the output current
The waveform of (2). When in use
When approaching 0, the input voltage is observed
And output current
The waveform of (2) is shown in fig. 14.
Viewing data to which cursor is positioned, e.g. map15, at this time the input voltage
Get the maximum value at 198.8270 mus and output the same current
A maximum was also taken at 198.8270. Mu.s. Since the sampling period of the oscilloscope is 0.1ns, the input voltage is
And output current
The time difference between them is less than 0.1ns, so the phase difference is less than 0.36 °.
The voltage-controlled constant current source shown in fig. 2 is used to build a simulation circuit diagram of the automatic phase-locking constant current source circuit disclosed in this embodiment, as shown in fig. 16, the input voltage
Setting the frequency to 10MHz, observing an oscilloscope XSC2, and displaying the waveform as
After feedback adjustment of the phase locked loop, it can be observed
Gradually approaches 0 as shown in fig. 17.
Observing the oscilloscope XSC1, the oscilloscope A channel being input voltage
The B channel is the output current
The waveform of (2). When in use
When the voltage of the power supply approaches to 0,observe the input voltage
And output current
The waveform of (2) is shown in FIG. 18. Looking at the data at which the cursor is positioned, as shown in FIG. 19, the input voltage is now
The maximum value is obtained at 218.5157 mu s, and the current is output
A maximum was also taken at 218.5157 μ s. Since the sampling period of the oscilloscope is 0.1ns, the input voltage is
And output current
The time difference between them is less than 0.1ns, so the phase difference is less than 0.36 °.
The automatic phase-locking constant current source circuit for driving the tunable laser disclosed by the embodiment is verified by setting up two simulation circuits for simulation analysis, and the output current is realized by utilizing the phase-locked loop
Auto-locking input voltage
Ensuring output current
And an input voltage
Same frequency and phase, eliminating output current
Lagging the input voltage
The phase difference greatly improves the demodulation speed of the high-speed fiber grating demodulator. The problem of low demodulation speed when a traditional constant current source drives a tunable laser is solved.
Since the constant current source circuit disclosed in this embodiment eliminates the output current
Lags behind the input voltage
When a high-frequency voltage signal is input, whether the expected current is output or not can be judged by synchronously measuring the output current of the constant current source circuit, and the demodulation precision of the high-speed fiber grating demodulator is effectively improved. The problem of low demodulation precision when the traditional constant current source drives the tunable laser is solved.
The low-pass filter of the phase discriminator in the phase-locked loop uses a program-controlled low-pass filter, and the program-controlled low-pass filter is connected with the master control module, so that different cut-off frequencies are set for different input voltage signals, and the adaptability is improved.
Example 2
In this embodiment, a control method of an automatic phase-locking constant current source circuit for driving a tunable laser is provided, including:
inputting an input voltage into the phase lag circuit;
the phase lag circuit inputs the input voltage into the phase-locked loop after lagging the phase;
the phase-locked loop multiplies the phase lag voltage and the feedback voltage to obtain a superposed voltage, and the superposed voltage is input into an adder after being filtered and oscillated;
the adder adds the oscillation voltage and the direct-current bias voltage and inputs the added voltage into the voltage-controlled constant-current source;
and after the output voltage of the voltage-controlled constant current source enters a high-pass filter for filtering, the feedback voltage is input into the phase-locked loop.
Finally, it should be noted that: although the present invention has been described in detail with reference to the above embodiments, it should be understood by those skilled in the art that: modifications and equivalents may be made to the embodiments of the invention without departing from the spirit and scope of the invention, which is to be covered by the claims.
Claims (10)
1. The automatic phase-locking constant current source circuit for driving the tunable laser is characterized by comprising a phase lag circuit, a phase-locked loop, an adder and a voltage-controlled constant current source which are sequentially connected, wherein the output end of the voltage-controlled constant current source is connected with a high-pass filter, and the high-pass filter is connected with the phase-locked loop;
the input voltage is input into the phase lag circuit, the phase lag circuit can input the input voltage into the phase-locked loop after the phase lag, the phase-locked loop multiplies the phase lag voltage and the feedback voltage to obtain a superposed voltage, the superposed voltage is input into the adder after being filtered and oscillated, the summated voltage adds the oscillating voltage and the direct current bias voltage and then inputs the voltage-controlled constant current source, the output voltage of the voltage-controlled constant current source enters the high-pass filter for high-pass filtering, and then the feedback voltage is input into the phase-locked loop.
2. An auto-phase locked constant current source circuit for driving a tunable laser as claimed in claim 1, further comprising a voltage output module, the voltage output module connected to the phase lag circuit for providing an input voltage to the phase lag circuit.
3. The auto-phase-locked constant current source circuit for driving a tunable laser according to claim 2, further comprising a main control module connected to the voltage output module.
4. An automatic phase-locking constant current source circuit for driving a tunable laser as claimed in claim 3, wherein the phase-locked loop comprises a phase detector, a loop filter and a voltage-controlled oscillator connected in sequence; the phase lag circuit and the high-pass filter are both connected with the phase discriminator.
5. The automatic phase-locking constant current source circuit for driving a tunable laser as claimed in claim 4, wherein the phase detector comprises a multiplier and a low-pass filter connected in sequence; the phase lag circuit and the high-pass filter are both connected with the multiplier.
6. The auto-lock phase constant current source circuit for driving a tunable laser as claimed in claim 5, wherein the low pass filter is a programmable low pass filter, and the programmable low pass filter is connected to the main control module.
7. An auto-phase-lock constant current source circuit for driving a tunable laser as claimed in claim 1, wherein the phase lag circuit employs a 90 ° phase lag circuit, the 90 ° phase lag circuit being capable of phase-lagging the input voltage by 90 °.
8. The auto-phase-locked constant current source circuit for driving a tunable laser according to claim 1, wherein the adder adds the oscillating voltage and the input dc offset voltage to raise the voltage signal above the horizontal axis.
9. The automatic phase-locking constant current source circuit for driving a tunable laser according to claim 1, wherein the output current of the voltage-controlled constant current source is in the same frequency and phase as the feedback voltage input to the phase-locked loop by the high-pass filter; the feedback voltage of the high-pass filter input phase-locked loop is in the same frequency and phase as the input voltage.
10. A control method of an automatic phase-locking constant current source circuit for driving a tunable laser is characterized by comprising the following steps:
inputting an input voltage into the phase lag circuit;
the phase lag circuit inputs the input voltage into the phase-locked loop after lagging the phase;
the phase-locked loop multiplies the phase lag voltage and the feedback voltage to obtain a superposed voltage, and the superposed voltage is input into an adder after being filtered and oscillated;
the adder adds the oscillation voltage and the direct current bias voltage and inputs the added voltage and the added voltage into the voltage-controlled constant current source;
and after the output voltage of the voltage-controlled constant current source enters a high-pass filter for filtering, the feedback voltage is input into the phase-locked loop.
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| CN110798207A (en) * | 2019-09-29 | 2020-02-14 | 浙江大学 | Phase-locked loop bandwidth expanding circuit |
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| JP5570905B2 (en) * | 2010-08-05 | 2014-08-13 | 株式会社ミツトヨ | Frequency stabilized laser light source and wavelength calibration method |
| CN104821603A (en) * | 2015-06-03 | 2015-08-05 | 郭建林 | Method for controlling wind power integration inverter for realizing same frequency and same phase, and circuit thereof |
| CN113097860B (en) * | 2021-03-10 | 2022-09-13 | 浙江大学 | Semiconductor laser driving current circuit and output frequency real-time feedback method |
| CN113572022B (en) * | 2021-06-02 | 2022-04-19 | 西安电子科技大学 | Laser frequency stabilization system based on improved double-path digital phase-locked amplifier |
| CN114628991A (en) * | 2022-03-10 | 2022-06-14 | 中国科学院半导体研究所 | Tunable semiconductor laser driving device |
| CN217008072U (en) * | 2022-04-15 | 2022-07-19 | 哈尔滨理工大学 | High-resolution arbitrary waveform laser driving source |
| CN115220512B (en) * | 2022-08-10 | 2023-10-17 | 山东大学 | Automatic phase-locking constant current source circuit and method for driving tunable laser |
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- 2022-08-10 CN CN202210956456.XA patent/CN115220512B/en active Active
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| CN205754276U (en) * | 2015-05-21 | 2016-11-30 | 意法半导体国际有限公司 | Phaselocked loop and circuit |
| CN109639272A (en) * | 2018-12-14 | 2019-04-16 | 北京时代民芯科技有限公司 | A kind of adaptive wideband phase-locked loop circuit |
| CN110071418A (en) * | 2019-04-25 | 2019-07-30 | 电子科技大学 | A kind of differential mode-locked laser phaselocked loop |
| CN110798207A (en) * | 2019-09-29 | 2020-02-14 | 浙江大学 | Phase-locked loop bandwidth expanding circuit |
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| WO2024031944A1 (en) * | 2022-08-10 | 2024-02-15 | 山东大学 | Automatic phase-locked constant-current source circuit and method for driving tunable laser |
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| WO2024031944A1 (en) | 2024-02-15 |
| CN115220512B (en) | 2023-10-17 |
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