CN111865060B - Output short-circuit protection method of boost converter - Google Patents
Output short-circuit protection method of boost converter Download PDFInfo
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- CN111865060B CN111865060B CN202010750368.5A CN202010750368A CN111865060B CN 111865060 B CN111865060 B CN 111865060B CN 202010750368 A CN202010750368 A CN 202010750368A CN 111865060 B CN111865060 B CN 111865060B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
- H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
- H02H7/10—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers
- H02H7/12—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers
- H02H7/1213—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers for DC-DC converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
Abstract
The invention relates to an output short-circuit protection method of a boost converter.A second switching tube with a parasitic diode reversely biased is arranged between a freewheeling diode and the output end of the boost converter; the output voltage of the boost converter and the current flowing through the second switching tube are sampled to determine the over-current and short-circuit states and respond correspondingly. After a voltage signal at the joint of the freewheeling diode and the second switching tube rises to reach a threshold voltage, the rising speed of the output voltage of the boost converter is controlled by controlling the rising speed of a first reference voltage connected with the first transimpedance amplifier, meanwhile, the current flowing through the second switching tube is sampled and combined with loop control of the second transimpedance amplifier to adjust the output current of the boost converter, and overcurrent protection is carried out by combining hiccup logic to control the boost converter to exit a short-circuit state. The invention solves the problem that the current cannot be controlled when the boost converter outputs overcurrent, short circuit or drives a large capacitor, can be integrated in a chip, and does not increase the system volume.
Description
Technical Field
The invention belongs to the technical field of switching power supplies, and relates to an overcurrent protection, large-capacitance driving and soft start technology of a BOOST converter (BOOST converter).
Background
Because of the structural characteristics of the boost converter, a parasitic diode channel always exists between input and output, and when the output is in an overcurrent state, a short circuit state or a large capacitance state, the diode is always in a conducting state, so that the current cannot be controlled, and the chip can be permanently damaged.
As shown in fig. 1, the boost converter includes an inductor L, a first switching tube M0, and a freewheeling diode D1, where one end of the inductor L is connected to the input end of the boost converter, and the other end of the inductor L is connected to the output end of the boost converter after passing through the freewheeling diode D1; the first switch transistor M0 is connected between the connection point of the inductor L and the freewheeling diode D1 and ground. The freewheeling diode D1 is a parasitic diode of the switch M1, and Cload and Rload are a load capacitor and a load resistor, respectively. It can be seen that in the BOOST converter BOOST architecture of the conventional BOOST converter, since the freewheeling diode D1 path exists between the input and the output, the current on the path cannot be controlled, and when the capacitance of the load capacitor Cload is large, or the resistance of the load resistor Rload is small, or the output is short-circuited, the input signal V is insertedINThe current in this path is large and uncontrollable, possibly resulting in permanent chip damage.
The existing solution to this problem is shown in fig. 2, a fuse is added to the BOOST converter BOOST output, and when the output is short-circuited, protection is achieved by a fuse blowing manner. However, this approach has the disadvantage of requiring the addition of external devices for protection, and does not facilitate the minimization of system volume, while being less likely to be integrated. And when output has big electric capacity, probably have continuous heavy current on the afterflow route, can lead to the fuse fusing to unable normal start limits output capacitance's application range.
Disclosure of Invention
The invention provides an output short-circuit protection method of a boost converter, aiming at the problems that a parasitic diode channel existing between the input and the output of the boost converter is always conducted when outputting overcurrent, short circuit or driving a large capacitor, so that the current cannot be controlled, and the defects that an external fuse device needs to be added and the fuse is easy to fuse when the large capacitor exists in the output in the traditional solution.
The technical scheme of the invention is as follows:
the output short-circuit protection method of the boost converter comprises an inductor, a first switching tube and a freewheeling diode, wherein one end of the inductor is connected with the input end of the boost converter, and the other end of the inductor is connected with the output end of the boost converter after passing through the freewheeling diode; the first switch tube is connected between the connection point of the inductor and the freewheeling diode and the ground;
the output short-circuit protection method of the boost converter comprises the following steps: a second switching tube is arranged between the freewheeling diode and the output end of the boost converter, and a parasitic diode of the second switching tube is reversely biased; sampling the output voltage of the boost converter, connecting the output voltage to a negative input end of a first transconductance amplifier, sampling the current flowing through the second switching tube, and connecting the current to a negative input end of a second transconductance amplifier, wherein a positive input end of the first transconductance amplifier is connected with a first reference voltage, and a positive input end of the second transconductance amplifier is connected with a second reference voltage; selecting a lower signal of the output signal of the first transconductance amplifier and the output signal of the second transconductance amplifier as a grid control signal of the second switching tube;
after the input end of the boost converter is connected with an input power supply, the voltage signal at the joint of the freewheeling diode and the second switching tube gradually rises until reaching the threshold voltage, and the second switching tube keeps a turn-off state in the process; when the voltage signal at the connection position of the freewheeling diode and the second switching tube rises to the threshold voltage, controlling the rising speed of the output voltage of the boost converter by controlling the rising speed of the first reference voltage, and controlling the output current of the boost converter by sampling the current flowing through the second switching tube;
the specific method for controlling the output current of the boost converter comprises the following steps:
A. after the voltage signal at the joint of the freewheeling diode and the second switching tube rises to reach the threshold voltage, when the output of the boost converter is short-circuited, sampling the current flowing through the second switching tube to obtain a signal exceeding the second reference voltage, and turning to the step B;
B. selecting an output signal of a second transconductance amplifier to control the grid-source voltage of the second switching tube so as to limit the output current of the boost converter and simultaneously generate an overcurrent state signal;
C. after the overcurrent state signal maintains the first set time, the second switching tube is controlled to be switched off;
D. opening the second switching tube after the off state of the second switching tube is maintained for a second set time, judging whether a signal obtained by sampling current flowing through the second switching tube still exceeds the second reference voltage, if so, turning to the step B, otherwise, turning to the step E;
E. at this time, the output of the boost converter is recovered to the normal working state from the short-circuit state, and the output short-circuit protection is quitted.
Specifically, the initial value of the first reference voltage is zero, and when the voltage signal at the junction between the freewheeling diode and the second switching tube rises to the threshold voltage, the first reference voltage starts to rise slowly from the zero value, so that the output voltage of the boost converter rises slowly.
Specifically, when the voltage signal at the junction of the freewheeling diode and the second switching tube rises to reach the threshold voltage, the first reference voltage rises at a rate of 100 mV/mS.
Specifically, the second reference voltage is a fixed value, and the voltage value of the second reference voltage is set according to an overcurrent threshold of the output current of the boost converter.
Specifically, the output signal of the first transconductance amplifier and the output signal of the second transconductance amplifier are respectively connected to two input ends of a low value selector, and an output end of the low value selector is connected to a gate of the second switching tube.
Specifically, the grid of the second switch tube is further connected with the output end of a charge pump, and the charge pump is used for ensuring that the second switch tube can be opened.
The invention has the beneficial effects that: according to the invention, the overcurrent and short-circuit states are determined by sampling the current on the second switching tube M2 and the output voltage of the BOOST, and corresponding response is made by logic design in combination with the loop control of the transimpedance amplifier, so that after the PMID voltage rises to the threshold voltage, the loop is controlled by using the first transconductance amplifier gm1 to enable the BOOST output voltage to follow the first reference voltage VREF1The output voltage rises slowly, and when the output is short-circuited, the second transconductance amplifier gm2 is used for controlling a loop to adjust the output current, so that the current is prevented from being overlarge in the rising process of the output voltage, and the problem that the current cannot be controlled when the boost converter outputs overcurrent and short-circuit or drives a large capacitor is solved; according to the invention, only one second switching tube M2 and the parasitic diode D2 are added in the boost converter, so that the boost converter can be integrated in a chip, and the system volume is not increased.
Drawings
Fig. 1 is a block diagram of a conventional boost converter.
Fig. 2 is a schematic diagram of a conventional solution in which a fuse is added to a boost converter.
Fig. 3 is a schematic block diagram of an isolation tube added in a boost converter in the method for protecting an output short circuit of the boost converter according to the present invention.
Fig. 4 is a logic control block diagram of an isolation tube in the output short-circuit protection method of the boost converter according to the present invention.
Fig. 5 is a voltage waveform diagram of a boost converter adopting the output short-circuit protection method of the present invention in normal operation.
Fig. 6 is a diagram of operating voltage waveforms of a boost converter employing the output short-circuit protection method of the present invention at the time of an output short-circuit.
Detailed Description
The technical scheme of the invention is explained in detail in the following by combining the drawings and the specific embodiment.
As shown in FIG. 3, the present invention provides an isolation tube, i.e. a second switch tube M2, between a freewheeling diode D1 in the conventional boost converter and the output terminal of the boost converter, D2 is a parasitic diode of the second switch tube M2, due to the addition of the second switch tube M2, a reverse biased diode D2 and a second switch tube M2 are added to the path from the freewheeling diode D1 to the output terminal, and the path between the input and the output is cut off, and the present invention also combines the logic control of the second switch tube M2, realizes the output overcurrent and short-circuit protection by controlling the second switch tube M2, and controls the output voltage V2 at the same timeOUTThe working process of the present invention will be described in detail with reference to the accompanying drawings.
As shown in fig. 4, the current flowing through the second switching tube M2 and the output voltage V of the boost converter are sampled respectivelyOUTTo determine the over-current and short-circuit state and respond accordingly, the output voltage V of the boost converter can be sampled by adopting a resistance voltage division modeOUTAnd the sampled signal is connected to the negative input terminal of the first transconductance amplifier gm1, and the positive input terminal of the first transconductance amplifier gm1 is connected to the first reference voltage VREF1. Sampling the current flowing through the second switching tube M2The obtained signal is connected to the negative input terminal of the second transconductance amplifier gm2, and the positive input terminal of the second transconductance amplifier gm2 is connected to the second reference voltage VREF2. The output signals of the first transconductance amplifier gm1 and the second transconductance amplifier gm2 are connected to two input terminals of a selector MUX, respectively, which is a low value selector for exceeding a first reference voltage V at the sample value of the output voltageREF1Or the sampled value of the output current exceeds the second reference voltage VREF2In this case, the low value selector selects the lower signal output of the output signal of the first transconductance amplifier gm1 and the output signal of the second transconductance amplifier gm2 as the gate control signal of the second switching transistor M2, the transconductance amplifier is used for loop control, and the second transconductance amplifier gm2 is further used for generating the over-current status signal OCP _ STATE for over-current protection. Since the second switch transistor M2 is an NMOS transistor, and the gate voltage is greater than the source voltage when the second switch transistor M2 is turned on, a Charge Pump (Charge Pump) is usually configured to generate a voltage greater than the source voltage for providing a driving voltage for turning on the second switch transistor M2, as shown in fig. 4.
As shown in fig. 5 and 6, when the input signal is switched in, phase 1: the PMID voltage (i.e. the voltage signal at the junction of the freewheeling diode D1 and the second switch tube M2) rises to VIN-0.7V (where 0.7V is the forward conduction voltage of one diode) due to the presence of the freewheeling diode D1 in the parasitic path, the second switch tube M2 is in a closed state, and the output voltage V isOUTIf the BOOST output is in a short-circuit state at this time, since the second switch M2 is turned off and the diode D2 is reversely biased, the PMID voltage has no current path to the output, and therefore, a large current is not generated on the chip.
And (2) stage: with the start of BOOST, the duty ratio of the first switch tube M0 and the second switch tube M2 is controlled to enable the PMID voltage to gradually rise, before the PMID voltage rises to reach the BOOST set threshold, the second switch tube M2 is always kept in a closed state in the whole process, no path exists between the output and the input, the chip current is controllable, and the risk of burnout does not exist.
And (3) stage: when the PMID voltage completely rises to the BOOST set threshold, the second switch tube M2 is controlled to be connectedA first reference voltage V across the forward input of the transconductance amplifier gm1REF1The first transconductance amplifier gm1 is used for controlling the output voltage, and the first reference voltage V is used for controlling the rising speed of the output voltage of the boost converterREF1Is zero, and when the PMID voltage is completely raised to the BOOST set threshold value, the first reference voltage VREF1Slowly rises from zero value so that the output voltage of the boost converter follows the first reference voltage VREF1Slowly rising, e.g. controlling the first reference voltage V in some embodimentsREF1Slowly increasing at a rate of 100 mV/mS.
Simultaneously, the current on the second switching tube M2 is sampled, the sampled signal is connected with the second transconductance amplifier gm2, and the second transconductance amplifier gm2 is used for controlling the output current, wherein the specific control method comprises the following steps: the output current is sampled by a second switch tube M2, and the sampling signal exceeds a set second reference voltage VREF2Then, the output current is limited by controlling the gate terminal of the second switching tube M2 through a second transconductance amplifier gm2, which is an amplifier that converts the input differential voltage into the output current and is used for loop control, and the output signal of the second transconductance amplifier gm2 controls the current of the second switching tube M2 by controlling the gate-source voltage of the second switching tube M2, so as to limit the output current of the boost converter. Second reference voltage VREF2Is a fixed threshold whose magnitude depends on the magnitude of the output current to be controlled. The signal of the second switch tube M2 sampling the output current exceeds the set second reference voltage VREF2An over-current STATE signal OCP _ STATE is also generated, the over-current STATE signal OCP _ STATE is combined with Hiccup (Hiccup) logic to control the second switch tube M2 to be turned off, which is specifically shown in that the second switch tube M2 is turned off after the over-current STATE signal OCP _ STATE is generated and maintained for a first set time, the second switch tube M2 is turned on after the second switch tube M2 is turned off and maintained for a second set time, and whether the signal of the second switch tube M2 sampling the output current still exceeds a set second reference voltage VREF2If yes, the output signal of the second transconductance amplifier gm2 is used to control the current of the second switch tube M2 to limit the boosting voltageThe output current of the inverter is maintained for the first set time, then the second switching tube M2 is turned off, and the above process is repeated; until the signal sampled by the second switch tube M2 for the output current does not exceed the set second reference voltage VREF2When the over-current STATE signal OCP _ STATE is not generated any more, which indicates that the BOOST is recovered to the normal STATE from the output short-circuit STATE, the output voltage V of the BOOST isOUTAnd recovering to normal voltage, and carrying out normal load of the BOOST to realize output short-circuit protection.
The first set time and the second set time are both set in the chip, the first set time is set to ensure that the normal starting can be realized when the load capacitor Cload is larger, the second set time is set to prevent the switch MOS tube from generating heat seriously under the constant current state for a long time, and the second set time is set for safety.
In summary, the overcurrent and short-circuit conditions are determined by sampling the current of the second switch tube M2 and the output voltage of the BOOST, so that the corresponding response is made and the chip is not damaged. The second switch tube M2 is in the off state in the PMID voltage rising process, when the PMID rises to the BOOST set threshold, the second switch tube M2 is controlled by the first transconductance amplifier gm1 or the second transconductance amplifier gm2 in a loop mode, the first transconductance amplifier gm1 controls the output voltage, and the BOOST output voltage follows the first reference voltage V through controlling the second switch tube M2REF1Slowly rising; meanwhile, the second transconductance amplifier gm2 is used for controlling the current flowing through the second switch tube M2 to control the output current, so that the current is prevented from being overlarge in the rising process of the output voltage, when the output is short-circuited, because the current on the second switch tube M2 is controlled, after overcurrent protection (OCP) is triggered, the short-circuit state is exited by combination of hiccup (hiccup) logic control, and the BOOST is enabled to recover normal work.
Those skilled in the art can make various other specific changes and combinations based on the teachings of the present invention without departing from the spirit of the invention, and these changes and combinations are within the scope of the invention.
Claims (6)
1. The output short-circuit protection method of the boost converter comprises an inductor, a first switching tube and a freewheeling diode, wherein one end of the inductor is connected with the input end of the boost converter, and the other end of the inductor is connected with the output end of the boost converter after passing through the freewheeling diode; the first switch tube is connected between the connection point of the inductor and the freewheeling diode and the ground;
the output short-circuit protection method of the boost converter is characterized by comprising the following steps: a second switching tube is arranged between the freewheeling diode and the output end of the boost converter, and a parasitic diode of the second switching tube is reversely biased; sampling the output voltage of the boost converter, connecting the output voltage to a negative input end of a first transconductance amplifier, sampling the current flowing through the second switching tube, and connecting the current to a negative input end of a second transconductance amplifier, wherein a positive input end of the first transconductance amplifier is connected with a first reference voltage, and a positive input end of the second transconductance amplifier is connected with a second reference voltage; selecting a lower signal of the output signal of the first transconductance amplifier and the output signal of the second transconductance amplifier as a grid control signal of the second switching tube;
after the input end of the boost converter is connected with an input power supply, the voltage signal at the joint of the freewheeling diode and the second switching tube gradually rises until reaching the threshold voltage, and the second switching tube keeps a turn-off state in the process; when the voltage signal at the connection position of the freewheeling diode and the second switching tube rises to the threshold voltage, controlling the rising speed of the output voltage of the boost converter by controlling the rising speed of the first reference voltage, and controlling the output current of the boost converter by sampling the current flowing through the second switching tube;
the specific method for controlling the output current of the boost converter comprises the following steps:
A. after the voltage signal at the joint of the freewheeling diode and the second switching tube rises to reach the threshold voltage, when the output of the boost converter is short-circuited, sampling the current flowing through the second switching tube to obtain a signal exceeding the second reference voltage, and turning to the step B;
B. selecting an output signal of a second transconductance amplifier to control the grid-source voltage of the second switching tube so as to limit the output current of the boost converter and simultaneously generate an overcurrent state signal;
C. after the overcurrent state signal maintains the first set time, the second switching tube is controlled to be switched off;
D. opening the second switching tube after the off state of the second switching tube is maintained for a second set time, judging whether a signal obtained by sampling current flowing through the second switching tube still exceeds the second reference voltage, if so, turning to the step B, otherwise, turning to the step E;
E. at this time, the output of the boost converter is recovered to the normal working state from the short-circuit state, and the output short-circuit protection is quitted.
2. A method as claimed in claim 1, wherein the initial value of the first reference voltage is zero, and when the voltage signal at the junction of the freewheeling diode and the second switching tube rises to the threshold voltage, the first reference voltage slowly rises from zero, so that the output voltage of the boost converter slowly rises.
3. The method of claim 2, wherein the first reference voltage rises at 100mV/mS when the voltage signal at the junction of the freewheeling diode and the second switching tube rises to reach the threshold voltage.
4. A method as claimed in any one of claims 1 to 3, wherein the second reference voltage is a fixed value, and the voltage value is set according to an overcurrent threshold of the output current of the boost converter.
5. The output short-circuit protection method of a boost converter according to claim 4, wherein the output signal of the first transconductance amplifier and the output signal of the second transconductance amplifier are respectively connected to two input terminals of a low value selector, and an output terminal of the low value selector is connected to the gate of the second switching tube.
6. The output short-circuit protection method of a boost converter according to claim 1 or 5, wherein the gate of the second switch tube is further connected to the output end of a charge pump, and the charge pump is used to ensure that the second switch tube can be turned on.
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| CN113541488B (en) * | 2021-06-28 | 2022-09-06 | 中车青岛四方机车车辆股份有限公司 | Boost chopper circuit, protection circuit, control method, equipment and vehicle |
| TWI807977B (en) * | 2022-08-26 | 2023-07-01 | 立錡科技股份有限公司 | Switching regulator and control circuit and control method thereof |
| CN117013836B (en) * | 2023-09-11 | 2024-01-12 | 深圳市微源半导体股份有限公司 | Voltage conversion circuit and power supply system |
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| US5726845A (en) * | 1996-02-28 | 1998-03-10 | Astec International Limited | Short circuit protection for power factor correction circuit |
| US6985341B2 (en) * | 2001-04-24 | 2006-01-10 | Vlt, Inc. | Components having actively controlled circuit elements |
| KR100476202B1 (en) * | 2002-06-25 | 2005-03-10 | 현대자동차주식회사 | A method for preventing and diagnosing an arm-short of bi-directional dc/dc converter |
| CN101753003B (en) * | 2008-12-05 | 2014-04-09 | 立锜科技股份有限公司 | Protective device and method of boost converter |
| CN102570809B (en) * | 2010-12-31 | 2016-02-24 | 意法半导体研发(深圳)有限公司 | Short-circuit protection circuit and method |
| CN103746342B (en) * | 2014-01-10 | 2016-09-21 | 成都芯源系统有限公司 | Boost converter, controller for boost converter and short-circuit protection method |
| US11031796B2 (en) * | 2016-05-25 | 2021-06-08 | Dialog Semiconductor Inc. | Short circuit and soft short protection for data interface charging |
| CN106786396B (en) * | 2017-01-16 | 2019-01-08 | 广东百事泰电子商务股份有限公司 | A kind of amendment wave inverter intelligent type protective switch of the short circuit circuit |
| CN112534668B (en) * | 2018-04-10 | 2023-09-29 | 德州仪器公司 | Boost converter short circuit protection |
| US11079443B2 (en) * | 2018-12-21 | 2021-08-03 | Analog Devices International Unlimited Company | Switch fault detection techniques for DC-DC converters |
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