CN108923658B - LLC resonant converter - Google Patents

LLC resonant converter Download PDF

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Publication number
CN108923658B
CN108923658B CN201810744843.0A CN201810744843A CN108923658B CN 108923658 B CN108923658 B CN 108923658B CN 201810744843 A CN201810744843 A CN 201810744843A CN 108923658 B CN108923658 B CN 108923658B
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switch tube
switch
bridge arm
transformer
diode
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CN108923658A (en
Inventor
于磊
张宝英
王双
谷文旗
金言
谢旭
付启
韩宇龙
米春泉
张蕾
王阳
王满帅
李云
王祖光
王川
范华
何涛
穆亮
路建敏
孙丽娜
朱梅
王延平
王永星
孟玲梅
孙孝峰
郑智文
贾磊磊
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State Grid Corp of China SGCC
Yanshan University
KME Sp zoo
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State Grid Corp of China SGCC
Yanshan University
KME Sp zoo
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses an LLC resonant converter, which comprises a power supply input end, a first switch bridge arm, a resonant network, a second switch bridge arm, a rectification output circuit and a load output end, wherein two ends of the first switch bridge arm are connected with the power supply input end, and the midpoint of the first switch bridge arm is connected with one end of the resonant network; the other end of the resonant network is connected with the midpoint of the second switch bridge arm; one end of the second switch bridge arm is connected with the negative electrode of the power supply input end, the other end of the second switch bridge arm is connected with the output end of the rectification output circuit, and the load output end is connected with the rectification output circuit. The invention has simple structure and can realize the wide voltage input to supply power for the load under narrow frequency. The invention is suitable for any load needing stable high-voltage direct current power supply.

Description

LLC resonant converter
Technical Field
The invention belongs to the field of load power supply, and relates to a converter for providing stable direct current for application, in particular to an LLC resonant converter.
Background
At present, a power battery for supplying power to a load has the characteristics of high output voltage and wide range, for example, the output voltage of a lithium battery is generally 200-400V. However, most communication systems, UPS, DC motors and the like require a stable high-voltage DC power supply, so a wide-voltage DC/DC converter must be connected behind the lithium battery to provide stable DC power to the load. Therefore, a unidirectional DC/DC converter with high efficiency suitable for wide voltage range input needs to be researched.
In the prior art, the LLC converter has the advantages of easy soft switching and high transmission efficiency, and is therefore widely used in switching power supplies. However, how to increase the voltage range of the LLC converter in the load power supply so as to provide high-voltage direct current for the load is the focus of current research.
Disclosure of Invention
In order to solve the above disadvantages in the prior art, the present invention aims to provide an LLC resonant converter to improve the voltage range of the LLC converter.
In order to achieve the purpose, the technical scheme adopted by the invention is as follows:
an LLC resonant converter comprises a power supply input end, a first switch bridge arm, a resonant network, a second switch bridge arm, a rectification output circuit and a load output end, wherein two ends of the first switch bridge arm are connected with the power supply input end, and the midpoint of the first switch bridge arm is connected with one end of the resonant network; the other end of the resonant network is connected with the midpoint of the second switch bridge arm; one end of the second switch bridge arm is connected with the negative electrode of the power supply input end, the other end of the second switch bridge arm is connected with the output end of the rectification output circuit, and the load output end is connected with the output end of the rectification output circuit.
As a limitation of the present invention: the first switch bridge arm and the second switch bridge arm are both half-bridge power switch tube structures, the first switch bridge arm comprises a first switch tube and a second switch tube which are connected in series, the second switch bridge arm comprises a third switch tube and a fourth switch tube which are connected in series, the frequencies from the first switch tube to the fourth switch tube are the same, the duty ratio is 0.5, the phases of the first switch tube and the third switch tube are the same, the phases of the second switch tube and the fourth switch tube are the same, and the phase difference between the first switch tube and the second switch tube is 180 degrees.
As a limitation of the resonant network of the present invention: the resonance network comprises a resonance inductor, a transformer primary side and a resonance capacitor which are sequentially connected in series.
As a limitation of the rectification output circuit of the present invention: the rectification output circuit comprises a secondary side of a transformer with a middle tap, and a first diode and a second diode which are connected in parallel; one end of the first diode is connected with one end of the secondary side of the transformer, one end of the second diode is connected with the other end of the secondary side of the transformer, the other ends of the first diode and the second diode, which are not connected with the secondary side of the transformer, are connected with one end of the load output end, and the other end of the load output end is connected with a tap on the secondary side of the transformer.
As a limitation of the transformer of the present invention: and the tap on the negative side of the transformer is positioned in the center of the secondary side of the transformer.
As a further limitation of the transformer of the present invention: and the tap on the negative side of the transformer is positioned in the center of the secondary side of the transformer.
As a final limitation to the invention: the first switch tube, the second switch tube, the third switch tube and the fourth switch tube are one of MOSFET power tubes, IGBT power tubes and GTO power tubes.
Due to the adoption of the technical scheme, compared with the prior art, the invention has the following beneficial effects:
in the invention, a first switch bridge arm is formed by a first switch tube S1 and a second switch tube S2, and a second switch bridge arm is formed by a third switch tube S3 and a fourth switch tube S4.
In the invention, the first switch tube S1 to the fourth switch tube S4 all adopt power transistors, the frequencies are the same, the duty ratios are all 0.5, the phases of the first switch tube S1 and the third switch tube S3 are the same, the phases of the second switch tube S2 and the fourth switch tube S4 are the same, the phase difference between the first switch tube S1 and the second switch tube S2 is 180 degrees, and the on-off of the first switch tube S1 to the fourth switch tube S4 can be controlled, so that when the input voltage is smaller, the gain of the LLC converter is approximate to the gain of a full-bridge LLC converter; when the input voltage is larger, the gain of the LLC converter is approximate to that of a half-bridge LLC converter, so that the LLC converter can realize wide voltage input at narrow frequency;
the invention can realize zero voltage switching-on (ZVS) of the power switch tube and zero current switching-off (ZCS) of the rectifier diode.
In conclusion, the invention has simple structure and can realize the wide voltage input to supply power for the load under narrow frequency.
The invention is suitable for any load needing stable high-voltage direct current power supply.
Drawings
The invention is described in further detail below with reference to the figures and the embodiments.
FIG. 1 is a schematic diagram of an electrical configuration of an embodiment of the present invention;
FIG. 2 is a waveform diagram of simulation according to an embodiment of the present invention;
FIG. 3a is a schematic diagram of an embodiment of the present inventiont 0～t 1An equivalent circuit diagram of a stage;
FIG. 3b shows an embodiment of the present inventiont 1～t 3An equivalent circuit diagram of a stage;
FIG. 3c shows an embodiment of the present inventiont 3～t 4An equivalent circuit diagram of a stage;
FIG. 3d shows an embodiment of the present inventiont 4～t 5An equivalent circuit diagram of a stage;
FIG. 4a is an equivalent circuit diagram of FIG. 3 a;
FIG. 4b is an equivalent circuit diagram of FIG. 3 b;
FIG. 4c is an equivalent circuit diagram of FIG. 3 c;
FIG. 5 is a waveform of an experimental portion of an embodiment of the present invention;
FIG. 6 is a soft switching waveform of an embodiment of the present invention;
fig. 7 shows a comparison of the gain of an embodiment of the present invention with the waveforms of half-bridge LLC gain and full-bridge LLC gain.
Detailed Description
Example LLC resonant converter
The present embodiment is shown in fig. 1, and includes:
① power supply input terminal.
② A first switch bridge arm connected to two ends of the power input end, including a first switch tube S1 and a second switch tube S2 connected in series, wherein the first switch tube S1 is connected to the positive pole of the power input end, and the second switch tube S2 and the negative pole of the power input end are grounded together.
③ a second switch bridge arm, including a third switch tube S3 and a fourth switch tube S4 connected in series in sequence, wherein one end of the third switch tube S3 not connected with the fourth switch tube S4 is grounded.
④ resonant network, which comprises a resonant inductor Lr, a primary winding of a transformer T, and a resonant capacitor Cr connected in series in turn, wherein the free end of the resonant inductor Lr is used as one end of the resonant network to connect with the midpoint of the first switch bridge arm, and the free end of the resonant capacitor Cr is used as the other end of the resonant network to connect with the midpoint of the two switch bridge arms.
⑤ rectification output circuit, which comprises a secondary winding of transformer T, a first diode D1, a second diode D2, wherein the secondary winding of transformer T has a tap, the tap is located at the center of the secondary winding, the first diode D1 is connected with the cathode of the second diode D2 and then connected with one end of the fourth switch tube S4 which is not connected with the third switch tube S3, the anode of the first diode D1 is connected with one end of the secondary winding of transformer T, and the anode of the second diode D2 is connected with the other end of the secondary winding of transformer T.
⑥ load output terminal, which includes a capacitor C and a resistor R connected in parallel, one end of the load output terminal is connected to the cathodes of the first diode D1 and the second diode D2, and the other end is connected to the middle tap of the secondary winding of the transformer T.
In the above structure, the first switch tube S1 to the fourth switch tube S4 are all power switch tube structures in the prior art, such as MOSFET power tubes, IGBT power tubes or GTO power tubes in the prior art. The frequencies of the first switching tube S1 to the fourth switching tube S4 are the same, and the duty ratios are all 0.5; the phase of the first switch tube S1 is the same as the phase of the third switch tube S3, the phase of the second switch tube S2 is the same as the phase of the fourth switch tube S4, and the phase of the first switch tube S1 is 180 ° different from the phase of the second switch tube S2.
Lm in figure 1 is equivalent excitation inductance i of transformerLrCurrent, i, of resonant inductor LrLmTo excite the current of inductance Lm, ucrThe voltage at two ends of the resonance capacitor Cr, Vtrank is the voltage of the resonance tank iDO1Is the current through the first diode D1, iDO2Is the current flowing through the second diode D2. To better describe this embodiment, as shown in FIG. 2, the working process of this embodiment is divided into 0 to t9The pairs of fig. 3a to 3d are schematic diagrams of the specific operating circuit of the present embodiment at different stages, and the dotted line represents that the current does not flow through the circuit at the stage, so the operating principle at each stage is analyzed in detail with reference to fig. 3a to 3 d.
Stage one (t)0～t1): as shown in FIG. 3a, t0At the moment, the dead time is over, the first switch tube S1 and the third switch tube S3 are conducted, and the current i is in the resonant inductorLrIs a negative value, iLrStarts to decrease in absolute value, has a value of iLm-iLrIs passed through a transformer T to a transformerOn the secondary side of the device T, the first diode D1 is turned on, the magnetizing inductor Lm is clamped and does not participate in resonance, and the equivalent circuit is shown in fig. 4 a. The resonant frequency at this stage is fr, and the secondary energy of the transformer T is provided by the resonant inductor Lr. Before that, the resonant current flows through the anti-parallel diodes of the first switching tube S1 and the third switching tube S3, and the first switching tube S1 and the third switching tube S3 implement ZVS.
Stage two (t)1～t2): as shown in FIG. 3b, t1Time, iLrDecreases to 0 and rises in the forward direction, starts to flow through the first switching tube S1, and the magnitude of the current flowing through the transformer T becomes iLm+iLrThe first diode D1 continues to conduct, the magnetizing inductance Lm is clamped and does not participate in resonance, and the equivalent circuit is as shown in fig. 4 b. The resonant frequency at this stage is fr and the secondary energy of the transformer T is provided by the input power.
Stage three (t)2～t3): still as shown in FIG. 3b, iLrMaintaining the direction unchanged at t2Time, iLmCommutation, the exciting inductor Lm in charged state and exciting current iLmGradually increases, and the magnitude of the current flowing through the transformer T becomes iLr-iLmAt t3Time, iLmIs equal to iLrAt this time, the primary side of the transformer T has no current, the secondary side outputs a current of 0, and the current flowing through the two diodes is 0, so as to implement ZCS, and the equivalent circuit is shown in fig. 4 b. At this stage, the resonant frequency is fr, and the secondary energy of the transformer T is still provided by the input power.
Stage four (t)3～t4): at this stage i is shown in FIG. 3cLrAnd iLmKeeping the primary side of the transformer T equal, keeping the primary side of the transformer equal, enabling the exciting inductor Lm to be separated from clamping and participate in resonance, enabling the resonance frequency to be fm, enabling load energy to be provided by the filter capacitor C, and enabling the voltage at two ends of the second switching tube S2 to be input voltage V during the period that the first switching tube S1 and the second switching tube S3 are conductediAnd the voltage across the fourth switching tube S4 is the output voltage Vo, and the equivalent circuit refers to fig. 4 c.
Stage five (t)4～t5): as shown in FIG. 3d, this embodiment enters the dead band, first switchThe transistors S1 to S4 are all turned off, the parasitic capacitances Coss2 and Coss4 of the second switch transistor S2 and the fourth switch transistor S4 discharge and then charge in the reverse direction until the diodes of the second switch transistor S2 and the fourth switch transistor S4 conduct, and simultaneously the parasitic capacitances Coss1 and Coss3 of the first switch transistor S1 and the third switch transistor S3 start to charge to the input voltage Vi and the output voltage Vo. The resonant frequency at this stage is fm, and the load energy is provided by the filter capacitor.
The next half cycle of this embodiment (i.e., t)5～t9Phase) is similar to the first half cycle, except that the filter capacitor C serves the role of the input power supply.
In order to facilitate understanding of the stages, the operation mode of the resonant tank of the present embodiment is divided into three stages regardless of the dead zone condition according to whether the switching mode of the first switching tube S1 to the fourth switching tube S4 and the excitation inductance Lm participate in resonance, and a time domain equation expression is calculated.
The equivalent models of stage one, stage two and stage three are shown in fig. 3a, and the time domain equation expression is as follows:
Figure RE-611294DEST_PATH_IMAGE001
in the formula, angular frequency
Figure RE-325172DEST_PATH_IMAGE002
Characteristic impedance
Figure RE-449117DEST_PATH_IMAGE003
N is the primary and secondary turn ratio of the transformer, Vi is the input voltage, Vo is the output voltage,
Figure RE-375485DEST_PATH_IMAGE004
。
the equivalent model of stage four is shown in fig. 3b, and the time domain equation expression is as follows:
Figure RE-970283DEST_PATH_IMAGE005
in the formula, angular frequency
Figure RE-58325DEST_PATH_IMAGE006
Characteristic impedance
Figure RE-856516DEST_PATH_IMAGE007
，
Figure RE-586575DEST_PATH_IMAGE008
。
The lower half period t5-t8The time period model is shown in fig. 3-c, and the time domain equation expression is as follows:
Figure RE-786612DEST_PATH_IMAGE009
to this LLC converter, the input voltage
Figure RE-61867DEST_PATH_IMAGE010
Ratio of excitation inductance to resonance inductance
Figure RE-347355DEST_PATH_IMAGE011
Quality factor of
Figure RE-615525DEST_PATH_IMAGE012
Frequency of resonance
Figure RE-670069DEST_PATH_IMAGE013
The transformer transformation ratio is 4:3, the output voltage is stable at 240V, the switching frequency is changed within the range of 43KHz-60KHz, and the switching frequency is changed to 17 KHz. Whereas the conventional LLC frequency translates to 61.02 KHz.
FIG. 5 shows a part of experimental waveforms of 400V input voltage, 240V output voltage and 1kW power according to the embodiment of the present invention, where the waveforms include, from top to bottom, a driving signal of the first switching tube S1 and a voltage V of the resonant tanktankAnd a resonant current iLrAt this time, the frequencies of the first switch tube S1 to the fourth switch tube S4 are 60kHz and equal to the resonant frequency fr。
FIG. 6 shows an embodiment of the present invention with an input voltage of 400V and an output voltage of 240VV, a soft switching waveform with the power of 1kW, and the driving signals V2 and V3 of the second switching tube S2 and the third switching tube S3 are measured respectively due to symmetrygsAnd drain-source voltage VdsTherefore, the soft switching can be judged.

Claims (6)

1. An LLC resonant converter, characterized in that: the power supply comprises a power supply input end, a first switch bridge arm, a resonant network, a second switch bridge arm, a rectification output circuit and a load output end, wherein two ends of the first switch bridge arm are connected with the power supply input end, and the middle point of the first switch bridge arm is connected with one end of the resonant network; the other end of the resonant network is connected with the midpoint of the second switch bridge arm; one end of the second switch bridge arm is connected with the negative electrode of the power supply input end, the other end of the second switch bridge arm is connected with the output end of the rectification output circuit, and the load output end is connected with the output end of the rectification output circuit.
2. The LLC resonant converter of claim 1, wherein: the first switch bridge arm and the second switch bridge arm are both half-bridge power switch tube structures, the first switch bridge arm comprises a first switch tube and a second switch tube which are connected in series, the second switch bridge arm comprises a third switch tube and a fourth switch tube which are connected in series, the switching frequencies of the first switch tube to the fourth switch tube are the same, the duty ratios of the first switch tube to the fourth switch tube are 0.5, the phases of the first switch tube and the third switch tube are the same, the phases of the second switch tube and the fourth switch tube are the same, and the phase difference between the first switch tube and the second switch tube is 180 degrees.
3. The LLC resonant converter of claim 2, wherein: the resonance network comprises a resonance inductor, a transformer primary side and a resonance capacitor which are sequentially connected in series.
4. The LLC resonant converter of claim 3, wherein: the rectification output circuit comprises a secondary side of a transformer with a middle tap, and a first diode and a second diode which are connected in parallel; one end of the first diode is connected with one end of the secondary side of the transformer, one end of the second diode is connected with the other end of the secondary side of the transformer, the other ends of the first diode and the second diode, which are not connected with the secondary side of the transformer, are connected with one end of the load output end, and the other end of the load output end is connected with a tap on the secondary side of the transformer.
5. The LLC resonant converter of claim 4, wherein: and the tap on the secondary side of the transformer is positioned in the center of the secondary side of the transformer.
6. LLC resonant converter according to any of claims 2-5, characterized in that: the first switch tube, the second switch tube, the third switch tube and the fourth switch tube are one of MOSFET power tubes, IGBT power tubes and GTO power tubes.
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Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2013106692A1 (en) * 2012-01-13 2013-07-18 Power-One, Inc. Resonant converter with auxiliary resonant components and holdup time control circuitry
CN104756385A (en) * 2012-10-31 2015-07-01 麻省理工学院 Systems and methods for a variable frequency multiplier power converter
WO2015136097A1 (en) * 2014-03-14 2015-09-17 Eisergy Limited A switched mode ac-dc converter
CN106100344A (en) * 2016-07-05 2016-11-09 陕西科技大学 A kind of LLC resonant converter with liter high voltage gain
WO2017049179A1 (en) * 2015-09-18 2017-03-23 Murata Manufacturing Co., Ltd. Converters with hold-up operation

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2013166579A1 (en) * 2012-05-10 2013-11-14 Arda Power Inc. Dc-dc converter circuit using an llc circuit in the region of voltage gain above unity

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2013106692A1 (en) * 2012-01-13 2013-07-18 Power-One, Inc. Resonant converter with auxiliary resonant components and holdup time control circuitry
CN104756385A (en) * 2012-10-31 2015-07-01 麻省理工学院 Systems and methods for a variable frequency multiplier power converter
WO2015136097A1 (en) * 2014-03-14 2015-09-17 Eisergy Limited A switched mode ac-dc converter
WO2017049179A1 (en) * 2015-09-18 2017-03-23 Murata Manufacturing Co., Ltd. Converters with hold-up operation
CN106100344A (en) * 2016-07-05 2016-11-09 陕西科技大学 A kind of LLC resonant converter with liter high voltage gain

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