CN104852590A - Novel three-level logical link control (LLC) resonant converter - Google Patents
Novel three-level logical link control (LLC) resonant converter Download PDFInfo
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
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Abstract
The invention relates to a novel three-level logical link control (LLC) resonant converter which comprises an input dividing capacitor, a switch bridge arm, a resonant cavity, a transformer and a rectification filter circuit, wherein the input dividing capacitor is formed by two capacitors which are connected in series, and the other ends of the two capacitors are respectively connected with the positive pole of a power supply; the switch bridge arm is formed by sequentially connecting drain-source electrodes of four switching tubes provided with body diodes in series; the drain-source electrodes of the switching tubes arranged at the two ends of the switch bridge arm are respectively connected with the positive pole and the negative pole of the power supply; a middle connecting point of the two middle switching tubes is connected with that of the two capacitors; the resonant cavity consists of an inductor, a capacitor and an excitation inductor which are sequentially connected in series; the other end of the inductor is connected with a middle connecting point of the first switching tube and the second switching tube; the other end of the excitation inductor is connected with a middle connecting point of the third switching tube and the fourth switching tube; the primary side of the transformer is connected with the excitation inductor in parallel, and the secondary side of the transformer is connected with the input end of the rectification filter circuit. After the novel three-level LLC resonant converter is used, the circuit structure is simplified, power devices are reduced, the cost is lowered, and the system reliability is improved.
Description
Technical field
The present invention relates to a kind of controlled resonant converter, be specifically related to a kind of novel three-level LLC resonance inverter.
Background technology
Controlled resonant converter has the advantages such as switching frequency is high, switching loss is little, efficiency is high, quality is light, volume is little, EMI noise is little, switch stress is little.LLC resonant converter has former limit metal-oxide-semiconductor and easily realizes full-load range ZVS, and secondary diode easily realizes ZCS, and resonant inductance and transformer easily realize the advantages such as magnetic is integrated, are widely used in recent years.Meanwhile, be elementary metal-oxide-semiconductor voltage stress high problem under solution high input voltage occasion, three level be incorporated in LLC converter.Traditional three-level LLC resonance inverter needs Yin Ru Clamp-on position diode to realize metal-oxide-semiconductor voltage stress to be restricted to input voltage half, can select the metal-oxide-semiconductor of relative low voltage specification like this.The introducing of Dan Clamp-on position diode adds cost, and circuit is more complicated simultaneously.
Summary of the invention
In order to solve above-mentioned prior art Problems existing, the object of the present invention is to provide a kind of novel three-level LLC resonance inverter, by the control to switching tube each in converter, the body diode making full use of topological circuit breaker in middle pipe in control procedure realizes switch tube both end voltage Clamp-on position, reaches the object reducing switch tube voltage stress; Compared with traditional three-level LLC circuit topology, this circuit topological structure is fewer than traditional three-level LLC circuit Du Li Clamp-on position diode, this circuit simplifies circuit structure to a certain extent, decreases power device, reduce cost on the whole, improve system reliability.
In order to achieve the above object, the present invention adopts following technical scheme:
A kind of novel three-level LLC resonance inverter, comprises the input derided capacitors 1, switch brachium pontis 2, resonant cavity 3, transformer 4 and the current rectifying and wave filtering circuit 5 that connect successively; Described input derided capacitors 1 is made up of the first electric capacity C1 be connected in series and the second electric capacity C2, and other one end of the first electric capacity C1 and the second electric capacity C2 is connected respectively with the positive pole of power supply and negative pole respectively; Described switch brachium pontis 2 is sequentially connected in series by with the first switching tube MOS1, the second switch pipe MOS2 of body diode, the drain-source pole of the 3rd switching tube MOS3 and the 4th switching tube MOS4, the drain electrode being positioned at the first switching tube MOS1 at switch brachium pontis two ends is connected with negative pole with the positive pole of power supply respectively with the source electrode of the 4th switching tube MOS4, and described second switch pipe MOS2 is connected with the intermediate connection point of the second electric capacity C2 with the first electric capacity C1 in input derided capacitors 1 with the intermediate connection point of the 3rd switching tube MOS3; Described resonant cavity 3 is composed in series resonant circuit successively by inductance L r, electric capacity Cr and magnetizing inductance Lm, the other end of described inductance L r is connected with the intermediate connection point of second switch pipe MOS2 with the first switching tube MOS1 in switch brachium pontis 2, and the other end of described magnetizing inductance Lm is connected with the intermediate connection point of the 4th switching tube MOS4 with the 3rd switching tube MOS3 in switch brachium pontis 2; Magnetizing inductance Lm in the former limit of described transformer 4 and resonant cavity 3 is connected in parallel, and the secondary of transformer 4 is connected with the input of current rectifying and wave filtering circuit 5; Described current rectifying and wave filtering circuit 5 adopts the mode of general rectifier bridge and output parallel filtering electric capacity to carry out rectifying and wave-filtering.
The driving process of each switching tube is: be a switch periods between t1 to T, at the positive half cycle of switch periods, t1 moment first switching tube MOS1 and the 4th switching tube MOS4 conducting simultaneously, second switch pipe MOS2 and the 3rd switching tube MOS3 is in off state, in the t2 moment, 4th switching tube MOS4 first turns off, first switching tube MOS1 continues conducting, until t3 moment first switching tube MOS1 turns off, in t3 ~ t4 moment, in circuit, resonance current is by continuous current circuit afterflow, resonance current slowly reduces simultaneously, until be reduced to zero, resonance current starts oppositely, for negative half-cycle is ready, the positive half period of whole switch terminates, at the negative half-cycle of switch periods, t4 moment second switch pipe MOS2 and the 3rd switching tube MOS3 conducting simultaneously, first switching tube MOS1 and the 4th switching tube MOS4 is in off state, in the t5 moment, 3rd switching tube MOS3 first turns off, second switch pipe MOS2 continues conducting, until t6 moment second switch pipe MOS2 turns off, in t6 ~ T moment, in circuit, resonance current is by continuous current circuit afterflow, resonance current slowly increases simultaneously, until increase to zero, resonance current starts oppositely, for the positive half period in next cycle is ready, the negative half-cycle of whole switch terminates, circulation like this.
Compared with prior art, tool has the following advantages in the present invention:
Relative to traditional half-bridge three-level LLC circuit, invention removes two Du Li Clamp-on position diodes, the voltage stress born when each switching tube in circuit is turned off is identical with the effect using Du Li Clamp-on position diode to reach.
Accompanying drawing explanation
Fig. 1 is three-level LLC converter topological circuit.
Fig. 2 is each metal-oxide-semiconductor drive waveforms in LLC converter topology circuit.
Fig. 3 is switch positive half period t1 ~ t2 moment current direction figure.
Fig. 4 is switch positive half period t2 ~ t3 moment current direction figure.
Fig. 5 is switch positive half period t3 ~ t4 moment current direction figure.
Fig. 6 is the reverse current direction figure before of switch negative half-cycle t4 ~ t5 moment resonance current.
Fig. 7 is the reverse current direction figure afterwards of switch negative half-cycle t4 ~ t5 moment resonance current.
Fig. 8 is switch negative half-cycle t5 ~ t6 moment current direction figure.
Fig. 9 is switch negative half-cycle t6 ~ T moment resonance current flow graph.
Figure 10 is the reverse current direction figure before of next start time in cycle resonance current of switch.
Figure 11 is key node oscillogram.
Embodiment
Below in conjunction with drawings and the specific embodiments, the present invention is described in further detail.
As shown in drawings, a kind of novel three-level LLC resonance inverter of the present invention, comprises the input derided capacitors 1, switch brachium pontis 2, resonant cavity 3, transformer 4 and the current rectifying and wave filtering circuit 5 that connect successively; Described input derided capacitors 1 is made up of the first electric capacity C1 be connected in series and the second electric capacity C2, and other one end of the first electric capacity C1 and the second electric capacity C2 is connected respectively with the positive pole of power supply and negative pole respectively; Described switch brachium pontis 2 is sequentially connected in series by with the first switching tube MOS1, the second switch pipe MOS2 of body diode, the drain-source pole of the 3rd switching tube MOS3 and the 4th switching tube MOS4, the drain electrode being positioned at the first switching tube MOS1 at switch brachium pontis two ends is connected with negative pole with the positive pole of power supply respectively with the source electrode of the 4th switching tube MOS4, and described second switch pipe MOS2 is connected with the intermediate connection point of the second electric capacity C2 with the first electric capacity C1 in input derided capacitors 1 with the intermediate connection point of the 3rd switching tube MOS3; Described resonant cavity 3 is composed in series resonant circuit successively by inductance L r, electric capacity Cr and magnetizing inductance Lm, the other end of described inductance L r is connected with the intermediate connection point of second switch pipe MOS2 with the first switching tube MOS1 in switch brachium pontis 2, and the other end of described magnetizing inductance Lm is connected with the intermediate connection point of the 4th switching tube MOS4 with the 3rd switching tube MOS3 in switch brachium pontis 2; Magnetizing inductance Lm in the former limit of described transformer 4 and resonant cavity 3 is connected in parallel, and the secondary of transformer 4 is connected with the input of current rectifying and wave filtering circuit 5; Described current rectifying and wave filtering circuit 5 adopts the mode of general rectifier bridge and output parallel filtering electric capacity to carry out rectifying and wave-filtering.
As shown in Figure 2, it is a switch periods between t1 to T, at the positive half cycle of switch periods, t1 moment first switching tube MOS1 and the 4th switching tube MOS4 conducting simultaneously, second switch pipe MOS2 and the 3rd switching tube MOS3 is in off state, in the t2 moment, 4th switching tube MOS4 first turns off, first switching tube MOS1 continues conducting, until t3 moment first switching tube MOS1 turns off, in t3 ~ t4 moment, in circuit, resonance current is by continuous current circuit afterflow, resonance current slowly reduces simultaneously, until be reduced to zero, resonance current starts oppositely, for negative half-cycle is ready, the positive half period of whole switch terminates, at the negative half-cycle of switch periods, t4 moment second switch pipe MOS2 and the 3rd switching tube MOS3 conducting simultaneously, first switching tube MOS1 and the 4th switching tube MOS4 is in off state, in the t5 moment, 3rd switching tube MOS3 first turns off, second switch pipe MOS2 continues conducting, until t6 moment second switch pipe MOS2 turns off, in t6 ~ T moment, in circuit, resonance current is by continuous current circuit afterflow, resonance current slowly increases simultaneously, until increase to zero, resonance current starts oppositely, for the positive half period in next cycle is ready, the negative half-cycle of whole switch terminates.Whole circuit constantly circulates down according to this working method in a switch periods exactly.
The course of work of circuit topology in a switch periods and current direction:
For fm < fs < fr (fm is the series resonance frequency of resonant inductance Lr, resonant capacitance Cr, static exciter inductance L m,
); Fr is the series resonance frequency of resonant inductance Lr, resonant capacitance Cr,
) this LLC circuit working process mainly comprises following critical stage:
A () is at the positive half period of switch periods
As shown in Figure 3, in the t1 moment, first switching tube MOS1 and the 4th switching tube MOS4 conducting simultaneously, second switch pipe MOS2 and the 3rd switching tube MOS3 is in off state, electric current now in circuit flows through the first switching tube MOS1 successively, resonant cavity 3, 4th switching tube MOS4, DC input voitage Vin is added on resonant cavity 3, resonant element inductance L r, electric capacity Cr and magnetizing inductance Lm carries out resonance, to the secondary transferring energy of transformer T, the voltage that now second switch pipe MOS2 and the 3rd switching tube MOS3 two ends are born is respectively the voltage at the first electric capacity C1 and the second electric capacity C2 two ends in input derided capacitors 1, i.e. Vin/2.
In the t2 moment, 4th switching tube MOS4 first turns off, first switching tube MOS1 continues conducting, 4th switching tube MOS4 closes and has no progeny, resonance current charges to the 4th switching tube MOS4 junction capacitance, to the 3rd switching tube MOS3 junction capacitance electric discharge, after discharge and recharge completes, 3rd switching tube MOS3 junction capacitance terminal voltage is 0V, the 3rd body diode D3 of the 3rd switching tube MOS3 starts conducting afterflow, 4th switching tube MOS4 drain-source voltage Bei Clamp-on position is the voltage at the second electric capacity C2 two ends, i.e. Vin/2, until t3 moment first switching tube MOS1 turns off, from the current direction t2 ~ t3 moment circuit as shown in Figure 4, electric current flows through the first switching tube MOS1 successively, resonant cavity 3, the 3rd body diode D3 of the 3rd switching tube MOS3, first electric capacity C1.
First switching tube MOS1 closes and has no progeny, resonance current charges to the first switching tube MOS1 junction capacitance, second switch pipe MOS2 junction capacitance is discharged, after discharge and recharge completes, second switch pipe MOS2 junction capacitance terminal voltage is 0V, the second body diode D2 conducting afterflow of second switch pipe MOS2, first switching tube MOS1 drain-source voltage Bei Clamp-on position is in C1 both end voltage, i.e. Vin/2, until the body diode afterflow of t4 moment the 3rd switching tube MOS3 and second switch pipe MOS2 terminates, the positive half period of switching tube terminates, from the current direction t3 ~ t4 moment circuit as shown in Figure 5, electric current flows through resonant cavity 3 successively, the 3rd body diode D3 of the 3rd switching tube MOS3, the second body diode D2 of second switch pipe MOS2, first electric capacity C1.
B () is at the negative half-cycle of switch periods
In the t4 moment, second switch pipe MOS2 and the 3rd switching tube MOS3 conducting simultaneously, first switching tube MOS1 and the 4th switching tube MOS4 turns off, now resonance current continues to reduce, current direction in circuit as shown in Figure 6, flow through the 3rd switching tube MOS3, second switch pipe MOS2, resonant cavity 3 successively, until resonance current is reduced to zero; After this, resonance current is reverse, and as shown in Figure 7, electric current flows through second switch pipe MOS2, the 3rd switching tube MOS3, resonant cavity 3 to the current direction in circuit successively.In this process, the first switching tube MOS1 and the 4th switching tube MOS4 is in off state, and the voltage Fen other Bei Clamp-on position of its switching tube drain-source interpolar is the terminal voltage of the first electric capacity C1 and the second electric capacity C2, is Vin/2.
In the t5 moment, 3rd switching tube MOS3 first turns off, second switch pipe MOS2 continues conducting, 3rd switching tube MOS3 closes and has no progeny, resonance current charges to the 3rd switching tube MOS3 junction capacitance, to the 4th switching tube MOS4 junction capacitance electric discharge, after discharge and recharge completes, 4th switching tube MOS4 junction capacitance terminal voltage is 0V, the 4th body diode D4 of the 4th switching tube MOS4 starts conducting afterflow, 3rd switching tube MOS3 drain-source voltage Bei Clamp-on position is the voltage at the second electric capacity C2 two ends, i.e. Vin/2, until t6 moment second switch pipe MOS2 turns off, from the current direction t5 ~ t6 moment circuit as shown in Figure 8, electric current flows through second switch pipe MOS2 successively, second electric capacity C2, the 4th body diode D4 of the 4th switching tube MOS4, resonant cavity 3.
Second switch pipe MOS2 closes and has no progeny, resonance current charges to second switch pipe MOS2 junction capacitance, to the first switching tube MOS1 junction capacitance electric discharge, after discharge and recharge completes, first switching tube MOS1 junction capacitance terminal voltage is 0V, the first body diode D1 of the first switching tube MOS1 starts conducting afterflow, second switch pipe MOS2 drain-source voltage Bei Clamp-on position is in the first electric capacity C1 both end voltage, i.e. Vin/2, until the body diode afterflow of T moment first switching tube MOS1 and the 4th switching tube MOS4 terminates, the negative half-cycle of switching tube terminates, from the current direction t6 ~ T moment circuit as shown in Figure 9, electric current flows through resonant cavity 3 successively, the first body diode D1 of the first switching tube MOS1, first electric capacity C1 and the second electric capacity C2, the 4th body diode D4 of the 4th switching tube MOS4.
In the beginning of next switch periods, first switching tube MOS1 and the 4th switching tube MOS4 drives enable, resonance current continues to increase, flow into from the 4th switching tube MOS4 source electrode, first switching tube MOS1 drains and flows out, until resonance current is increased to zero, the current direction figure now in circuit as shown in Figure 10; After this, resonance current is reverse, and the current direction figure in circuit as shown in Figure 3, enters the positive half cycle of next switch periods again, and so constantly circulation is gone down.
In circuit working process, key node waveform as shown in figure 11, be followed successively by from top to bottom: the first switching tube MOS1 drive waveforms, the first switching tube MOS1 pipe drain-source voltage stress wave, primary winding voltage waveform, the first switching tube MOS1 current waveform, the 3rd switching tube MOS3 current waveform, resonant cavity 3 current waveform.
Claims (2)
1. a novel three-level LLC resonance inverter, is characterized in that: comprise the input derided capacitors (1), switch brachium pontis (2), resonant cavity (3), transformer (4) and the current rectifying and wave filtering circuit (5) that connect successively, described input derided capacitors (1) is made up of the first electric capacity (C1) be connected in series and the second electric capacity (C2), and other one end of the first electric capacity (C1) and the second electric capacity (C2) is connected respectively with the positive pole of power supply and negative pole respectively, described switch brachium pontis (2) is by the first switching tube (MOS1) with body diode, second switch pipe (MOS2), the drain-source pole of the 3rd switching tube (MOS3) and the 4th switching tube (MOS4) is sequentially connected in series, the drain electrode being positioned at first switching tube (MOS1) at switch brachium pontis two ends is connected with negative pole with the positive pole of power supply respectively with the source electrode of the 4th switching tube (MOS4), described second switch pipe (MOS2) is connected with the intermediate connection point of the second electric capacity (C2) with the first electric capacity (C1) in input derided capacitors (1) with the intermediate connection point of the 3rd switching tube (MOS3), described resonant cavity (3) is composed in series resonant circuit successively by inductance (Lr), electric capacity (Cr) and magnetizing inductance (Lm), the other end of described inductance (Lr) is connected with the intermediate connection point of second switch pipe (MOS2) with the first switching tube (MOS1) in switch brachium pontis (2), and the other end of described magnetizing inductance (Lm) is connected with the intermediate connection point of the 4th switching tube (MOS4) with the 3rd switching tube (MOS3) in switch brachium pontis (2), magnetizing inductance (Lm) in the former limit of described transformer (4) and resonant cavity (3) is connected in parallel, and the secondary of transformer (4) is connected with the input of current rectifying and wave filtering circuit (5), described current rectifying and wave filtering circuit (5) adopts the mode of general rectifier bridge and output parallel filtering electric capacity to carry out rectifying and wave-filtering.
2. a kind of novel three-level LLC resonance inverter according to claim 1, it is characterized in that: the driving process of each switching tube is: be a switch periods between t1 to T, at the positive half cycle of switch periods, t1 moment first switching tube (MOS1) and the conducting simultaneously of the 4th switching tube (MOS4), second switch pipe (MOS2) and the 3rd switching tube (MOS3) are in off state, in the t2 moment, 4th switching tube (MOS4) first turns off, first switching tube (MOS1) continues conducting, until the t3 moment first switching tube (MOS1) turns off, in t3 ~ t4 moment, in circuit, resonance current is by continuous current circuit afterflow, resonance current slowly reduces simultaneously, until be reduced to zero, resonance current starts oppositely, for negative half-cycle is ready, the positive half period of whole switch terminates, at the negative half-cycle of switch periods, t4 moment second switch pipe (MOS2) and the conducting simultaneously of the 3rd switching tube (MOS3), first switching tube (MOS1) and the 4th switching tube (MOS4) are in off state, in the t5 moment, 3rd switching tube (MOS3) first turns off, second switch pipe (MOS2) continues conducting, until t6 moment second switch pipe (MOS2) turns off, in t6 ~ T moment, in circuit, resonance current is by continuous current circuit afterflow, resonance current slowly increases simultaneously, until increase to zero, resonance current starts oppositely, for the positive half period in next cycle is ready, the negative half-cycle of whole switch terminates, circulation like this.
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Cited By (6)
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| CN105119496A (en) * | 2015-09-29 | 2015-12-02 | 燕山大学 | Wide input range three-level LLC resonant converter and level switching control method |
| CN105897000A (en) * | 2016-04-25 | 2016-08-24 | 陕西科技大学 | Phase shift compensation interleaved three-level LLC resonant converter |
| CN106026673A (en) * | 2016-07-05 | 2016-10-12 | 陕西科技大学 | Wide-scope input LLC resonance converter with high-voltage gain |
| CN111525807A (en) * | 2020-04-13 | 2020-08-11 | 哈尔滨工业大学 | Harmonic optimization-based high-order LCLCL direct current converter and parameter design method |
| US10833594B2 (en) | 2017-05-19 | 2020-11-10 | Infineon Technologies Austria Ag | System and method of controlling a power converter having an LC tank coupled between a switching network and a transformer winding |
| CN112994499A (en) * | 2021-03-02 | 2021-06-18 | 济宁奥太电气有限公司 | Three-level half-bridge soft switch converter circuit, control system and control method thereof |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105119496A (en) * | 2015-09-29 | 2015-12-02 | 燕山大学 | Wide input range three-level LLC resonant converter and level switching control method |
| CN105897000A (en) * | 2016-04-25 | 2016-08-24 | 陕西科技大学 | Phase shift compensation interleaved three-level LLC resonant converter |
| CN106026673A (en) * | 2016-07-05 | 2016-10-12 | 陕西科技大学 | Wide-scope input LLC resonance converter with high-voltage gain |
| US10833594B2 (en) | 2017-05-19 | 2020-11-10 | Infineon Technologies Austria Ag | System and method of controlling a power converter having an LC tank coupled between a switching network and a transformer winding |
| CN111525807A (en) * | 2020-04-13 | 2020-08-11 | 哈尔滨工业大学 | Harmonic optimization-based high-order LCLCL direct current converter and parameter design method |
| CN111525807B (en) * | 2020-04-13 | 2023-04-14 | 哈尔滨工业大学 | High-order LCLCLCL direct current converter based on harmonic optimization and parameter design method |
| CN112994499A (en) * | 2021-03-02 | 2021-06-18 | 济宁奥太电气有限公司 | Three-level half-bridge soft switch converter circuit, control system and control method thereof |
| CN112994499B (en) * | 2021-03-02 | 2022-03-29 | 济宁奥太电气有限公司 | Three-level half-bridge soft switch converter circuit, control system and control method thereof |
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| Publication number | Publication date |
|---|---|
| CN104852590B (en) | 2017-07-18 |
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