CN110445387B - Topological structure and control method of formation and grading power supply - Google Patents

Topological structure and control method of formation and grading power supply Download PDF

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Publication number
CN110445387B
CN110445387B CN201910614570.2A CN201910614570A CN110445387B CN 110445387 B CN110445387 B CN 110445387B CN 201910614570 A CN201910614570 A CN 201910614570A CN 110445387 B CN110445387 B CN 110445387B
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voltage
current
capacitor
switching
resonant
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CN110445387A (en
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孙尧
邓国良
许国
陈孝莺
谢诗铭
言书田
栗梅
韩华
王辉
刘永露
但汉兵
熊文静
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Central South University
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Central South University
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    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02JCIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00Circuit arrangements for ac mains or ac distribution networks
    • H02J3/38Arrangements for parallely feeding a single network by two or more generators, converters or transformers
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02JCIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/0068Battery or charger load switching, e.g. concurrent charging and load supply
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00Conversion of dc power input into dc power output
    • H02M3/22Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33584Bidirectional converters
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00Conversion of dc power input into dc power output
    • H02M3/22Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H02M7/2195Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration the switches being synchronously commutated at the same frequency of the AC input voltage
    • YGENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02BCLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The invention relates to the field of power electronic system control, in particular to a topological structure and a control method of a formation and grading power supply. The invention relates to a topological structure of a power supply for component capacitance, which comprises a three-phase AC/DC rectifier, an LLC resonant converter, and a voltage stabilizing capacitor C at the output side of the three-phase AC/DC rectifierdA voltage stabilizing capacitor C connected in parallel with the LLC resonant converter at the output side of the LLC resonant converter0The LLC resonant converter is connected with a load battery E in parallel, has the characteristics of bidirectional energy flow and automatic switching, and has constant voltage gain when the switching frequency is not higher than the resonant frequency; and a control method for a component-capacitance power supply using the output voltage V of the LLC resonant converter0The method comprises the following steps of taking input current of a three-phase AC/DC rectifier as an outer loop and taking the input current of the three-phase AC/DC rectifier as an inner loop; the bidirectional flow of energy is realized and the automatic switching is realized.

Description

Topological structure and control method of formation and grading power supply
Technical Field
The invention relates to the technical field of power electronic system control, in particular to a topological structure and a control method of a formation and grading power supply.
Background
The chemical composition capacity is the last very important process before the battery leaves a factory, namely, the electrochemical performance of an active substance in the battery is improved and enhanced by carrying out a series of charging and discharging on the battery. Compared with foreign chemical composition capacity grading equipment, most chemical composition equipment used in the market at present has single chemical composition function and only has three simple modes of constant current charging, constant voltage charging and constant current discharging. The formation capacitance-sharing power supply is an alternating current input and direct current output (AC/DC) device. Most of the traditional formation power supply equipment adopts unidirectional power flow, namely, the battery can only be charged by a formation and grading power supply or discharged by the battery through the formation and grading power supply, and the energy flow direction switching of the formation and grading power supply cannot be realized on line. Although some capacity-sharing power supplies can switch the energy flow direction in recent years, the output voltage is specially detected, compared with the reference value of the output voltage, and the energy flow direction is judged through a control algorithm so as to select a corresponding system control scheme. In order to prevent frequent switching of the energy flow direction, a dead zone is often required to be set, which causes large fluctuation of the output voltage when the energy flow direction is switched, and prolongs the transient regulation time of the system. In addition, because the formation capacitance-capacitance capacitor is usually used in low-voltage and high-current occasions, the selected device has low voltage-resistant grade, so the highest allowable value of the output voltage is low, the set voltage dead zone threshold is very low, the control algorithm is very complex when the energy flow direction switching is actually realized, and if the energy flow direction switching fails, the output voltage is suddenly changed, even the highest allowable value is possibly exceeded, and serious consequences such as formation power supply damage occur.
Disclosure of Invention
Technical problem to be solved
Based on the above problems, the present invention provides a topology structure and a control method for a power supply for component capacitance, which can realize bidirectional flow of energy and automatic switching.
(II) technical scheme
Based on the technical problems, the invention provides a chemical compositionThe topological structure of the capacitor power supply is characterized in that the power supply comprises a three-phase AC/DC rectifier, an LLC resonant converter and a voltage stabilizing capacitor C at the output side of the three-phase AC/DC rectifierdA voltage stabilizing capacitor C connected in parallel with the LLC resonant converter at the output side of the LLC resonant converter0The LLC resonant converter is connected with a load battery E in parallel, has the characteristics of bidirectional energy flow and automatic switching, and has constant voltage gain when the switching frequency is not higher than the resonant frequency; the energy flows bidirectionally and switches automatically, i.e. the voltage of the battery E is lower than the reference voltage V of the LLC resonant converter0 *When the energy flows in the positive direction, the battery E is charged; the voltage of the battery E is higher than the reference voltage V of the LLC resonant converter0 *When the energy flows reversely, the battery E feeds back the energy.
Further, the LLC resonant converter includes a main circuit and a control circuit, the main circuit includes a resonant circuit, two switching circuits, a transformer, and two ports; the primary side of the transformer comprises a resonant inductor LrResonant capacitor Cr1And Cr2And an auxiliary diode connected in reverse parallel to the resonant circuit and composed of a switching tube S1And S2A switching circuit; the secondary side of the transformer comprises a switching tube Q1、Q2、Q3、Q4A switching circuit; first port parallel voltage-stabilizing capacitor CdThe second port is connected with a voltage-stabilizing capacitor C in parallel0
The connection relationship of each component in the main circuit is as follows: on the primary side of the transformer, a resonant capacitor Cr1Positive electrode of (2) and switching tube S1The drain electrode of the capacitor is simultaneously connected with the voltage-stabilizing capacitor CdIs connected with the positive pole of the resonant capacitor Cr1The negative electrode of the capacitor is simultaneously connected with the resonant capacitor Cr2Is connected with the negative pole of the primary side of the transformer, and a switching tube S1Source electrode of the resonant inductor LrAnd a switching tube S2Is connected with the drain electrode of the switching tube S2Source electrode and resonant capacitor Cr2The negative electrode of the capacitor is simultaneously connected with the voltage-stabilizing capacitor CdIs connected to the negative pole of the resonant inductor LrThe other end of the resonant capacitor is connected with the positive electrode of the primary side of the transformer, and the resonant capacitor Cr1、Cr2Respectively connecting an auxiliary diode in parallel in the reverse direction; on the secondary side of the transformer, a switching tube Q1Drain electrode of (1) and switching tube Q2The drain electrode of the capacitor is simultaneously connected with the voltage-stabilizing capacitor C0Is connected with the positive pole of the switching tube Q1The source electrode of the transformer is simultaneously connected with the anode of the secondary side of the transformer and the switching tube Q3Is connected with the drain electrode of the switching tube Q2The source electrode of the transformer is simultaneously connected with the cathode of the secondary side of the transformer and the switching tube Q4Is connected with the drain electrode of the switching tube Q3Source electrode of (1) and switching tube Q4Source electrode of the capacitor and the voltage-stabilizing capacitor C0Are connected with each other.
Furthermore, the control circuit comprises a controller and a driving circuit, wherein the controller is a DSP controller and is used for generating a set of complementary PWM driving signals, and the driving circuit isolates and enhances the received PWM driving signals from the controller to form a switching tube S of the main circuit1、S2、Q1~Q4A driving voltage is provided.
Further, the switch tube S1、S2、Q1~Q4The switch tube is a parasitic capacitor with a body diode and a drain source electrode which are connected in an anti-parallel mode.
Further, the switch tube S1And Q1、Q4Is identical with the drive signal of S2And Q2、Q3Is consistent, ignoring dead time, S1And S2Are complementary to each other.
Further, the LLC resonant converter operates in an open loop mode, and when the switching frequency is not higher than the resonant frequency, the input voltage V isdAnd an output voltage V0The proportional relationship, independent of load variations, can be considered to be DCX, i.e.
Vd=kV0=2nV0
Wherein k is LLC resonant converter input voltage VdAnd an output voltage V0N is the transformation ratio of the transformer.
A control method based on the topology of the formation-capacitance power supply is characterized in that LLC resonance transformation is adoptedOutput voltage V of the device0Is an outer loop, and is connected to a reference voltage V0 *The compared difference value is regulated by PI to obtain a reference value I of the direct-axis currentd *The input current of the three-phase AC/DC rectifier is used as an inner loop, and the direct-axis current I is obtained through park transformationdAnd quadrature axis current IqDirect axis current IdAnd quadrature axis current IqRespectively with reference value I of direct-axis currentd *Reference value I of quadrature axis currentq *Comparing, adjusting error value by PI to obtain control rate of dq coordinate axis, inverse park transforming, and outputting to PWM modulation module to control switching device of three-phase AC/DC rectifier and adjust input voltage V of LLC resonant converterdThereby regulating the output voltage V of the LLC resonant converter0(ii) a When V is0Greater than a reference voltage V0 *When it is, control and regulate Vd、V0Decrease; when V is0Less than reference voltage V0 *When it is, control and regulate Vd、V0And is increased.
(III) advantageous effects
The technical scheme of the invention has the following advantages:
(1) the driving signals of the switching tubes are consistent during the positive and negative operation, so that the bidirectional flow and automatic switching of energy can be realized, the voltage of an output load does not need to be detected, and a switching control algorithm is not needed;
(2) the bidirectional resonant soft switch can be realized, namely zero-voltage switching-on and zero-current switching-off of the input end and zero-voltage switching-on of the output end are realized, the switching-on and switching-off loss of the switch is reduced, the overall efficiency is improved, meanwhile, harmonic waves are greatly reduced, and the interference to other equipment is reduced;
(3) synchronous rectification is adopted, so that the conversion loss of a rectification part is reduced;
(4) the energy feedback of the battery to the power grid is automatically realized, and energy and battery production cost are saved;
(5) because the LLC resonant converter can be equivalent to a proportional link, the output voltage feedback of the LLC resonant converter is adopted, and the load regulation rate can be improved;
(6) the closed-loop control of the input power grid current can improve the input power factor and reduce the harmonic pollution to the power grid;
(7) the control structure is simple, the cost is lower, but the control effect is reliable and safe.
Drawings
The features and advantages of the present invention will be more clearly understood by reference to the accompanying drawings, which are illustrative and not to be construed as limiting the invention in any way, and in which:
fig. 1 is a topology structure diagram of a component-capacitor power supply according to an embodiment of the present invention;
fig. 2 is a topology structure diagram of an LLC resonant converter of a component-capacitance power supply according to an embodiment of the present invention;
FIG. 3 is a control block diagram of a component-capacitor power supply according to an embodiment of the present invention;
FIG. 4(a) is a waveform diagram of an LLC resonant converter according to the embodiment of the invention in forward operation;
FIG. 4(b) is a waveform diagram of the LLC resonant converter of the embodiment of the invention in reverse operation;
FIG. 5 shows an LLC resonant converter of an embodiment of the invention at t0-t6Equivalent circuit diagram of the working condition of (1);
FIG. 6 is a graph of gain curves of an LLC resonant converter in accordance with an embodiment of the invention;
FIG. 7 is a waveform diagram of three-phase AC/DC rectifier input grid voltage, input grid current, and three-phase AC/DC rectifier output DC voltage under reverse power flow conditions;
fig. 8 shows waveforms of the three-phase AC/DC rectifier input grid voltage, input grid current and three-phase AC/DC rectifier output DC voltage, and the load battery voltage, current waveforms when the power flow is automatically switched from forward to reverse.
Detailed Description
The following detailed description of embodiments of the present invention is provided in connection with the accompanying drawings and examples. The following examples are intended to illustrate the invention but are not intended to limit the scope of the invention.
The invention relates to a topological structure of a variable-capacity power supply,as shown in FIG. 1, the power supply comprises a three-phase AC/DC rectifier, an LLC resonant converter, a voltage stabilizing capacitor C at the output side of the three-phase AC/DC rectifierdA voltage stabilizing capacitor C connected in parallel with the LLC resonant converter at the output side of the LLC resonant converter0The LLC resonant converter is connected with a load battery E in parallel, has the characteristics of bidirectional energy flow and automatic switching, and has constant voltage gain when the switching frequency is not higher than the resonant frequency; the energy flows bidirectionally and switches automatically, i.e. the voltage of the battery E is lower than the reference voltage V of the LLC resonant converter0 *When the energy flows in the positive direction, the battery E is charged; the voltage of the battery E is higher than the reference voltage V of the LLC resonant converter0 *When the energy flows reversely, the battery E feeds back the energy.
The LLC resonant converter includes a main circuit and a control circuit, as shown in fig. 2, the main circuit includes a resonant circuit, two switching circuits, a transformer, and two ports; the primary side of the transformer comprises a resonant inductor LrResonant capacitor Cr1And Cr2And an auxiliary diode connected in reverse parallel to the resonant circuit and composed of a switching tube S1And S2A switching circuit; the secondary side of the transformer comprises a switching tube Q1、Q2、Q3、Q4A switching circuit; first port parallel voltage-stabilizing capacitor CdThe second port is connected with a voltage-stabilizing capacitor C in parallel0
The connection relationship of each component in the main circuit is as follows: at the primary side of the transformer, a resonant capacitor Cr1Positive electrode of (2) and switching tube S1The drain electrode of the capacitor is simultaneously connected with the voltage-stabilizing capacitor CdIs connected with the positive pole of the resonant capacitor Cr1The negative electrode of the capacitor is simultaneously connected with the resonant capacitor Cr2Is connected with the negative pole of the primary side of the transformer, and a switching tube S1Source electrode of the resonant inductor LrAnd a switching tube S2Is connected with the drain electrode of the switching tube S2Source electrode and resonant capacitor Cr2The negative electrode of the capacitor is simultaneously connected with the voltage-stabilizing capacitor CdIs connected to the negative pole of the resonant inductor LrThe other end of the resonant capacitor is connected with the positive electrode of the primary side of the transformer, and the resonant capacitor Cr1、Cr2Are respectively connected in reverse parallel toAn auxiliary diode; on the secondary side of the transformer, a switching tube Q1Drain electrode of (1) and switching tube Q2The drain electrode of the capacitor is simultaneously connected with the voltage-stabilizing capacitor C0Is connected with the positive pole of the switching tube Q1The source electrode of the transformer is simultaneously connected with the anode of the secondary side of the transformer and the switching tube Q3Is connected with the drain electrode of the switching tube Q2The source electrode of the transformer is simultaneously connected with the cathode of the secondary side of the transformer and the switching tube Q4Is connected with the drain electrode of the switching tube Q3Source electrode of (1) and switching tube Q4Source electrode of the capacitor and the voltage-stabilizing capacitor C0Are connected with each other.
The switch tube S1、S2、Q1~Q4The switch tube is a parasitic capacitor with an anti-parallel body diode and a drain source electrode.
The voltage of the first port of the LLC resonant converter is VdCurrent is IinAnd the voltage of the second port is V0;imFor passing through the excitation inductance LmCurrent of (i)rFor flowing through resonant inductor LrResonant current of, IsIs secondary side current, IEFor the current flowing through the battery E, ur1、ur2Are respectively a resonant capacitor Cr1、Cr2Voltage across, S1、S2、Q1、Q2、Q3、Q4Respectively, represent the gate signals of the corresponding MOSFETs.
A control method of the variable-capacity power supply is characterized in that the output voltage V of the LLC resonant converter is used as shown in figure 30Is an outer loop, and is connected to a reference voltage V0 *The compared difference value is regulated by PI to obtain a reference value I of the direct-axis currentd *The input current of the three-phase AC/DC rectifier is used as an inner loop, and the direct-axis current I is obtained through park transformationdAnd quadrature axis current IqDirect axis current IdAnd quadrature axis current IqRespectively with reference value I of direct-axis currentd *Reference value I of quadrature axis currentq *Comparing, adjusting error value by PI to obtain control rate of dq coordinate axis, inverse park transforming, and outputting to PWM modulation module to control switch of three-phase AC/DC rectifierDevice for regulating input voltage V of LLC resonant converterdThereby regulating the output voltage V of the LLC resonant converter0(ii) a When V is0Greater than a reference voltage V0 *When it is, control and regulate Vd、V0Decrease; when V is0Less than reference voltage V0 *When it is, control and regulate Vd、V0And is increased.
Besides the main circuit, the LLC resonant converter also comprises a control circuit, the control circuit comprises a controller and a drive circuit, the controller is a DSP controller and is used for generating a set of complementary PWM drive signals, and the drive circuit isolates and enhances the PWM drive signals received from the controller to form a switching tube S of the main circuit1、S2、Q1~Q4Providing a drive voltage, S1And Q1、Q4Is identical with the drive signal of S2And Q2、Q3Is identical with the drive signal of S1And S2The on-time is fixed to half of the LLC resonant period, i.e. the MOSFET drive signal is a pulse signal with a fixed duty cycle of 50% (ignoring dead time).
The working process of the embodiment and the circuit topology thereof is as follows:
in the forward operation, as shown in FIGS. 4(a) and 5, at t0Time of day, resonant current irWhen starting to increase from zero, the switching tube S1And Q1、Q4Simultaneously, if the parameters and the dead time are reasonably designed, t0Time S1Just after the discharge is finished, S can be realized at the same time1According to the voltage-second balance characteristic of the inductor, the exciting current i before the switch-on between the dead zonesmNegative, secondary current from Q1、Q4Flows through the body diode of (Q)1、Q4The voltage across is clamped to zero and to Q1、Q4The zero voltage switching on creates conditions; by adjusting the dead time to make the switching frequency less than the resonance frequency, at t0Time of day, S1And Q1、Q4Zero voltage on, irBeing a sinusoidal signal, excitation current imLinearly increasing, secondary side synchronously rectifying until t1Time of day, resonant current irWith excitation current imAre equal in absolute value, secondary side current IsIs zero due to Q1、Q4Is still in the on state, Q1、Q4Current reversal, energy feedback; at t2Time of day, resonant current irWhen the half resonant period reaches zero again, the switch tube S1And Q1、Q4Are turned off at the same time, at this time S1Is turned off at zero current, and Q1、Q4There is an off current; t is t2To t3Is the dead time, at which the S of the primary side1Charging of the junction capacitance of S2Discharge of junction capacitance, Q of secondary side1、Q4Charging of junction capacitance, Q2、Q3The primary side current is less than the secondary side current, and the Q of the secondary side1、Q4After the junction capacitor is charged first, Q2、Q3Is turned on, thus Q2、Q3Zero voltage conduction can be realized; if the parameters and dead time are reasonably designed, at t3Time S2After the discharge is completed, S2Zero voltage conduction can be realized; the waveform of the second half of the switching period is symmetrical, and the principle is the same.
In reverse operation, the waveform of the LLC resonant converter is as shown in FIG. 4(b), at t0-t6Is the same as that in the forward operation shown in FIG. 5, but the resonant current irAnd secondary side current IsThe direction is opposite to that of the positive working at t0Time of day, secondary side current IsWhen starting to increase from zero, the switching tube S1And Q1、Q4Simultaneously, if the parameters and the dead time are reasonably designed, t0Time Q1、Q4Just after the discharge is finished, Q can be realized at the same time1、Q4Is turned on due to the exciting current i in the dead timemIs negative and is related to the resonant current irIs equal to S1Completing discharge before turning on1The voltage at both ends is clamped to zero and is S1Zero voltage turn-on creates a stripeA member; by adjusting the dead time to make the switching frequency less than the resonance frequency, at t0Time of day, S1And Q1、Q4Zero voltage on, IsBeing a sinusoidal signal, excitation current imIncrease linearly until t1Time of day, secondary side current I s1/n times of and excitation current imAre equal in absolute value, the resonant current irIs zero due to S1Is still in the on state, S1Current reversal, energy feedback; at t2Time of day, secondary side current IsWhen the half resonant period reaches zero again, the switch tube S1And Q1、Q4Are turned off at the same time, at this time Q1、Q4Is turned off at zero current, and S1There is an off current; t is t2To t3Is the dead time, at which the S of the primary side1Charging of the junction capacitance of S2Discharge of junction capacitance, Q of secondary side1、Q4Charging of junction capacitance, Q2、Q3Due to the exciting current i in the dead timemIs positive and resonant current irEqual, the primary junction capacitance of S2 is discharged first, S2Is turned on, so that S2Zero voltage conduction can be realized, if the parameters and the dead time are reasonably designed, at t3Time Q2、Q3After the discharge is completed, Q2、Q3Zero voltage conduction can be realized; the waveform of the second half of the switching period is symmetrical, and the principle is the same.
Therefore, under the modulation strategy of 'same switch and same switch', the driving signal of the LLC resonant converter is not changed, the energy of the LLC resonant converter can flow in two directions and automatically switch, and when the voltage of the load battery E is lower than the reference voltage V0 *When the power supply energy flows in the positive direction, the battery E is charged; when the voltage of the load battery E is higher than the reference voltage V0 *When the power supply energy flows reversely, the battery E feeds back energy to the power grid.
Since the waveforms of the positive and negative half cycles of the LLC resonant converter are symmetrical, the derivation is made here in the positive half cycle mode when the LLC resonant converter is operating in the forward direction.
At t0Time of day, S1And Q1、Q4When the system is opened, a differential equation is established:
Figure BDA0002123480730000101
and Cr1=Cr2=CrSolving a differential equation to obtain:
Figure BDA0002123480730000102
the principle of conservation of input and output power comprises the following steps:
Figure BDA0002123480730000103
where R is the equivalent resistance of the battery load,
Figure BDA0002123480730000104
obtained by the formula (2):
Figure BDA0002123480730000111
will be provided with
Figure BDA0002123480730000112
Substituting into formula (2) to obtain
Figure BDA0002123480730000113
Substituting the formula (3) into the formula (4) to obtain:
Figure BDA0002123480730000114
therefore, under the modulation strategy of 'same switch and same switch', when the switching frequency is lower than the resonant frequency, the LLC resonant converter can realize constant gain, and LLConstant gain can be realized when the switching frequency of the C resonant converter is equal to the resonant frequency, therefore, when the switching frequency is not higher than the resonant frequency, the LLC resonant converter can realize constant gain, and can be regarded as LLC-DCX, and the output voltage V of the three-phase AC/DC rectifierdOutput voltage V of resonant converter with LLC0Proportional relationship, independent of load variations, i.e.
Vd=kV0=2nV0
Wherein k is LLC resonant converter input voltage VdAnd an output voltage V0N is the transformation ratio of the transformer.
Accordingly, a gain curve graph when the switching frequency is higher than the resonant frequency can be obtained by combining with the FHA (fundamental wave approximation analysis), so that a voltage gain curve when the LLC resonant converter adopts the "same-switch" modulation strategy is obtained as shown in fig. 6.
Waveforms of the three-phase AC/DC rectifier input grid voltage, input grid current and three-phase AC/DC rectifier output DC voltage under the condition of reverse power flow (energy feedback from the battery to the grid) are shown in fig. 7; the waveforms of the input grid voltage, the input grid current and the output DC voltage of the three-phase AC/DC rectifier and the waveforms of the load battery voltage and current when the power flow is automatically switched from the forward direction (the grid charging the battery) to the reverse direction (the battery feeding back energy to the grid) are shown in fig. 8.
In summary, the topology and the control method of the compound capacitive power supply have the following advantages:
(1) the driving signals of the switching tubes are consistent during the positive and negative operation, so that the bidirectional flow and automatic switching of energy can be realized, the voltage of an output load does not need to be detected, and a switching control algorithm is not needed;
(2) the bidirectional resonant soft switch can be realized, namely zero-voltage switching-on and zero-current switching-off of the input end and zero-voltage switching-on of the output end are realized, the switching-on and switching-off loss of the switch is reduced, the overall efficiency is improved, meanwhile, harmonic waves are greatly reduced, and the interference to other equipment is reduced;
(3) synchronous rectification is adopted, so that the conversion loss of a rectification part is reduced;
(4) the energy feedback of the battery to the power grid is automatically realized, and energy and battery production cost are saved;
(5) because the LLC resonant converter can be equivalent to a proportional link, the output voltage feedback of the LLC resonant converter is adopted, and the load regulation rate can be improved;
(6) the closed-loop control of the input power grid current can improve the input power factor and reduce the harmonic pollution to the power grid;
(7) the control structure is simple, the cost is lower, but the control effect is reliable and safe.
Finally, it should be noted that: the above examples are only intended to illustrate the technical solution of the present invention, but not to limit it; although the embodiments of the present invention have been described in conjunction with the accompanying drawings, those skilled in the art may make various modifications and variations without departing from the spirit and scope of the invention, and such modifications and variations fall within the scope defined by the appended claims.

Claims (5)

1. The control method of the topological structure of the power supply for the component and the capacitor is characterized in that the topological structure of the power supply for the component and the capacitor comprises a three-phase AC/DC rectifier, an LLC resonant converter and a voltage stabilizing capacitor C at the output side of the three-phase AC/DC rectifierdA voltage stabilizing capacitor C connected in parallel with the LLC resonant converter at the output side of the LLC resonant converter0The LLC resonant converter is connected with a load battery E in parallel, has the characteristics of bidirectional energy flow and automatic switching, does not need a switching control algorithm, and has constant voltage gain when the switching frequency is not higher than the resonant frequency under the modulation strategy of 'same switch and same switch'; the energy flows bidirectionally and switches automatically, i.e. the voltage of the battery E is lower than the reference voltage V of the LLC resonant converter0 *When the energy flows in the positive direction, the battery E is charged; the voltage of the battery E is higher than the reference voltage V of the LLC resonant converter0 *When the energy flows reversely, the battery E feeds back the energy; the LLC resonant converter operates in an open loop mode;
the control method comprises the following steps: with output voltage V of the LLC resonant converter0Is an outer ring, andreference voltage V0 *The compared difference value is regulated by PI to obtain a reference value I of the direct-axis currentd *The input current of the three-phase AC/DC rectifier is used as an inner loop, and the direct-axis current I is obtained through park transformationdAnd quadrature axis current IqDirect axis current IdAnd quadrature axis current IqRespectively with reference value I of direct-axis currentd *Reference value I of quadrature axis currentq *Comparing, adjusting error value by PI to obtain control rate of dq coordinate axis, inverse park transforming, and outputting to PWM modulation module to control switching device of three-phase AC/DC rectifier and adjust input voltage V of LLC resonant converterdThereby regulating the output voltage V of the LLC resonant converter0(ii) a When V is0Greater than a reference voltage V0 *When it is, control and regulate Vd、V0Decrease; when V is0Less than reference voltage V0 *When it is, control and regulate Vd、V0Increasing;
the LLC resonant converter comprises a main circuit and a control circuit, wherein the main circuit comprises a resonant circuit, two switching circuits, a transformer and two ports; the primary side of the transformer comprises a resonant inductor LrResonant capacitor Cr1And Cr2And an auxiliary diode connected in reverse parallel to the resonant circuit and composed of a switching tube S1And S2A switching circuit; the secondary side of the transformer comprises a switching tube Q1、Q2、Q3、Q4A switching circuit; first port parallel voltage-stabilizing capacitor CdThe second port is connected with a voltage-stabilizing capacitor C in parallel0
The connection relationship of each component in the main circuit is as follows: on the primary side of the transformer, a resonant capacitor Cr1Positive electrode of (2) and switching tube S1The drain electrode of the capacitor is simultaneously connected with the voltage-stabilizing capacitor CdIs connected with the positive pole of the resonant capacitor Cr1The negative electrode of the capacitor is simultaneously connected with the resonant capacitor Cr2Is connected with the negative pole of the primary side of the transformer, and a switching tube S1Source electrode of the resonant inductor LrAnd a switching tube S2Is connected with the drain electrode of the switching tube S2Source electrode and resonant capacitor Cr2The negative electrode of the capacitor is simultaneously connected with the voltage-stabilizing capacitor CdIs connected to the negative pole of the resonant inductor LrThe other end of the resonant capacitor is connected with the positive electrode of the primary side of the transformer, and the resonant capacitor Cr1、Cr2Respectively connecting an auxiliary diode in parallel in the reverse direction; on the secondary side of the transformer, a switching tube Q1Drain electrode of (1) and switching tube Q2The drain electrode of the capacitor is simultaneously connected with the voltage-stabilizing capacitor C0Is connected with the positive pole of the switching tube Q1The source electrode of the transformer is simultaneously connected with the anode of the secondary side of the transformer and the switching tube Q3Is connected with the drain electrode of the switching tube Q2The source electrode of the transformer is simultaneously connected with the cathode of the secondary side of the transformer and the switching tube Q4Is connected with the drain electrode of the switching tube Q3Source electrode of (1) and switching tube Q4Source electrode of the capacitor and the voltage-stabilizing capacitor C0The negative electrodes are connected;
the circuit topology works as follows:
in forward operation, at t0Time of day, resonant current irWhen starting to increase from zero, the switching tube S1And Q1、Q4Simultaneously, if the parameters and the dead time are reasonably designed, t0Time S1Just after the discharge is finished, S can be realized at the same time1According to the voltage-second balance characteristic of the inductor, the exciting current i before the switch-on between the dead zonesmNegative, secondary current from Q1、Q4Flows through the body diode of (Q)1、Q4The voltage across is clamped to zero and to Q1、Q4The zero voltage switching on creates conditions; by adjusting the dead time to make the switching frequency less than the resonance frequency, at t0Time of day, S1And Q1、Q4Zero voltage on, irBeing a sinusoidal signal, excitation current imLinearly increasing, secondary side synchronously rectifying until t1Time of day, resonant current irWith excitation current imAre equal in absolute value, secondary side current IsIs zero due to Q1、Q4Is still in the on state, Q1、Q4Current reversal, energy feedback; at t2Time of day, resonant current irWhen the half resonant period reaches zero again, the switch tube S1And Q1、Q4Are turned off at the same time, at this time S1Is turned off at zero current, and Q1、Q4There is an off current; t is t2To t3Is the dead time, at which the S of the primary side1Charging of the junction capacitance of S2Discharge of junction capacitance, Q of secondary side1、Q4Charging of junction capacitance, Q2、Q3The primary side current is less than the secondary side current, and the Q of the secondary side1、Q4After the junction capacitor is charged first, Q2、Q3Is turned on, thus Q2、Q3Zero voltage conduction can be realized; if the parameters and dead time are reasonably designed, at t3Time S2After the discharge is completed, S2Zero voltage conduction can be realized; the waveform of the second half of the switching period is symmetrical, and the principle is the same;
in reverse operation, at t0-t6The equivalent circuit diagram of the working condition of (1) is the same as that of the forward working, but the resonant current irAnd secondary side current IsThe direction is opposite to that of the positive working at t0Time of day, secondary side current IsWhen starting to increase from zero, the switching tube S1And Q1、Q4Simultaneously, if the parameters and the dead time are reasonably designed, t0Time Q1、Q4Just after the discharge is finished, Q can be realized at the same time1、Q4Is turned on due to the exciting current i in the dead timemIs negative and is related to the resonant current irIs equal to S1Completing discharge before turning on1The voltage at both ends is clamped to zero and is S1The zero voltage switching on creates conditions; by adjusting the dead time to make the switching frequency less than the resonance frequency, at t0Time of day, S1And Q1、Q4Zero voltage on, IsBeing a sinusoidal signal, excitation current imIncrease linearly until t1Time of day, secondary side current Is1/n times of and excitation current imAre equal in absolute value, the resonant current irIs zero due to S1Is still in the on state, S1Current reversal, energy feedback; at t2Time of day, secondary side current IsWhen the half resonant period reaches zero again, the switch tube S1And Q1、Q4Are turned off at the same time, at this time Q1、Q4Is turned off at zero current, and S1There is an off current; t is t2To t3Is the dead time, at which the S of the primary side1Charging of the junction capacitance of S2Discharge of junction capacitance, Q of secondary side1、Q4Charging of junction capacitance, Q2、Q3Due to the exciting current i in the dead timemIs positive and resonant current irEqual, the primary junction capacitance of S2 is discharged first, S2Is turned on, so that S2Zero voltage conduction can be realized, if the parameters and the dead time are reasonably designed, at t3Time Q2、Q3After the discharge is completed, Q2、Q3Zero voltage conduction can be realized; the waveform of the second half of the switching period is symmetrical, and the principle is the same.
2. The method according to claim 1, wherein the control circuit comprises a controller and a driving circuit, the controller is a DSP controller for generating a set of complementary PWM driving signals, and the driving circuit isolates and boosts the received PWM driving signals from the controller to form the switching tube S of the main circuit1、S2、Q1~Q4A driving voltage is provided.
3. The method according to claim 1, wherein the switch tube S is connected to the power supply1、S2、Q1~Q4The switch tube is a parasitic capacitor with a body diode and a drain source electrode which are connected in an anti-parallel mode.
4. The method according to claim 1, wherein the switch tube S is connected to the power supply1And Q1、Q4Is identical with the drive signal of S2And Q2、Q3Is consistent, ignoring dead time, S1And S2The driving signals are complementary, the duty ratio of the driving signals is fixed to be 50%, and the driving signals of the switching tubes in positive and negative operation are consistent.
5. A control method for a topology of a component-capacitive power supply according to claim 1, wherein the LLC resonant converter has an input voltage V at a switching frequency not higher than a resonant frequencydAnd an output voltage V0The proportional relationship, independent of load variations, can be considered to be DCX, i.e.
Vd=kV0=2nV0
Wherein k is LLC resonant converter input voltage VdAnd an output voltage V0N is the transformation ratio of the transformer.
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Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102437628A (en) * 2011-10-22 2012-05-02 华北电力大学(保定) Storage battery reduction charge-discharge converter circuit
CN107733236A (en) * 2017-10-27 2018-02-23 深圳市保益新能电气有限公司 A kind of two-way Sofe Switch DC transfer circuit of wide scope and its control method
CN110027490A (en) * 2019-03-21 2019-07-19 中南大学 A kind of automobile double power voltage supply system and its control method

Family Cites Families (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR101031217B1 (en) * 2009-10-21 2011-04-27 주식회사 오리엔트전자 Two-stage bidirectional isolated dc/dc power converter using fixed duty llc resonant converter
CN103780099A (en) * 2014-01-21 2014-05-07 广东易事特电源股份有限公司 Bi-directional direct current switching circuit and switching power supply
CN105634286A (en) * 2016-01-28 2016-06-01 山东鲁能智能技术有限公司 Bidirectional full-bridge converter-based wide-output voltage range control method for soft switching

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102437628A (en) * 2011-10-22 2012-05-02 华北电力大学(保定) Storage battery reduction charge-discharge converter circuit
CN107733236A (en) * 2017-10-27 2018-02-23 深圳市保益新能电气有限公司 A kind of two-way Sofe Switch DC transfer circuit of wide scope and its control method
CN110027490A (en) * 2019-03-21 2019-07-19 中南大学 A kind of automobile double power voltage supply system and its control method

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