CN112311245B - High-frequency intermittent control system and method of bidirectional series resonant converter - Google Patents

High-frequency intermittent control system and method of bidirectional series resonant converter Download PDF

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CN112311245B
CN112311245B CN202011230886.0A CN202011230886A CN112311245B CN 112311245 B CN112311245 B CN 112311245B CN 202011230886 A CN202011230886 A CN 202011230886A CN 112311245 B CN112311245 B CN 112311245B
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pin
output
frequency
inversion
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CN112311245A (en
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岳浩江
董翰林
方支剑
谢非
孙皓天
魏治国
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China University of Geosciences
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33584—Bidirectional converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses a high-frequency intermittent control system and a method suitable for a bidirectional series resonant converter, which comprise a first filter circuit, a first inversion/rectification circuit, a resonant circuit, a high-frequency transformer, a second inversion/rectification circuit, a second filter circuit, a voltage and current acquisition circuit, a controller and a drive circuit, wherein the first filter circuit is connected with the first inversion/rectification circuit; the bidirectional series resonant converter can realize the functions of voltage reduction and voltage increase at the same time, a wider working range is realized, all switches realize wide-range zero-current switching, and the switching loss is reduced. Pulse control is added in the switching period and the pulses can be up to half the resonant frequency, thereby reducing the voltage ripple. The control strategy can enable the system to have a linear power transmission characteristic, and the system characteristic is simple and easy to operate.

Description

High-frequency intermittent control system and method of bidirectional series resonant converter
Technical Field
The invention relates to the technical field of power electronics and power automation equipment, in particular to a high-frequency intermittent control system and method of a bidirectional series resonant converter.
Background
The bidirectional resonant converter is a device capable of enabling direct current electric energy to flow bidirectionally, and can be a bridge between power systems with different connection voltage grades. However, since the voltage variation of the lithium ion battery on the charging side and the discharging side during charging and discharging is generally large, the bidirectional DC-DC converter must have a wide gain range. In addition, the DC-DC converter needs to achieve high efficiency not only under heavy load, but also under light load, high transmission efficiency is required to ensure the charging process of the battery. The main solutions currently in use are the following two types:
(1) a hybrid modulation scheme of frequency-variable modulation and phase-shift modulation (VFM + PSM), where frequency-variable modulation is used for implementation and phase-shift modulation is used to increase the gain range of the converter.
The method can reduce energy loss in the transmission process, but when the load is light, the operating frequency requirement of the method is high, and the method cannot be easily realized in practical application.
(2) And pulse control is carried out, and the converter realizes high-performance transmission power under the condition of light load through controlling the switch.
However, in the mainstream pulse control at present, the pulse frequency is very low, which causes large voltage ripple and affects the normal operation of the circuit. Therefore, a control method of the bidirectional resonant converter is needed, which has the advantages of convenient control, good light-load working condition, small voltage ripple, and better dynamic response performance and stability.
Disclosure of Invention
In view of the above, the present invention provides a system and a method for controlling a bidirectional series resonant converter intermittently at a high frequency.
A high-frequency intermittent control system of a bidirectional series resonant converter comprises a first input power supply, a first filter circuit, a first inversion/rectification circuit, a resonant circuit, a high-frequency transformer, a second inversion/rectification circuit, a second filter circuit, a second input power supply, a first voltage and current acquisition circuit, a second voltage and current acquisition circuit, a first controller, a second controller, a first drive circuit and a second drive circuit;
the output end of the first input power supply is connected with the input end of the first filter circuit, and the feedback end of the first filter circuit is connected with the input end of the first voltage and current acquisition circuit; the output end of the first voltage and current acquisition circuit is connected with the input end of the first controller, the output end of the first controller is connected with the driving circuit, and the output end of the first driving circuit is connected with the first input end of the second inversion/rectification circuit;
the output end of the first filter circuit is connected with the first input end of the first inversion/rectification circuit, the input end of the resonance circuit is connected with the output end of the first inversion/rectification circuit, and the output end of the resonance circuit is connected with the input end of the high-frequency transformer; the output end of the high-frequency transformer is connected with the second input end of the second inversion/rectification circuit; the output end of the second inversion/rectification circuit is connected with the input end of the second filter circuit; the output end of the second filter circuit is used for being connected with a second input power supply, and the feedback end of the second filter circuit is connected with the input end of the voltage and current acquisition circuit; the output end of the second voltage and current acquisition circuit is connected to the input end of the second controller, the output end of the second controller is connected to the input end of the second driving circuit, and the output end of the second driving circuit is connected with the second input end of the first inversion/rectification circuit.
Further, the high-frequency intermittent control system of the bidirectional series resonant converter enables direct current to flow bidirectionally, wherein the working mode of energy transmission from the first input power supply to the second input power supply is a forward transmission mode, and the working mode of energy transmission from the second input power supply to the first input power supply is a reverse transmission mode.
Furthermore, the first filter circuit is a direct current filter capacitor C1First inverter/rectifier circuit switching tube S3Pin 2 and switch tube S4Pin 1 of the resonant converter is connected with the first filter circuit of the resonant converter, wherein the switching tube S1And S3Pin 1 for connecting filter capacitor C1Positive electrode of (2), switching tube S1And S3Pin 2 for connecting filter capacitor C1The first filter circuit is used for filtering harmonic waves in current output by the rectifying circuit in a reverse transmission mode and providing stable direct current energy for the first input power supply.
Furthermore, the first inversion/rectification circuit comprises four identical switching tubes S1～S4Each switching tube S1-S4Pin 1 and pin2 are connected with a group of diodes and buffer capacitors in parallel respectively, wherein the anode of the diode is connected with a pin 2 corresponding to the switch tube, the cathode is connected with a pin 1 corresponding to the switch tube, and the switch tube S1Pin 2 and switch tube S2Pin 1 is connected between two output ends of a first input power supply, and a switching tube S3Pin 2 and switch tube S4The pin 1 is connected and then used for connecting between two output ends of a first input power supply; wherein, the switch tube S1And S3Pin 1 for connecting a first input power supply and a reverse filter capacitor C1Positive electrode of (2), switching tube S2And S4Pin 2 for connecting a first input power supply and a reverse filter capacitor C1Negative electrode of (2), switching tube S1-S4Selected types include MOSFETs, BJTs and IGBTs.
Furthermore, the resonance circuit adopts a series LC resonance circuit comprising an inductor and a capacitor, and the series LC resonance circuit comprises a resonance inductor LrAnd a resonant capacitor CrResonant capacitor CrOne end of the first inverter/rectifier circuit is connected with a switching tube S1Pin 2, the other end is connected in series with a resonance inductor Lr，LrThe other end of the switch tube S is connected with the switch tube S3Pin 2 of the transformer is connected with one end of the primary side of the high-frequency transformer.
Furthermore, the high-frequency transformer is a high-frequency isolation transformer, and one end of the primary side of the high-frequency isolation transformer is connected with a resonant inductor LrAnd a switching tube S3Pin 2, the other end of the primary side is connected to a third switch tube S3And a fourth switching tube S4Under the excitation of the square wave voltage output by the first inverter/rectifier circuit, the resonant inductor L of the resonant circuitrResonant capacitor CrThe equivalent excitation inductance of the primary side of the high-frequency isolation transformer generates a high-frequency resonant current which is approximate to sine and is transmitted to the secondary side of the high-frequency isolation transformer through the primary side of the high-frequency isolation transformer.
Furthermore, the second inversion/rectification circuit has four same switching tubes S5～S8Each switching tube S5-S8Pin 1 and pin 2 are respectively connected with one group anda diode and a buffer capacitor connected in series, wherein the anode of the diode is connected with a pin 2 corresponding to the switch tube, the cathode is connected with a pin 1 corresponding to the switch tube, and the switch tube S5Pin 2 and switch tube S6Pin 1 is connected to be connected between two output ends of a second input power supply, and a switching tube S7Pin 2 and switch tube S8The pin 1 is connected and then used for connecting between two output ends of a second input power supply; wherein, the switch tube S5And S7Pin 1 and pin 2 of (2) are used for connecting the output end of the high-frequency transformer, S5And S7Pin 1 of the filter is used for connecting a second input power supply and a filter capacitor C2Positive electrode of (2), S6And S8Pin 2 for connecting a second input power supply and a filter capacitor C2Negative electrode of (2), switching tube S5-S8Types of (d) include MOSFETs, BJTs and IGBTs.
Furthermore, the second filter circuit is a DC filter capacitor C2Second inverter/rectifier circuit switching tube S7Pin 2 and switch tube S8Pin 1 is connected for connection to both ends of a second filter circuit, wherein a switching tube S5And S7Pin 1 for connecting filter capacitor C2Positive electrode of (2), switching tube S6And S8Pin 2 for connecting filter capacitor C2And the second filter circuit is used for filtering harmonic waves in the current output by the rectifying circuit in the forward transmission mode and providing stable direct current energy for the second input power supply.
A high-frequency intermittent control method of a bidirectional series resonant converter is used for any one of the high-frequency intermittent control systems of the bidirectional series resonant converter, and comprises the following steps:
s101: collecting voltage value V of first input power supply1A current value I output by the first inversion/rectification circuit1And a voltage value V of the second input power supply2A current value I output by the second inverter/rectifier circuit2The power P output by the first inversion/rectification circuit is calculated by the controller1And power P output by the second inverter/rectifier circuit2；
S102: determining reference power PrefIf P is positive or negativerefIf > 0, the converter works in the forward direction, and the step S103 is carried out, Pref< 0, the inverter operates in reverse, step S104, where PrefIs the set value of the output power;
s103: judgment V1And nV2If V is a magnitude relation of1≤nV2Step S105 is executed to step S105 if the converter is boosted in the forward direction1＞nV2Step S107 is executed after the converter forward voltage reduction;
s104: judgment V1And nV2If V is a magnitude relation of1≤nV2Step S108 is performed, if V is reached, the converter is reversely reduced1＞nV2Step S106 is executed;
s105: according to the formula fs＝Kp1e1+Ki1×(∫e1dt+C1) Obtaining an operating frequency command fsGenerating duty ratio of 0.5 and working frequency of fsPWM signal for controlling the switch S1、S2，S5-S8According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S3And S4Wherein S is1And S5Same phase, S2And S6Same phase, S8Relative to S2Hysteresis TrTime; s1、S2Complementary phase, S5、S6Complementary phase, S7、S8Complementary in phase, during a working period TsIn the first half period, S4Relative to S2Lead TrTime, S3And S2In phase; in the second half period, S3Relative to S1Lead TrTime, S4And S1Turning to step S109 in the same phase;
wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e1In order to be able to measure the power error,e1＝Pref－P2，Kp1and Ki1Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C1C in the current beat calculation as an integral constant1Integral e with last beat calculation1dt+C1Value of (C) at the time of the first calculation1＝0，PrefTo output power set point, P2The output power value of the second inversion/rectification circuit;
s106: according to the formula fs＝Kp1e1+Ki1×(∫e1dt+C1) Obtaining an operating frequency command fsGenerating duty ratio of 0.5 and working frequency of fsPWM signal for controlling the switch S1-S4，S5、S6According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S7And S8(ii) a Wherein S is5And S1Same phase, S6And S2Same phase, S4Relative to S6Hysteresis TrTime; s5、S6Complementary phase, S1、S2Complementary phase, S3、S4Complementary in phase, during a working period TsIn the first half period, S8Relative to S6Lead TrTime, S7And S6In phase; in the second half period, S7Relative to S5Lead TrTime, S8And S5Turning to step S109 in the same phase;
wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e1As power error, e1＝Pref－P1，Kp1And Ki1Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C1C in the current beat calculation as an integral constant1Integral e with last beat calculation1dt+C1The value of (A), first countingTime calculation C1＝0，PrefTo output power set point, P1The output power value of the first inversion/rectification circuit;
s107: according to the formula fs＝Kp2e2+Ki2×(∫e2dt+C2) Obtaining an operating frequency command fsGenerating duty ratio of 0.5 and working frequency of fsPWM signal for controlling the switch S1-S4，S5、S6According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S7And S8Wherein S is1And S5Same phase, S2And S6Same phase, S4Relative to S2Tr time ahead; s1、S2Complementary phase, S3、S4Complementary phase, S5、S6Complementary in phase, during a working period TsIn the first half period, S8And S4Same phase, S7And S6In phase; in the second half period, S7And S3Same phase, S8And S1Turning to step S109 in the same phase;
wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e2As power error, e2＝Pref－P2，Kp2And Ki2Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C2C in the current beat calculation as an integral constant2Integral e with last beat calculation2dt+C2Value of (C) at the time of the first calculation2＝0，PrefTo output power set point, P2The output power value of the second inversion/rectification circuit;
s108: according to the formula fs＝Kp2e2+Ki2×(∫e2dt+C2) Obtaining an operating frequency command fsGenerating duty ratio of 0.5, operating frequencyIs fsPWM signal for controlling the switch S1、S2，S5-S8According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S3And S4Wherein S is5And S1Same phase, S6And S2Same phase, S8Relative to S6Lead TrTime; s5、S6Complementary phase, S7、S8Complementary phase, S1、S2Complementary in phase, during a working period TsIn the first half period, S4And S8Same phase, S3And S2In phase; in the second half period, S3And S7Same phase, S4And S5Turning to step S109 in the same phase;
wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e2As power error, e2＝Pref－P1，Kp2And Ki2Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C2C in the current beat calculation as an integral constant2Integral e with last beat calculation2dt+C2Value of (C) at the time of the first calculation2＝0，PrefTo output power set point, P1The output power value of the first inversion/rectification circuit;
s109: and (4) transmitting the PWM signals to corresponding switching tubes, and finishing the work after the transmission process is finished.
Further, the output power proportionality coefficient Kp1And the output power integral coefficient Ki1The determination process of (2) is:
s201: will Ki1The initial value is 0;
s202: debugging K firstp1Checking whether the output power waveform of the high-frequency intermittent control system of the bidirectional series resonant converter oscillates or not, if so, reducing Kp1Up to waveShape oscillation elimination, turning to process S203; otherwise, the process S202 continues debugging Kp1Until the waveform oscillation is eliminated;
s203: fixed Kp1Value, debug Ki1Checking whether the output power waveform fluctuates at the moment, if so, reducing Ki1Until the waveform oscillation is eliminated; otherwise, continue debugging Ki1Until the waveform oscillation is eliminated;
s204: will Kp1And Ki1The final value of (a) is used as the output power proportionality coefficient Kp1And the output power integral coefficient Ki1。
Further, the output power proportionality coefficient Kp2And the output power integral coefficient Ki2The determination process of (2) is:
s301: will Ki2The initial value is 0;
s302: debugging K firstp2Checking whether the output power waveform of the high-frequency intermittent control system of the bidirectional series resonant converter oscillates or not, if so, reducing Kp2Until the waveform oscillation is eliminated, the process is switched to S303; otherwise, continue debugging Kp2Until the waveform oscillation is eliminated;
s303: fixed Kp2Value, debug Ki2Checking whether the output power waveform fluctuates at the moment, if so, reducing Ki2Until the waveform oscillation is eliminated; otherwise, continue debugging K2Until the waveform oscillation is eliminated;
s304: finally obtaining the output power proportionality coefficient Kp2And the output power integral coefficient Ki2。
The technical scheme provided by the invention has the beneficial effects that: the bidirectional DC-DC series resonant converter simultaneously realizes the functions of boosting and reducing voltage and realizes a wide gain range; the operation of the converter in a half switching period is divided into a working state and a silent state, in the working state, the high pulse frequency can effectively reduce voltage ripple, and in the silent state, energy stored in the working state of the resonant network generates pulse control oscillation to release the energy to a load, so that the oscillation is inhibited. All switches are switched on or off when the resonant current is zero, so that the equipment realizes wide-range zero-current switching, and the switching loss is reduced.
Drawings
FIG. 1 is a schematic diagram of a high frequency intermittent control system and method of a bi-directional series resonant converter of the present invention;
FIG. 2 is a circuit diagram of an embodiment of a system and method for high frequency intermittent control of a bi-directional series resonant converter of the present invention;
FIG. 3 is a control flow chart of the high frequency intermittent control system and method of the bidirectional series resonant converter of the present invention;
FIG. 4 is a schematic diagram of the switching tube driving signals of the high-frequency intermittent control system and method of the bidirectional series resonant converter in the boost mode according to the present invention;
fig. 5 is a schematic diagram of the switching tube driving signals of the high-frequency intermittent control system and method of the bidirectional series resonant converter in the buck mode according to the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, embodiments of the present invention will be further described with reference to the accompanying drawings.
For a more clear understanding of the technical features, objects and effects of the present invention, embodiments of the present invention will now be described in detail with reference to the accompanying drawings. Referring to fig. 1 and fig. 2, fig. 1 and fig. 2 show a schematic diagram of a high-frequency intermittent control system of a bidirectional series resonant converter according to the present invention and a circuit diagram of an embodiment of the high-frequency intermittent control system.
The high-frequency intermittent control system of the bidirectional series resonant converter of the present embodiment can enable direct current electric energy to flow bidirectionally, and includes a first input power supply 1, a first filter circuit 2, a first inverter/rectifier circuit 3, a resonant circuit 4, a high-frequency transformer 5, a second inverter/rectifier circuit 6, a second filter circuit 7, a second input power supply 8 voltage and current acquisition circuit 91, a voltage and current acquisition circuit 92, a first controller 101, a second controller 102, a first driving circuit 111, and a second driving circuit 112;
the output end of the first input power supply 1 is connected with the input end of the first filter circuit 2, and the feedback end of the first filter circuit 2 is connected with the input end of the first voltage and current acquisition circuit 91; the output end of the first voltage and current acquisition circuit 91 is connected with the input end of the first controller 101, the output end of the first controller 101 is connected with the first driving circuit 111, and the output end of the first driving circuit 111 is connected with the first input end of the second inversion/rectification circuit 6;
the output end of the first filter circuit 2 is connected with the first input end of the first inversion/rectification circuit 3, the input end of the resonance circuit 4 is connected with the output end of the first inversion/rectification circuit 3, and the output end of the resonance circuit 4 is connected with the input end of the high-frequency transformer 5; the output end of the high-frequency transformer 5 is connected with the second input end of the second inversion/rectification circuit 6; the output end of the second inversion/rectification circuit is connected with the input end of the second filter circuit 7; the output end of the second filter circuit 7 is used for connecting with the second input power supply 8, and the feedback end of the second filter circuit 7 is connected with the input end of the second voltage and current acquisition circuit 92; the output end of the second voltage and current collecting circuit 92 is connected to the input end of the second controller 102, the output end of the second controller 102 is connected to the input end of the second driving circuit 112, and the output end of the second driving circuit 112 is connected to the second input end of the first inverter/rectifier circuit 3.
The high-frequency intermittent control system of the bidirectional series resonant converter enables direct current to flow bidirectionally, wherein the working mode of energy transmission from the first input power supply 1 to the second input power supply 8 is a forward transmission mode, and the working mode of energy transmission from the second input power supply 8 to the first input power supply 1 is a reverse transmission mode.
The first filter circuit 2 and the second filter circuit 7 include: an LC filter circuit, a CL filter circuit, and an LCL filter circuit.
The resonant circuit 4 adopts a resonant circuit containing an inductor and a capacitor, and comprises: a series resonant circuit, a parallel resonant circuit, a series-parallel resonant circuit, an LLC resonant circuit, a CLC resonant circuit, and an LCL resonant circuit.
The high-frequency transformer 5 comprises a high-frequency isolation transformer, a high-frequency autotransformer and a high-frequency transformer with a center tap.
The first filter circuit 2 is a DC filter capacitor C1First inverter/rectifier circuit 3 switching tube S3Pin 2 and switch tube S4Pin 1 is connected for connection to both ends of a first filter circuit 2, wherein a switching tube S1And S3Pin 1 for connecting filter capacitor C1Positive electrode of (2), switching tube S1And S3Pin 2 for connecting filter capacitor C1The first filter circuit 2 is used for filtering out harmonic waves in the current output by the rectifying circuit in a reverse transmission mode, and providing stable direct current energy for the first input power supply.
The first inverter/rectifier circuit 3 adopts a full-bridge voltage type converter for converting the DC voltage of the input power supply into periodically-changing square wave voltage with symmetrical positive and negative half periods according to the driving signal output by the driving circuit 11, and the voltage V of the first input power supply 11Has a range of 240V-480V, a rated voltage of 400V and a current I1In the range of 0-2.5A.
The first inversion/rectification circuit 3 comprises four same switching tubes S1～S4Each switching tube S1-S4A group of diodes and buffer capacitors connected in parallel are respectively connected between the pin 1 and the pin 2, wherein the anode of the diode is connected with the pin 2 corresponding to the switch tube, the cathode is connected with the pin 1 corresponding to the switch tube, and the switch tube S1Pin 2 and switch tube S2Pin 1 is connected for connection between two output terminals of a first input power supply 1, a switching tube S3Pin 2 and switch tube S4The pins 1 are connected and then used for being connected between two output ends of a first input power supply 1; wherein, the switch tube S1And S3Pin 1 for connecting a first input power supply 1 and a reverse filter capacitor C1Positive electrode of (2), switching tube S2And S4Pin 2 for connecting a first input power supply 1 and a reverse filter capacitor C1Negative electrode of (2), switching tube S1-S4Selected types include MOSFETs, BJTs and IGBTs.
The resonance circuit 4 adopts a series LC resonance circuit comprising an inductor and a capacitor and is used for generating high-frequency resonance current under the excitation of square wave voltage, and a resonance inductor Lr50 muH, resonant capacitance Cr12nF, resonant frequency 200 kHz; the series LC resonant circuit comprises a resonant inductor LrAnd a resonant capacitor CrResonant capacitor CrOne end of the first inverter/rectifier circuit 3 is connected with a switching tube S1Pin 2, the other end is connected in series with a resonance inductor Lr，LrThe other end of the switch tube S is connected with the switch tube S3Pin 2 of the transformer is connected with one end of the primary side of the high-frequency transformer 5.
The high-frequency transformer 5 is a high-frequency isolation transformer and is used for amplifying or reducing high-frequency resonance voltage and current, and the transformation ratio is 8: 1; one end of the primary side of the high-frequency isolation transformer is connected with a resonant inductor LrAnd a switching tube S3Pin 2, the other end of the primary side is connected to a third switch tube S3And a fourth switching tube S4Under the excitation of the square wave voltage output by the first inverter/rectifier circuit 3, the resonant inductor L of the resonant circuit 4rResonant capacitor CrThe equivalent excitation inductance of the primary side of the high-frequency isolation transformer generates a high-frequency resonant current which is approximate to sine and is transmitted to the secondary side of the high-frequency isolation transformer through the primary side of the high-frequency isolation transformer.
The second inverter/rectifier circuit 6 adopts a full-bridge circuit, is used as a full-wave rectifier circuit in a forward transmission mode, and is used for converting high-frequency resonance current into direct current and secondary side voltage; in reverse transmission mode, the voltage converter is used as a full-bridge voltage type converter for converting the DC voltage input to the power supply into periodically-changed square-wave voltages with positive and negative half-period symmetry and secondary side voltage V2In the range of 24-56V, rated voltage of 48V, current I2In the range of 0-20A.
The second inversion/rectification circuit 6 has four same switching tubes S5～S8Each switching tube S5-S8Pin 1 and pin 2 are connected with a group of diodes and buffer capacitors in parallel respectively, wherein the anodes of the diodes are connected with corresponding switchesPin 2 of switch tube, pin 1 of switch tube connected to cathode, and switch tube S5Pin 2 and switch tube S6Pin 1 is connected for connection between two output terminals of a second input power supply 2, a switching tube S7Pin 2 and switch tube S8The pin 1 is connected and then used for connecting between two output ends of a second input power supply 2; wherein, the switch tube S5And S7Pin 1 and pin 2 of (2) are used for connecting the output end of a high-frequency transformer 5, S5And S7Pin 1 for connecting a second input power supply 8 and a filter capacitor C2Positive electrode of (2), S6And S8Pin 2 for connecting a second input power supply 8 and a filter capacitor C2Negative electrode of (2), switching tube S5-S8Types of (d) include MOSFETs, BJTs and IGBTs.
The second filter circuit 7 is a DC filter capacitor C2Second inverter/rectifier circuit 6 switch tube S7Pin 2 and switch tube S8Pin 1 of the first filter circuit is connected for connection to two ends of a second filter circuit 7, wherein a switch tube S5And S7Pin 1 for connecting filter capacitor C2Positive electrode of (2), switching tube S6And S8Pin 2 for connecting filter capacitor C2And the second filter circuit 7 is used for filtering out harmonic waves in the current output by the rectifying circuit in the forward transmission mode and providing stable direct current energy for the second input power supply 8.
Referring to fig. 3, a high-frequency intermittent control method for a bidirectional series resonant converter is used in any one of the high-frequency intermittent control systems for a bidirectional series resonant converter, and includes the following steps:
(1) collecting a voltage value V of a first input power supply 11A current value I output by the first inverter/rectifier circuit 31And the voltage value V of the second input power supply 82A current value I output by the second inverter/rectifier circuit 62The power P output by the first inversion/rectification circuit 3 is calculated by the controller1And the power P output by the second inverter/rectifier circuit 62；
(2) Determining reference power PrefIf P is positive or negativerefIf more than 0, the converter works in the forward direction, step (3) is carried out, Pref< 0, the inverter operates in reverse, step (4) is carried out, wherein PrefIs the set value of the output power;
(3) judgment V1And nV2If V is a magnitude relation of1≤nV2Step (5), if V is1＞nV2The converter forward steps down, and then step (7) is carried out;
(4) judgment V1And nV2If V is a magnitude relation of1≤nV2Step (8) is carried out, if V is1＞nV2The converter boosts the voltage in the reverse direction, and then the step (6) is performed;
(5) according to the formula fs＝Kp1e1+Ki1×(∫e1dt+C1) Obtaining an operating frequency command fsGenerating duty ratio of 0.5 and working frequency of fsPWM signal for controlling the switch S1、S2，S5-S8According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S3And S4Wherein S is1And S5Same phase, S2And S6Same phase, S8Relative to S2Hysteresis TrTime; s1、S2Complementary phase, S5、S6Complementary phase, S7、S8Complementary in phase, during a working period TsIn the first half period, S4Relative to S2Lead TrTime, S3And S2In phase; in the second half period, S3Relative to S1Lead TrTime, S4And S1In phase, turning to step (9);
wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e1As power error, e1＝Pref－P2，Kp1And Ki1Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C1C in the current beat calculation as an integral constant1Integral e with last beat calculation1dt+C1Value of (C) at the time of the first calculation1＝0，PrefTo output power set point, P2The output power value of the second inversion/rectification circuit;
(6) according to the formula fs＝Kp1e1+Ki1×(∫e1dt+C1) Obtaining an operating frequency command fsGenerating duty ratio of 0.5 and working frequency of fsPWM signal for controlling the switch S1-S4，S5、S6According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S7And S8(ii) a Wherein S is5And S1Same phase, S6And S2Same phase, S4Relative to S6Hysteresis TrTime; s5、S6Complementary phase, S1、S2Complementary phase, S3、S4Complementary in phase, during a working period TsIn the first half period, S8Relative to S6Lead TrTime, S7And S6In phase; in the second half period, S7Relative to S5Lead TrTime, S8And S5In phase, turning to step (9);
wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e1As power error, e1＝Pref－P1，Kp1And Ki1Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C1C in the current beat calculation as an integral constant1Integral e with last beat calculation1dt+C1Value of (C) at the time of the first calculation1＝0，PrefFor setting the output power，P1The output power value of the first inversion/rectification circuit;
(7) according to the formula fs＝Kp2e2+Ki2×(∫e2dt+C2) Obtaining an operating frequency command fsGenerating duty ratio of 0.5 and working frequency of fsPWM signal for controlling the switch S1-S4，S5、S6According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S7And S8Wherein S is1And S5Same phase, S2And S6Same phase, S4Relative to S2Tr time ahead; s1、S2Complementary phase, S3、S4Complementary phase, S5、S6Complementary in phase, during a working period TsIn the first half period, S8And S4Same phase, S7And S6In phase; in the second half period, S7And S3Same phase, S8And S1In phase, turning to step (9);
wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e2As power error, e2＝Pref－P2，Kp2And Ki2Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C2C in the current beat calculation as an integral constant2Integral e with last beat calculation2dt+C2Value of (C) at the time of the first calculation2＝0，PrefTo output power set point, P2The output power value of the second inversion/rectification circuit;
(8) according to the formula fs＝Kp2e2+Ki2×(∫e2dt+C2) Obtaining an operating frequency command fsGenerating duty ratio of 0.5 and working frequency of fsPWM signal for controlling the switch S1、S2，S5-S8According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S3And S4Wherein S is5And S1Same phase, S6And S2Same phase, S8Relative to S6Lead TrTime; s5、S6Complementary phase, S7、S8Complementary phase, S1、S2Complementary in phase, during a working period TsIn the first half period, S4And S8Same phase, S3And S2In phase; in the second half period, S3And S7Same phase, S4And S5And (5) rotating to the step (9) in the same phase.
Wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e2As power error, e2＝Pref－P1，Kp2And Ki2Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C2C in the current beat calculation as an integral constant2Integral e with last beat calculation2dt+C2Value of (C) at the time of the first calculation2＝0，PrefTo output power set point, P1The output power value of the first inversion/rectification circuit;
(9) and (4) transmitting the PWM signals to corresponding switching tubes, and finishing the work after the transmission process is finished.
The output power proportional coefficient Kp1And the output power integral coefficient Ki1The determination process of (2) is:
(1) will Ki1The initial value is 0;
(2) debugging K firstp1Checking whether the output power waveform of the high-frequency intermittent control system of the bidirectional series resonant converter oscillates or not, if so, reducing Kp1Turning to the process (3) until the waveform oscillation is eliminated; otherwise, the process (2) is switched to continue debugging Kp1；
(3) Fixed Kp1Value, debug Ki1Checking whether the output power waveform fluctuates at the moment, if so, reducing Ki1Until the waveform oscillation is eliminated; otherwise, go to procedure (3) to continue debugging Ki1；
(4) Will Kp1And Ki1The final value of (a) is used as the output power proportionality coefficient Kp1And the output power integral coefficient Ki1。
The output power proportional coefficient Kp2And the output power integral coefficient Ki2The determination process of (2) is:
(1) will Ki2The initial value is 0;
(2) debugging K firstp2Checking whether the output power waveform of the high-frequency intermittent control system of the bidirectional series resonant converter oscillates or not, if so, reducing Kp2Turning to the process (3) until the waveform oscillation is eliminated; otherwise, the process (2) is switched to continue debugging Kp2；
(3) Fixed Kp2Value, debug Ki2Checking whether the output power waveform fluctuates at the moment, if so, reducing Ki2Until the waveform oscillation is eliminated; otherwise, go to procedure (3) to continue debugging K2；
(4) Finally obtaining the output power proportionality coefficient Kp2And the output power integral coefficient Ki2。
The previous description of the disclosed embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other embodiments without departing from the spirit or scope of the invention. Thus, the present invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.

Claims (1)

1. A high-frequency intermittent control method of a bidirectional series resonant converter is used for a high-frequency intermittent control system of the bidirectional series resonant converter and is characterized in that the high-frequency intermittent control system comprises a first input power supply (1), a first filter circuit (2), a first inversion/rectification circuit (3), a resonance circuit (4), a high-frequency transformer (5), a second inversion/rectification circuit (6), a second filter circuit (7), a second input power supply (8), a first voltage and current acquisition circuit (91), a second voltage and current acquisition circuit (92), a first controller (101), a second controller (102), a first drive circuit (111) and a second drive circuit (112);
the output end of the first input power supply (1) is connected with the input end of the first filter circuit (2), and the feedback end of the first filter circuit (2) is connected with the input end of the first voltage and current acquisition circuit (91); the output end of the first voltage and current acquisition circuit (91) is connected with the input end of a first controller (101), the output end of the first controller (101) is connected with a driving circuit (111), and the output end of the first driving circuit (111) is connected with the first input end of a second inversion/rectification circuit (6);
the output end of the first filter circuit (2) is connected with the first input end of the first inversion/rectification circuit (3), the input end of the resonance circuit (4) is connected with the output end of the first inversion/rectification circuit (3), and the output end of the resonance circuit (4) is connected with the input end of the high-frequency transformer (5); the output end of the high-frequency transformer (5) is connected with the second input end of the second inversion/rectification circuit (6); the output end of the second inversion/rectification circuit (6) is connected with the input end of the second filter circuit (7); the output end of the second filter circuit (7) is connected with a second input power supply (8), and the feedback end of the second filter circuit (7) is connected with the input end of the second voltage and current acquisition circuit (92); the output end of the second voltage and current acquisition circuit (92) is connected to the input end of a second controller (102), the output end of the second controller (102) is connected to the input end of a second driving circuit (112), and the output end of the second driving circuit (112) is connected with the second input end of the first inversion/rectification circuit (3);
the high-frequency intermittent control system of the bidirectional series resonant converter enables direct current to flow bidirectionally, wherein the working mode that energy is transmitted from the first input power supply (1) to the second input power supply (8) is a forward transmission mode, and the working mode that energy is transmitted from the second input power supply (8) to the first input power supply (1) is a reverse transmission mode;
the first filter circuit (2) is a direct current filter capacitor C1A first inversion/rectification circuit (3) switch tube S3Pin 2 and switch tube S4Pin 1 is connected for connection to both ends of a first filter circuit (2) of the resonant converter, wherein a switching tube S1And S3Pin 1 for connecting filter capacitor C1Positive electrode of (2), switching tube S1And S3Pin 2 for connecting filter capacitor C1The first filter circuit (2) is used for filtering harmonic waves in current output by the rectifying circuit in a reverse transmission mode and providing stable direct current energy for the first input power supply (1);
the first inversion/rectification circuit (3) comprises four same switching tubes S1～S4Each switching tube S1-S4A group of diodes and buffer capacitors connected in parallel are respectively connected between the pin 1 and the pin 2, wherein the anode of the diode is connected with the pin 2 corresponding to the switch tube, the cathode is connected with the pin 1 corresponding to the switch tube, and the switch tube S1Pin 2 and switch tube S2The pin 1 is connected and then used for being connected between two output ends of a first input power supply (1), and a switching tube S3Pin 2 and switch tube S4The pins 1 are connected and then are used for being connected between two output ends of a first input power supply (1); wherein, the switch tube S1And S3Pin 1 of the reverse filter is used for connecting a first input power supply (1) and a reverse filter capacitor C1Positive electrode of (2), switching tube S2And S4Pin 2 for connecting a first input power supply (1) to a reverse filter capacitor C1Negative electrode of (2), switching tube S1-S4The selected types comprise MOSFET, BJT and IGBT;
the resonance circuit (4) adopts a series LC resonance circuit comprising an inductor and a capacitor, and the series LC resonance circuit comprises a resonance inductor LrAnd a resonant capacitor CrResonant capacitor CrOne end of the first inverter/rectifier circuit (3) is connected with a switching tube S1Pin 2, the other end is connected in series with a resonance inductor Lr，LrThe other end of the switch tube S is connected with the switch tube S3The pin 2 is connected with one end of the primary side of the high-frequency transformer (5);
the high-frequency transformer (5) is a high-frequency isolation transformer, and one end of the primary side of the high-frequency isolation transformer is connected with a resonant inductor LrAnd a switching tube S3Pin 2, the other end of the primary side is connected to a third switch tube S3And a fourth switching tube S4Under the excitation of the square wave voltage output by the first inverter/rectifier circuit (3), the resonant inductor L of the resonant circuit (4)rResonant capacitor CrThe equivalent excitation inductance of the primary side of the high-frequency isolation transformer generates a high-frequency resonant current which is similar to a sine and is transmitted to the secondary side of the high-frequency isolation transformer through the primary side of the high-frequency isolation transformer;
the second inversion/rectification circuit (6) has four same switching tubes S5～S8Each switching tube S5-S8A group of diodes and buffer capacitors connected in parallel are respectively connected between the pin 1 and the pin 2, wherein the anode of the diode is connected with the pin 2 corresponding to the switch tube, the cathode is connected with the pin 1 corresponding to the switch tube, and the switch tube S5Pin 2 and switch tube S6The pin 1 is connected and then is used for being connected between two output ends of a second input power supply (8), and a switching tube S7Pin 2 and switch tube S8The pins 1 are connected and then are used for being connected between two output ends of a second input power supply (8); wherein, the switch tube S5And S7Pin 1 and pin 2 of (2) are used for connecting the output end of a high-frequency transformer (5), S5And S7Pin 1 of the filter is used for connecting a second input power supply (8) and a filter capacitor C2Positive electrode of (2), S6And S8Pin 2 for connecting a second input power supply (8) and a filter capacitor C2Negative electrode of (2), switching tube S5-S8Types of (d) include MOSFETs, BJTs and IGBTs;
the second filter circuit (7) is a direct current filter capacitor C2A second inverter/rectifier circuit (6) switching tube S7Pin 2 and switch tube S8Pin 1 is connected for connection to both ends of a second filter circuit (7), wherein a switching tube S5And S7Pin 1 for connecting filter capacitor C2Positive electrode of (2), switching tube S6And S8Pin 2 for connecting filter capacitorC2The second filter circuit (7) is used for filtering harmonic waves in the current output by the rectifying circuit in a forward transmission mode and providing stable direct current energy for the second input power supply (8);
the method comprises the following steps:
s101: collecting a voltage value V of a first input power supply (1)1A current value I output by the first inversion/rectification circuit (3)1And the voltage value V of the second input power supply (8)2A current value I output by the second inversion/rectification circuit (6)2The power P output by the first inversion/rectification circuit (3) is calculated by the controller1And the power P output by the second inversion/rectification circuit (6)2；
S102: determining reference power PrefIf P is positive or negativerefIf > 0, the converter works in the forward direction, and the step S103 is carried out, Pref< 0, the inverter operates in reverse, step S104, where PrefIs the set value of the output power;
s103: judgment V1And nV2If V is a magnitude relation of1≤nV2Step S105 is executed to step S105 if the converter is boosted in the forward direction1＞nV2Step S107 is executed after the converter forward voltage reduction;
s104: judgment V1And nV2If V is a magnitude relation of1≤nV2Step S108 is performed, if V is reached, the converter is reversely reduced1＞nV2Step S106 is executed;
s105: according to the formula fs＝Kp1e1+Ki1×(∫e1dt+C1) Obtaining an operating frequency command fsGenerating duty ratio of 0.5 and working frequency of fsPWM signal for controlling the switch S1、S2，S5-S8According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S3And S4Wherein S is1And S5Same phase, S2And S6Same phase, S8Relative to S2Hysteresis TrTime; s1、S2Complementary phase, S5、S6Complementary phase, S7、S8Complementary in phase, during a working period TsIn the first half period, S4Relative to S2Lead TrTime, S3And S2In phase; in the second half period, S3Relative to S1Lead TrTime, S4And S1Turning to step S109 in the same phase;
wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e1As power error, e1＝Pref－P2，Kp1And Ki1Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C1C in the current beat calculation as an integral constant1Integral e with last beat calculation1dt+C1Value of (C) at the time of the first calculation1＝0，PrefTo output power set point, P2The output power value of the second inversion/rectification circuit (6);
s106: according to the formula fs＝Kp1e1+Ki1×(∫e1dt+C1) Obtaining an operating frequency command fsGenerating duty ratio of 0.5 and working frequency of fsPWM signal for controlling the switch S1-S4，S5、S6According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S7And S8(ii) a Wherein S is5And S1Same phase, S6And S2Same phase, S4Relative to S6Hysteresis TrTime; s5、S6Complementary phase, S1、S2Complementary phase, S3、S4Complementary in phase, during a working period TsIn the first half period, S8Relative to S6Lead TrTime, S7And S6In phase;in the second half period, S7Relative to S5Lead TrTime, S8And S5Turning to step S109 in the same phase;
wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e1As power error, e1＝Pref－P1，Kp1And Ki1Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C1C in the current beat calculation as an integral constant1Integral e with last beat calculation1dt+C1Value of (C) at the time of the first calculation1＝0，PrefTo output power set point, P1The output power value of the first inversion/rectification circuit (3);
s107: according to the formula fs＝Kp2e2+Ki2×(∫e2dt+C2) Obtaining an operating frequency command fsGenerating duty ratio of 0.5 and working frequency of fsPWM signal for controlling the switch S1-S4，S5、S6According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S7And S8Wherein S is1And S5Same phase, S2And S6Same phase, S4Relative to S2Tr time ahead; s1、S2Complementary phase, S3、S4Complementary phase, S5、S6Complementary in phase, during a working period TsIn the first half period, S8And S4Same phase, S7And S6In phase; in the second half period, S7And S3Same phase, S8And S1Turning to step S109 in the same phase;
wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e2As power error, e2＝Pref－P2，Kp2And Ki2Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C2C in the current beat calculation as an integral constant2Integral e with last beat calculation2dt+C2Value of (C) at the time of the first calculation2＝0，PrefTo output power set point, P2The output power value of the second inversion/rectification circuit (6);
s108: according to the formula fs＝Kp2e2+Ki2×(∫e2dt+C2) Obtaining an operating frequency command fsGenerating duty ratio of 0.5 and working frequency of fsPWM signal for controlling the switch S1、S2，S5-S8According to D ═ fs/frGenerating a duty ratio of D and an operating frequency of fsPWM signal for controlling the switch S3And S4Wherein S is5And S1Same phase, S6And S2Same phase, S8Relative to S6Lead TrTime; s5、S6Complementary phase, S7、S8Complementary phase, S1、S2Complementary in phase, during a working period TsIn the first half period, S4And S8Same phase, S3And S2In phase; in the second half period, S3And S7Same phase, S4And S5Turning to step S109 in the same phase;
wherein f isrTo the resonant frequency, TrFor the resonance period, Tr＝1/fr；TsIs a duty cycle, Ts＝1/fs；e2As power error, e2＝Pref－P1，Kp2And Ki2Respectively an output power proportional coefficient and an output power integral coefficient, t is time, C2C in the current beat calculation as an integral constant2Integral e with last beat calculation2dt+C2Value of (C) at the time of the first calculation2＝0，PrefTo output power set point, P1The output power value of the first inversion/rectification circuit (3);
s109: sending the PWM signals to corresponding switch tubes, and finishing the work after the transmission process is finished;
the output power proportional coefficient Kp1And the output power integral coefficient Ki1The determination process of (2) is:
s201: will Ki1The initial value is 0;
s202: debugging K firstp1Checking whether the output power waveform of the high-frequency intermittent control system of the bidirectional series resonant converter oscillates or not, if so, reducing Kp1Until the waveform oscillation is eliminated, the process is switched to S203; otherwise, the process S202 continues debugging Kp1Until the waveform oscillation is eliminated;
s203: fixed Kp1Value, debug Ki1Checking whether the output power waveform fluctuates at the moment, if so, reducing Ki1Until the waveform oscillation is eliminated; otherwise, continue debugging Ki1Until the waveform oscillation is eliminated;
s204: will Kp1And Ki1The final value of (a) is used as the output power proportionality coefficient Kp1And the output power integral coefficient Ki1；
The output power proportional coefficient Kp2And the output power integral coefficient Ki2The determination process of (2) is:
s301: will Ki2The initial value is 0;
s302: debugging K firstp2Checking whether the output power waveform of the high-frequency intermittent control system of the bidirectional series resonant converter oscillates or not, if so, reducing Kp2Until the waveform oscillation is eliminated, the process is switched to S303; otherwise, continue debugging Kp2Until the waveform oscillation is eliminated;
s303: fixed Kp2Value, debug Ki2Checking whether the output power waveform fluctuates at the moment, if so, reducing Ki2Until the waveform oscillation is eliminated; otherwise, continue debugging K2Until the waveform oscillation is eliminated;
s304: finally obtaining the output power proportional coefficientKp2And the output power integral coefficient Ki2。
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