CN104993707A - Method of controlling bidirectional DC/DC converter based on LLC resonance - Google Patents
Method of controlling bidirectional DC/DC converter based on LLC resonance Download PDFInfo
- Publication number
- CN104993707A CN104993707A CN201510451866.9A CN201510451866A CN104993707A CN 104993707 A CN104993707 A CN 104993707A CN 201510451866 A CN201510451866 A CN 201510451866A CN 104993707 A CN104993707 A CN 104993707A
- Authority
- CN
- China
- Prior art keywords
- switching tube
- converter
- network
- full
- way
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Landscapes
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a method of controlling a bidirectional DC/DC converter based on LLC resonance. The method comprises the following steps that the two ends on the AC side of a first full-bridge switch network have voltages beyond zero during a first time period of one work cycle of the bidirectional DC/DC converter; and the voltage clamp of the two ends on the AC side of the first full-bridge switch network is set to be zero during other time periods from the first time period in one work cycle of the bidirectional DC/DC converter or during subordinate time periods of other time periods from the first time period. By adopting a common LLC resonant tank structure and additionally arranging no components, the method makes the LLC circuit forward running advantages maintained and meanwhile makes the normalization voltage gain greater than one during a reverse working process by adopting a unique and simple driving means when the circuit runs reversely.
Description
[technical field]
The present invention relates to the control method of the two-way DC/DC converter based on LLC resonance.
[background technology]
The existing two-way DC-DC converter based on LLC resonance is all the ability being obtained converter bidirectional voltage boosting by increase auxiliary induction or resonant capacitance, which not only adds the difficulty of circuit cost and design, and the operating characteristic of circuit under LLC mode of resonance also can change, converter resonance characteristic is deteriorated, loses the Sofe Switch advantage of topology.The two-way LLC topological structure of auxiliary induction is such as added at switching network brachium pontis mid point, although the ability that this kind of structure has bidirectional voltage boosting to run, but be the increase in a magnetic cell, and always have inductance during circuit working by resonant slots input voltage clamper, magnetic cell loss and saturation problem can be caused thus.Another is the CLLC topological structure (sometimes also referred to as two-way LLC) having the symmetry of resonant capacitance and resonant inductance in transformer both sides, although the characteristics symmetric of this kind of circuit structure way traffic, but its frequency-gain curve has multiple peak point, during variable frequency control, circuit may enter positive feedback, is unfavorable for control circui and parameter designing.
As shown in Figure 1, it is a kind of existing two-way DC/DC converter based on LLC resonance, comprise the first full-bridge switching network 1, resonant groove path, transformer T1, second switch network 2, first power supply V1 and second source V2, described first power supply V1 is connected with the input side of resonant groove path with transformer T1 by the first full-bridge switching network 1, and described second source V2 is connected with the outlet side of transformer T1 by second switch network 2.Here transformer T1 input side can be primary side or the primary side of transformer T1.When described first power supply V1 provides energy to second source V2, described first full-bridge switching network 1 is for being converted to alternating voltage by the direct voltage of described first power supply V1, and described second switch network 2 carries out rectification for the alternating voltage exported described transformer T1; When described second source V2 provides energy to the first power supply V1, described second switch network 2 is for being converted to alternating voltage by the direct voltage of described second source V2, and described first full-bridge switching network 1 carries out rectification for the alternating voltage exported described transformer T1.
First full-bridge switching network 1 comprises the first switching tube Q1, second switch pipe Q2, the 3rd switching tube Q3 and the 4th switching tube Q4, the two ends of the DC side of the first full-bridge switching network 1 are connected with the positive pole of the first power supply V1 and negative pole respectively, and the AC of the first full-bridge switching network 1 is connected with resonant groove path.First filter capacitor C1 is connected across the two ends of the first power supply V1.
Resonant groove path comprises the resonant inductance Lr, resonant capacitance Cr and the magnetizing inductance Lm that connect successively, wherein, two ports of the two ends of the magnetizing inductance Lm input side of connection transformer T1 respectively, the two ends of the AC of the first full-bridge switching network 1 are connected with the common port of transformer T1 with one end of resonant inductance Lr and magnetizing inductance Lm respectively.
Second switch network is a full-bridge switching network, comprise the 5th switching tube Q5, the 6th switching tube Q6, the 7th switching tube Q7 and the 8th switching tube Q8, the two ends of the DC side of second switch network are connected with the positive pole of second source V2 and negative pole respectively, the two ends of the AC of second switch network are connected with the two ends of the outlet side of transformer T1 respectively, second filter capacitor C2 and the 3rd filter capacitor C3 is connected across two ends, the centre tap of transformer T1 and the common port of the second filter capacitor C2 and the 3rd filter capacitor C3 of second source V2 after connecting.
[summary of the invention]
When second source V2 provides energy to the first power supply V1, adopt traditional driving method, as second switch pipe Q2 and the 3rd switching tube Q3, first switching tube Q1 and the 4th switching tube Q4 is synchronous with the sense of current in resonant groove path, wherein, when the electric current in resonant groove path will by second switch pipe Q2 and the 3rd switching tube Q3 time, second switch pipe Q2 and the 3rd switching tube Q3 conducting simultaneously (now the first switching tube Q1 and the 4th switching tube Q4 turns off simultaneously), when the electric current in resonant groove path will pass through the first switching tube Q1 and the 4th switching tube Q4, first switching tube Q1 and the 4th switching tube Q4 conducting simultaneously (now second switch pipe Q2 and the 3rd switching tube Q3 turns off simultaneously), magnetizing inductance Lm the whole cycle by clamper in exchange square-wave voltage in, magnetizing inductance Lm is made no longer to participate in resonant process, the gain characteristic of converter is also different from LLC resonance gain characteristic, deteriorate to LC resonant circuit structure, and the maximum voltage gain of LC resonant circuit is 1, namely transformer voltage ratio is not considered, the working method that can only be operated in step-down during circuit inverted running (is the relation curve between converter normalized voltage gain M and normalized frequency fn as shown in Figure 5, curve M 4, M5 and M6 is quality factor q=0.1 respectively, corresponding during Q=0.2 and Q=0.4, as can be seen from the figure, the normalized voltage gain M of converter is less than 1 in this case), this problem limits the application scenario of this kind of two-way LLC resonant circuit, also be unfavorable for selecting of parameter designing when circuit forward runs on LLC resonance and rated operation point simultaneously, limit the performance of LLC resonance advantage.
In order to overcome the above-mentioned technological deficiency of prior art, the invention provides a kind of control method of the two-way DC/DC converter based on LLC resonance, in general LLC resonant slots structure, normalized voltage gain during reverse operation can be made to be greater than 1.
Based on the control method of the two-way DC/DC converter of LLC resonance, described two-way DC/DC converter comprises the first full-bridge switching network, resonant groove path, transformer, second switch network, the first power supply and second source, the two ends of the DC side of described first full-bridge switching network are connected with the two ends of the first power supply respectively, connect described resonant groove path between the two ends of the AC of described first full-bridge switching network, described second source is connected with the outlet side of transformer by second switch network; It is characterized in that: described control method comprises the steps: when described second source provides energy to described first power supply,
In the first time period of a work period of described two-way DC/DC converter, the voltage at the two ends of the AC of described first full-bridge switching network is made to be in beyond 0, in the sub-time period of the time period beyond the first time period of a work period of described two-way DC/DC converter or the time period beyond described first time period, the voltage clamping at the two ends of the AC of described first full-bridge switching network is made to be 0.In one embodiment, the voltage clamping at the two ends of the AC of described first full-bridge switching network is made to be 0 in the following way:
Control one of them switching tube conducting of described first full-bridge switching network, or make source electrode and the drain electrode short circuit of one of them switching tube described;
Drive singal is not applied to its excess-three switching tube of described first full-bridge switching network, or apply synchronous rectification drive singal to all the other two each and every one switching tubes beyond one of them switching tube place brachium pontis described, described synchronous rectification drive singal is the signal with the current synchronization of described resonant groove path.
In one embodiment, source electrode and the drain electrode short circuit of one of them switching tube described is made by relay.
In one embodiment, described second switch network is full-bridge switching network.
In one embodiment, described second switch network comprises second switch network first switching tube and second switch network second switch pipe, described two-way DC/DC converter also comprises filter capacitor, described second switch network first switching tube and second switch network second switch pipe is connected in series, filter capacitor and second source described in the intermediate ends cross-over connection of the common port between described second switch network first switching tube and second switch network second switch pipe and the outlet side of described transformer between the two ends of the outlet side of described transformer.
In one embodiment, the switching tube of described first full-bridge switching network is MOSFET or IGBT.
In one embodiment, the switching tube of described second switch network is MOSFET or IGBT.
The invention has the beneficial effects as follows: the present invention is not when increasing components and parts, adopt general LLC resonant slots structure, while ensureing the advantage that LLC circuit forward runs, unique simple type of drive is taked when circuit inverted running, improve normalized voltage gain during reverse operation, can 1 be greater than in some cases, maximum can reach 2, improve the pressure regulation ability of converter way traffic, remain the Sofe Switch characteristic of circuit, the energy-storage system being specially adapted to bidirectional energy exchange is connected with the power conversion between DC bus simultaneously.
[accompanying drawing explanation]
Fig. 1 is the circuit theory diagrams of a kind of two-way DC/DC converter based on LLC resonance in prior art;
Fig. 2 is the another kind of circuit theory diagrams based on the two-way DC/DC converter of LLC resonance in prior art;
Oscillogram when Fig. 3 is the control method forward operation of a kind of two-way DC/DC converter based on LLC resonance of the present invention;
Oscillogram when Fig. 4 is the control method inverted running of a kind of two-way DC/DC converter based on LLC resonance of the present invention;
Normalized voltage gain during a kind of two-way DC/DC converter inverted running based on LLC resonance of Fig. 5 the present invention and existing comparison diagram.
[embodiment]
Below the preferred embodiment of invention is described in further detail.
As shown in figs. 1 and 3, when the first power supply V1 provides energy to second source V2, in two-way DC/DC converter, the oscillogram of portion voltage and electric current as shown in Figure 3.Symbol implication in Fig. 3 is: the control voltage of the vgs1: the first switching tube Q1, vgs2, vds2, ids2: the control voltage of second switch pipe Q2, the voltage between drain electrode and source electrode, the electric current between drain electrode and source electrode, ip: the electric current flowing through resonant capacitance Cr, is: the electric current of transformer T1 primary side.
The switching tube that first full-bridge switching network 1 and second switch network 2 adopt is MOSFET or IGBT, and the two ends of this kind of switching tube have junction capacitance and body diode, as shown in Figure 1.
Control method shown in Fig. 3 is also the method that prior art is commonly used.First switching tube Q1 and the 4th switching tube Q4 loads identical control voltage, second switch pipe Q2 and the 3rd switching tube Q3 loads identical control voltage, vgs1 and vgs2 is complementary and there is the control voltage in dead band, and by the effect of resonant groove path, at upper half, before vgs1 is high level, the body diode conducting of the first switching tube Q1 can be made, thus the first switching tube Q1 no-voltage conducting can be made, in like manner, second switch pipe Q2 also no-voltage conducting, therefore the first switching network 1 is operated in no-voltage conducting state.Simultaneously, synchronous rectification signal can be applied to the switching tube of second switch network 2, suppose that upper half is the 5th switching tube Q5 and the 8th switching tube Q8 conducting, then the electric current that the primary side of transformer T1 exports is powered to second source V2 through the rectification of the 5th switching tube Q5 and the 8th switching tube Q8.And when the first switching tube Q1 turns off, the primary side of transformer T1 and secondary side current are all zero, and the electric current of such 5th switching tube Q5 and the 8th switching tube Q8 is zero, thus achieve the zero-current switching of second switch network 2.By regulating the frequency of vgs1 and the operating frequency of converter, namely can regulate and the voltage of stable supplying second source V2.
In one embodiment, when second source V2 provides energy to the first power supply V1, in two-way DC/DC converter, the oscillogram of portion voltage and electric current as shown in Figure 4.Symbol implication in Fig. 4 is: the control voltage of the vgs1: the first switching tube Q1, the control voltage of the vgs6: the six switching tube Q6, vgs5, vds5, ids5: the control voltage of the 5th switching tube Q5, the voltage between drain electrode and source electrode, the electric current between drain electrode and source electrode, ip: the electric current flowing through resonant capacitance Cr.
5th switching tube Q5 and the 8th switching tube Q8 applies identical control voltage, 6th switching tube Q6 and the 7th switching tube Q7 applies identical control voltage, vgs1 is in high level (or duty ratio is 100%) all the time, to second switch pipe Q2, when 3rd switching tube Q3 and the 4th switching tube Q4 does not apply drive singal: at upper half, 5th switching tube Q5 and the 8th switching tube Q8 applies high level (vgs5), electric current flows out from the primary side of magnetizing inductance Lm and transformer T1, through resonant capacitance Cr, resonant inductance Lr, the body diode of second switch pipe Q2, first switching tube Q1 gets back to the primary side of magnetizing inductance Lm and transformer T1, current i p is greater than zero, within the time period of this half cycle, the voltage at the two ends of the AC of the first full-bridge switching network 1 is clamped to 0, the electric current of the primary side input of transformer T1 charges to a higher voltage value to resonant capacitance Cr.At lower half, vgs5 becomes low level, vgs6 becomes high level, current i p is reverse, electric current flows out from the primary side of magnetizing inductance Lm and transformer T1, through the first switching tube Q1, then the first power supply V1 is charged, and then through the body diode of the 4th switching tube Q4, resonant inductance Lr and resonant capacitance Cr, get back to the primary side of magnetizing inductance Lm and transformer T1, within the time period of this half cycle, the voltage at the two ends of the AC of the first full-bridge switching network 1 is in beyond 0, the primary side of resonant capacitance Cr and transformer T1 transfers its energy to the first power supply V1 jointly, the gain realizing converter is greater than the effect of 1.As shown in Figure 5, when curve M 1, M2 and M3 are Q=0.1, Q=0.2 and Q=0.4 under the present embodiment respectively, relation curve between the normalized voltage gain M of converter and normalized frequency fn, as can be seen from the figure, in the present embodiment, the normalized voltage gain M of converter is large than the normalized voltage gain M adopting the type of drive of prior art to obtain.
But, the conducting phase of the 5th switching tube Q5 can the minus half-cycle portions of corresponding ip, namely electric current flows to resonant capacitance Cr from resonant inductance Lr, this stage is the half cycle that the primary side of resonant capacitance Cr and transformer T1 transfers its energy to the first power supply V1 jointly, the factors such as this load with the first power supply V1 side are relevant, but this gain not affecting whole converter can be greater than 1.
In one embodiment, can to the switching tube of another brachium pontis of the first switching tube Q1 place brachium pontis, namely second switch pipe Q2 and the 4th switching tube Q4 applies synchronous rectification drive singal (the 3rd switching tube Q3 keeps turning off), and described synchronous rectification signal is the signal synchronous with the sense of current in resonant groove path.At upper half, second switch pipe Q2 and the 4th switching tube Q4 applies the rectification drive singal synchronous with current i p, second switch pipe Q2 and the 4th switching tube Q4 is placed in high level and low level respectively, electric current flows out from the primary side of magnetizing inductance Lm and transformer T1, gets back to the primary side of magnetizing inductance Lm and transformer T1 through resonant capacitance Cr, resonant inductance Lr, second switch pipe Q2, the first switching tube Q1.At lower half, current i p is reverse, second switch pipe Q2 and the 4th switching tube Q4 applies the rectification drive singal synchronous with current i p, second switch pipe Q2 and the 4th switching tube Q4 is placed in low level and high level respectively, electric current flows out from the primary side of magnetizing inductance Lm and transformer T1, through the first switching tube Q1, then charges to the first power supply V1, and then through the 4th switching tube Q4, resonant inductance Lr and resonant capacitance Cr, get back to the primary side of magnetizing inductance Lm and transformer T1.Equally, the conducting phase of the 5th switching tube Q5 can the minus half-cycle portions of corresponding ip, and namely electric current flows to resonant capacitance Cr from resonant inductance Lr.
In one embodiment, also can make source electrode and the drain electrode short circuit of the first switching tube Q1, it is equivalent to and applies duty ratio to the first switching tube Q1 is the control signal of 100%, and both can reach identical effect.Such as, Control can be utilized to make source electrode and the drain electrode short circuit of one of them switching tube described, when the first power supply V1 provides energy to second source V2, this relay can be disconnected.
In one embodiment, for first group of diagonal angle switching tube (the first switching tube Q1 place group) of the first full-bridge switching network, before the rectified current (direction is identical with resonance current ip) through it commutates (in the first time period of a converter work period, work period of converter is identical with the switch periods of now second switch network 2), be less than the drive singal of 100% until after its rectified current commutation with duty ratio can to the first switching tube Q1, like this in first time period, the voltage at the two ends of the AC of described first full-bridge switching network 1 is in beyond 0, electric current flows out from the primary side of magnetizing inductance Lm and transformer T1, through the first switching tube Q1 (if be high level at the drive singal applied, through the first switching tube Q1, if then through the body diode of the first switching tube Q1 during low level), then the first power supply V1 is charged, and then through the 4th switching tube Q4, resonant inductance Lr and resonant capacitance Cr, get back to the primary side of magnetizing inductance Lm and transformer T1.After the rectified current commutation through first group of diagonal angle switching tube, make the first switching tube Q1 triggering signal be in high level always, so during this period of time (in the remaining time section beyond a work period first time period), electric current flows out from the primary side of magnetizing inductance Lm and transformer T1, get back to the primary side of magnetizing inductance Lm and transformer T1 through resonant capacitance Cr, resonant inductance Lr, second switch pipe Q2, the first switching tube Q1, in remaining time section, make the voltage clamping to 0 at the two ends of the AC of the first full-bridge switching network 1 like this.After the rectified current commutation through first group of diagonal angle switching tube, the drive singal that also can be less than 100% to the first switching tube Q1 applying duty ratio, when in the sub-time period that drive singal high level is corresponding, the voltage at the two ends of the AC of the first full-bridge switching network 1 also will be clamped to 0, the effect that clamper is 0 can be played equally, thus improve the normalized voltage gain of converter.
In one embodiment, in a work period, in the time period only after the rectified current commutation through first group of diagonal angle switching tube (namely in remaining time section), the first switching tube Q1 can be made
triggering signalbe in high level (drive singal that also can be less than 100% to the first switching tube Q1 applying duty ratio) always, like this, also at least some sub-time period during this period of time, the voltage clamping to 0 at the two ends of the AC of the first full-bridge switching network 1 can be made.
In certain embodiments, within the work period of continuous multiple converter, type of drive traditionally controls the first full-bridge switching network 1, and then the some time periods in the next work period of closelying follow, make the voltage clamping to 0 at the two ends of the AC of the first full-bridge switching network 1, also can improve the normalized voltage gain of converter, the time period proportion that its normalized voltage gain is clamped to 0 with this is relevant with load.
In addition, because the first full-bridge switching network 1 is symmetrical, therefore, (applying duty ratio is the control signal of 100% can to substitute the first switching tube Q1 with all the other any one switching tubes, or make its source electrode and drain electrode short circuit), and drive singal is not applied to its excess-three switching tube of described first full-bridge switching network, or synchronous rectification drive singal is applied to its excess-three described switching tube.
In another embodiment, as shown in Figure 2, second switch network 2 can comprise the 5th switching tube Q5 and the 6th switching tube Q6, described two-way DC/DC converter also comprises filter capacitor C2, described 5th switching tube Q5 and the 6th switching tube Q6 is connected in series, filter capacitor C2 and second source V2 described in the intermediate ends cross-over connection of the outlet side of the common port between the 5th switching tube Q5 and the 6th switching tube Q6 and described transformer T1 between the two ends of the outlet side of described transformer T1.This structure of second switch network 2 can realize the function identical with the second switch network 2 shown in Fig. 1 equally.Such as, when the first power supply V1 provides energy to second source V2, when transformer T1 electric current upwards time, the 6th switching tube Q6 opens, the 5th switching tube Q5 closes, electric current to filter capacitor C2 charge after get back to transformer T1 through the 6th switching tube Q6; When the electric current of transformer T1 is downward, the 6th switching tube Q6 closes, the 5th switching tube Q5 opens, and electric current gets back to transformer T1 through the 5th switching tube Q5 after filter capacitor C2 charges.
Above content is in conjunction with concrete preferred implementation further description made for the present invention, can not assert that specific embodiment of the invention is confined to these explanations.For general technical staff of the technical field of the invention, without departing from the inventive concept of the premise, some simple deduction or replace can also be made, all should be considered as belonging to the scope of patent protection that the present invention is determined by submitted to claims.
Claims (7)
1. based on the control method of the two-way DC/DC converter of LLC resonance, described two-way DC/DC converter comprises the first full-bridge switching network, resonant groove path, transformer, second switch network, the first power supply and second source, the two ends of the DC side of described first full-bridge switching network are connected with the two ends of the first power supply respectively, connect described resonant groove path between the two ends of the AC of described first full-bridge switching network, described second source is connected with the outlet side of transformer by second switch network; It is characterized in that: described control method comprises the steps: when described second source provides energy to described first power supply,
In the first time period of a work period of described two-way DC/DC converter, the voltage at the two ends of the AC of described first full-bridge switching network is made to be in beyond 0, in the sub-time period of the time period beyond the first time period of a work period of described two-way DC/DC converter or the time period beyond described first time period, the voltage clamping at the two ends of the AC of described first full-bridge switching network is made to be 0.
2. as claimed in claim 1 based on the control method of the two-way DC/DC converter of LLC resonance, it is characterized in that, the voltage clamping making the two ends of the AC of described first full-bridge switching network is in the following way 0: one of them switching tube controlling described first full-bridge switching network applies drive singal, or makes source electrode and the drain electrode short circuit of one of them switching tube described;
Drive singal is not applied to its excess-three switching tube of described first full-bridge switching network, or apply synchronous rectification drive singal to two switching tubes of all the other beyond one of them switching tube place brachium pontis described, described synchronous rectification drive singal is the signal with the current synchronization of described resonant groove path.
3. as claimed in claim 1 based on the control method of the two-way DC/DC converter of LLC resonance, it is characterized in that: the source electrode and the drain electrode short circuit that are made one of them switching tube described by relay.
4., as claimed in claim 1 based on the control method of the two-way DC/DC converter of LLC resonance, it is characterized in that, described second switch network is full-bridge switching network.
5. as claimed in claim 1 based on the control method of the two-way DC/DC converter of LLC resonance, it is characterized in that, described second switch network comprises second switch network first switching tube and second switch network second switch pipe, described two-way DC/DC converter also comprises filter capacitor, described second switch network first switching tube and second switch network second switch pipe is connected in series between the two ends of the outlet side of described transformer, filter capacitor and second source described in the intermediate ends cross-over connection of the common port between described second switch network first switching tube and second switch network second switch pipe and the outlet side of described transformer.
6., as claimed in claim 1 based on the control method of the two-way DC/DC converter of LLC resonance, it is characterized in that, the switching tube of described first full-bridge switching network is MOSFET or IGBT.
7. the control method of the two-way DC/DC converter based on LLC resonance as described in claim 1 or 6, is characterized in that, the switching tube of described second switch network is MOSFET or IGBT.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201510451866.9A CN104993707A (en) | 2015-07-28 | 2015-07-28 | Method of controlling bidirectional DC/DC converter based on LLC resonance |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201510451866.9A CN104993707A (en) | 2015-07-28 | 2015-07-28 | Method of controlling bidirectional DC/DC converter based on LLC resonance |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN104993707A true CN104993707A (en) | 2015-10-21 |
Family
ID=54305474
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201510451866.9A Pending CN104993707A (en) | 2015-07-28 | 2015-07-28 | Method of controlling bidirectional DC/DC converter based on LLC resonance |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN104993707A (en) |
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105871215A (en) * | 2016-05-17 | 2016-08-17 | 华南理工大学 | Rectification control circuit for bidirectional CLLLC resonant converter |
| CN107124103A (en) * | 2016-02-25 | 2017-09-01 | 株式会社村田制作所 | DC/DC conversion equipments |
| CN108809104A (en) * | 2018-06-11 | 2018-11-13 | 南京航空航天大学 | A kind of two-way resonance converter and its control method of synchronous rectification |
| CN112311245A (en) * | 2020-11-06 | 2021-02-02 | 中国地质大学（武汉） | High-frequency intermittent control system and method of bidirectional series resonant converter |
| CN112436728A (en) * | 2020-11-06 | 2021-03-02 | 中国地质大学（武汉） | High-efficiency control system and method of bidirectional resonant converter |
| CN114123801A (en) * | 2022-01-25 | 2022-03-01 | 常州索维尔电子科技有限公司 | Boost circuit based on LLC circuit, control method, control device and electronic equipment |
| WO2023098218A1 (en) * | 2021-11-30 | 2023-06-08 | 刘三英 | Wide-range resonant soft-switching bidirectional direct-current converter, and control method therefor |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102064592A (en) * | 2011-01-21 | 2011-05-18 | 深圳市皓文电子有限公司 | High-power battery device |
| CN103944396A (en) * | 2014-04-11 | 2014-07-23 | 燕山大学 | LLC resonance type three-port DC-DC converter and control method thereof |
-
2015
- 2015-07-28 CN CN201510451866.9A patent/CN104993707A/en active Pending
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102064592A (en) * | 2011-01-21 | 2011-05-18 | 深圳市皓文电子有限公司 | High-power battery device |
| CN103944396A (en) * | 2014-04-11 | 2014-07-23 | 燕山大学 | LLC resonance type three-port DC-DC converter and control method thereof |
Non-Patent Citations (2)
| Title |
|---|
| ABE SEIYA等: "Seamless operation of bi-directional LLC resonant converter for PV system", 《2014 TWENTY一NINTH ANNUAL IEEE》 * |
| 陈启超等: "双向LLC谐振型直流变压器的软启动及功率换向控制", 《电工技术学报》 * |
Cited By (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN107124103A (en) * | 2016-02-25 | 2017-09-01 | 株式会社村田制作所 | DC/DC conversion equipments |
| CN107124103B (en) * | 2016-02-25 | 2020-04-14 | 株式会社村田制作所 | DC/DC converter |
| CN105871215A (en) * | 2016-05-17 | 2016-08-17 | 华南理工大学 | Rectification control circuit for bidirectional CLLLC resonant converter |
| CN108809104A (en) * | 2018-06-11 | 2018-11-13 | 南京航空航天大学 | A kind of two-way resonance converter and its control method of synchronous rectification |
| CN112311245A (en) * | 2020-11-06 | 2021-02-02 | 中国地质大学（武汉） | High-frequency intermittent control system and method of bidirectional series resonant converter |
| CN112436728A (en) * | 2020-11-06 | 2021-03-02 | 中国地质大学（武汉） | High-efficiency control system and method of bidirectional resonant converter |
| CN112311245B (en) * | 2020-11-06 | 2021-09-07 | 中国地质大学（武汉） | High-frequency intermittent control system and method of bidirectional series resonant converter |
| CN112436728B (en) * | 2020-11-06 | 2021-12-03 | 中国地质大学（武汉） | High-efficiency control method of bidirectional resonant converter |
| WO2023098218A1 (en) * | 2021-11-30 | 2023-06-08 | 刘三英 | Wide-range resonant soft-switching bidirectional direct-current converter, and control method therefor |
| CN114123801A (en) * | 2022-01-25 | 2022-03-01 | 常州索维尔电子科技有限公司 | Boost circuit based on LLC circuit, control method, control device and electronic equipment |
| CN114123801B (en) * | 2022-01-25 | 2022-04-22 | 常州索维尔电子科技有限公司 | Control method and control device of boost circuit based on LLC circuit |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN105720840B (en) | Power conversion unit and its setting method | |
| CN104993707A (en) | Method of controlling bidirectional DC/DC converter based on LLC resonance | |
| CN201541200U (en) | AC-DC intermediate circuit converter with rather wide AC input voltage range | |
| CN106685231B (en) | A kind of primary side clamper type soft switch full bridge converter and its asymmetric control method | |
| CN108462397B (en) | A kind of three road output DC-DC converter of hybrid modulation isolated form | |
| CN102299649B (en) | Supply convertor | |
| CN103312171A (en) | Isolated soft switching two-diode forward resonant DC / DC (direct-current/direct-current) circuit | |
| CN206807298U (en) | A kind of two-way resonance translation circuit and converter | |
| CN106169873A (en) | It is applicable to mixing connection in series-parallel full-bridge circuit and the control method thereof of high pressure or High-current output | |
| CN103595259A (en) | Double-transformer serial-parallel isolated-type soft switching direct-current converter and control method thereof | |
| CN107546959A (en) | A kind of Switching Power Supply, electronic equipment and Switching Power Supply control method | |
| CN107222096A (en) | Isolated CUK push-pull topologies in parallel | |
| CN104638931B (en) | The forward-flyback converter of symmetrical RCD clamps | |
| CN204700414U (en) | A kind of electric welding machine circuit of APFC | |
| CN110445387B (en) | Topological structure and control method of formation and grading power supply | |
| CN115694203A (en) | Direct-current isolated converter capable of bidirectional conversion and control method thereof | |
| CN101521460B (en) | Multi-channel output direct current-direct-current converter | |
| CN108599346B (en) | Three-level electric automobile charging circuit | |
| CN107612346A (en) | A kind of two-way DC/DC power inverters | |
| CN105322796A (en) | Polymorphic three-level booster circuit | |
| CN205646960U (en) | Rectification charging device | |
| CN107612340A (en) | A kind of low voltage stress isolating full-bridge converter circuit arrangement | |
| CN108494229B (en) | AC/DC universal power router topology and control method thereof | |
| CN208046459U (en) | A kind of DC-DC converter of fuel cell | |
| CN110739872A (en) | novel bidirectional high-transformation-ratio SWISS rectifier |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| RJ01 | Rejection of invention patent application after publication |
Application publication date: 20151021 |
|
| RJ01 | Rejection of invention patent application after publication |