CN115864615A - Full-bridge LLC soft switch resonant charger with power factor correction function and control method - Google Patents
Full-bridge LLC soft switch resonant charger with power factor correction function and control method Download PDFInfo
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Abstract
The invention discloses a full-bridge LLC soft switching resonant charger with power factor correction and a control method thereof, and relates to the technical field of charging circuits. The PFC circuit is a main power circuit adopting a Boost active power factor corrector and consists of a rectifying circuit and a Boost converter; the LLC full-bridge circuit comprises an inverter network, a resonant network and a rectifying network. The charger improves harmonic current in input current through the PFC circuit, so that the PF value of the input end of the charger is greatly reduced, direct current bus voltage can be stably output, the LLC full bridge circuit can realize ZVS (zero voltage switching on) of a primary side MOS tube and ZCS (zero current switching off) of a secondary side rectifier diode, MOS switching loss is greatly reduced, reverse recovery loss of the secondary side rectifier diode is eliminated, and therefore the problems of low efficiency, serious heating and the like caused by the traditional flyback topology and forward topology are solved.
Description
Technical Field
The invention relates to the technical field of charging circuits, in particular to a full-bridge LLC soft-switching resonant charger with power factor correction and a control method.
Background
With the continuous development of society and the continuous improvement of living standard of people, the stair climbing machine and the load carrier become one of articles which people can buy, and great convenience is brought to the transportation in the life of people. The two structures bring the biggest problems of low efficiency, serious heating, limited power density and low cost performance, and are difficult to stably and reliably operate in a wide voltage input range for a long time. Most importantly, the rectified current contains harmonic current which is extremely harmful to a power grid, and meanwhile, the power factor of the input end of the equipment can be greatly reduced, so that the proportion of idle work is increased, and the energy-saving concept is not met. Secondly, the rectified DC bus voltage is unstable and can not be adjusted.
Disclosure of Invention
The present invention is directed to solve the problems of the background art, and provides a full-bridge LLC soft-switching resonant charger with power factor correction and a control method thereof.
The purpose of the invention can be realized by the following technical scheme:
the embodiment of the invention provides a full-bridge LLC soft switching resonance charger with power factor correction, which comprises a PFC circuit, an LLC full-bridge circuit and a control module; the control module is respectively connected with the PFC circuit, the LLC full-bridge circuit and the lithium battery to be charged; the input end of the PFC circuit is connected with an external power supply, and the output end of the PFC circuit is connected with the input end of the LLC full-bridge circuit; the output end of the LLC full bridge is connected with the lithium battery;
the control module is used for controlling the PFC circuit and the LLC full-bridge circuit to work and charge the lithium battery;
the PFC circuit is a main power circuit adopting a Boost active power factor corrector and consists of a rectifying circuit and a Boost converter; the rectifying circuit converts the input alternating current with positive and negative values into steamed bun wave type direct current without negative values; the Boost converter adopts a preset duty ratio, converts the voltage of the steamed bun wave type direct current into a bus direct current voltage, and ensures that the input side inductive current presents a sinusoidal current consistent with the envelope curve of the input voltage waveform;
the LLC full-bridge circuit comprises an inverter network, a resonant network and a rectifier network; the inverter network comprises a main power MOS tube Q 1 、Q 2 、Q 3 And Q 4 ，Q 1 And Q 3 In series, Q 2 And Q 4 In series, and Q 1 And Q 3 And Q 2 And Q 4 Are bridged by the resonant network; the resonant network comprises a series resonant inductor L r And an excitation inductor L m And a resonance capacitor C r 。
Optionally, the rectifier circuit is a bridge rectifier circuit; the Boost converter comprises an inductor, an MOS (metal oxide semiconductor) tube, an output diode, a filter capacitor, a load resistor, an input sampling circuit, a comparator circuit, an output voltage sampling circuit, an error amplifier circuit and a multiplier.
The output end of the rectifying circuit is connected with the inductor in series, the other end of the inductor is respectively connected with the D pole of the MOS tube and the anode of the output diode, and the cathode of the output diode is connected with the filter capacitor and the load resistor; one end of the load resistor is the output end Vo of the PFC circuit, and the other end of the load resistor, the cathode of the filter capacitor and the source S of the MOS tube are connected to the output cathode of the rectifying circuit; the grid of the MOS tube is connected with the output end of the hysteresis comparator; the two ends of the input voltage sampling circuit are respectively connected with the rectifying circuit and the multiplier, the non-inverting input end of the hysteresis comparator is connected with the multiplier, and the inverting input end of the hysteresis comparator is connected with the output anode of the rectifying circuit; the output sampling circuit is connected with the inverting input end of the error amplifying circuit, and the non-inverting input end of the error amplifying circuit is a preset reference voltage.
Optionally, the inversion network comprises: main power MOS tube Q 1 、Q 2 、Q 3 And Q 4 ，Q 1 、Q 2 、Q 3 And Q 4 Respectively corresponding body diodes D 1 、D 2 、D 3 And D 4 ，Q 1 、Q 2 、Q 3 And Q 4 Parasitic capacitance C between the corresponding drain and source electrodes 1 、C 2 、C 3 And C 4 (ii) a The rectifier network comprises; main power transformer Tr, output rectifier diode D R1 And D R2 Output filter capacitor C f Load resistance R ld (ii) a The rectification network and the resonant network form an LLC resonant cavity.
The embodiment of the invention also provides a control method of a full-bridge LLC soft switch resonant charger with power factor correction, which comprises the following steps:
obtaining the resonant inductance L r The excitation inductor L m And said resonant capacitor C r ；
According to the resonance inductance L r And said resonant capacitor C r Calculating a first resonant frequency, said resonant inductance L r The excitation inductor L m And said resonant capacitor C r Calculating a second resonant frequency;
determining a target switching frequency according to the first resonant frequency and the second resonant frequency, so that the target switching frequency is greater than the second resonant frequency and not greater than the first resonant frequency;
controlling the first switch group and the second switch group to be alternately conducted in a complementary way at the target switching frequency; the first switch group comprises Q 1 And Q 4 The second switch group comprisesQ 2 And Q 3 。
The invention has the beneficial effects that:
the embodiment of the invention provides a full-bridge LLC soft switching resonance charger with power factor correction, which comprises a PFC circuit, an LLC full-bridge circuit and a control module; the control module is respectively connected with the PFC circuit, the LLC full-bridge circuit and the lithium battery to be charged; the input end of the PFC circuit is connected with an external power supply, and the output end of the PFC circuit is connected with the input end of the LLC full-bridge circuit; the output end of the LLC full bridge is connected with the lithium battery; the control module is used for controlling the PFC circuit and the LLC full-bridge circuit to work to charge the lithium battery; the PFC circuit is a main power circuit adopting a Boost active power factor corrector and consists of a rectifying circuit and a Boost converter; the rectifying circuit converts the input alternating current with positive and negative polarity into the steamed bun wave-type direct current without negative value; the Boost converter adopts a preset duty ratio, converts the voltage of the steamed bun wave type direct current into a bus direct current voltage, and ensures that the input side inductive current presents a sinusoidal current consistent with the envelope curve of the input voltage waveform; the LLC full-bridge circuit comprises an inverter network, a resonant network and a rectifier network; the inverter network comprises a main power MOS transistor Q 1 、Q 2 、Q 3 And Q 4 ，Q 1 And Q 3 In series, Q 2 And Q 4 In series, and Q 1 And Q 3 And Q 2 And Q 4 Are bridged by a resonant network; the resonant network comprises a series resonant inductor L r Excitation inductance L m And a resonance capacitor C r 。
The charger improves harmonic current in input current through the PFC circuit, so that the PF value of the input end of the charger is greatly reduced, direct current bus voltage can be stably output, the LLC full-bridge circuit can realize ZVS (zero voltage switching on) of a primary side MOS tube and ZCS (zero current switching off) of a secondary side rectifier diode, MOS switching loss is greatly reduced, reverse recovery loss of the secondary side rectifier diode is eliminated, and the problems of low efficiency, serious heating and the like caused by the traditional flyback topology and forward topology are solved.
Drawings
The invention will be further described with reference to the accompanying drawings.
Fig. 1 is a schematic diagram of a full-bridge LLC soft-switching resonant charger with power factor correction according to an embodiment of the present invention;
fig. 2 is a schematic circuit diagram of a PFC circuit according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of a rectified waveform according to an embodiment of the present invention;
fig. 4 is a schematic circuit diagram of an LLC full-bridge circuit according to an embodiment of the present invention;
fig. 5 is a flowchart of a control method of a full-bridge LLC soft-switching resonant charger with power factor correction according to an embodiment of the present invention;
fig. 6 is a waveform diagram of three operation modes of the LLC resonant converter provided in the embodiment of the present invention;
fig. 7 is a mode diagram of the full-bridge LLC resonant circuit in the working mode 1 in the embodiment of the present invention.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
The embodiment of the invention provides a full-bridge LLC soft switch resonance charger with power factor correction. Referring to fig. 1, fig. 1 is a schematic diagram of a full-bridge LLC soft-switching resonant charger with power factor correction according to an embodiment of the present invention. The charger comprises a PFC circuit, an LLC full-bridge circuit (LLC full-bridge) and a control module (MCU control module); the control module is respectively connected with the PFC circuit, the LLC full-bridge circuit and the lithium battery to be charged; the input end of the PFC circuit is connected with an external power supply (Uac), and the output end of the PFC circuit is connected with the input end of the LLC full-bridge circuit; the output end of the LLC full bridge is connected with the lithium battery;
the control module is used for controlling the PFC circuit and the LLC full-bridge circuit to work to charge the lithium battery;
the PFC circuit is a main power circuit adopting a Boost active power factor corrector and consists of a rectifying circuit and a Boost converter; the rectifying circuit converts the input alternating current with positive and negative polarity into the steamed bun wave-type direct current without negative value; the Boost converter adopts a preset duty ratio, converts the voltage of the steamed bun wave type direct current into a bus direct current voltage, and ensures that the input side inductive current presents a sinusoidal current consistent with the envelope curve of the input voltage waveform;
the LLC full-bridge circuit comprises an inverter network, a resonant network and a rectifier network; the inverter network comprises a main power MOS transistor Q 1 、Q 2 、Q 3 And Q 4 ，Q 1 And Q 3 In series, Q 2 And Q 4 In series, and Q 1 And Q 3 And Q 2 And Q 4 Are bridged by a resonant network; the resonant network comprises a series resonant inductor L r And an excitation inductor L m And a resonant capacitor C r 。
Based on the full-bridge LLC soft switching resonance charger with the power factor correction provided by the embodiment of the invention, the harmonic current in the input current is improved through the PFC circuit, the PF value at the input end of the charger is greatly reduced, the direct current bus voltage can be stably output, the LLC full-bridge circuit can realize ZVS (zero voltage switching on) of a primary side MOS tube and ZCS (zero current switching off) of a secondary side rectifier diode, the switching loss of the MOS is greatly reduced, and the reverse recovery loss of the secondary side rectifier diode is eliminated, so that the problems of low efficiency, serious heating and the like caused by the traditional flyback topology and forward topology are solved.
In one implementation, the resonant inductor L r Including primary side leakage inductance and excitation inductance L of transformer Tr m Concentrated in transformer Tr, resonant capacitor C r The series connection plays a role of blocking the direct current in the primary side loop.
In an embodiment, referring to fig. 2, fig. 2 is a circuit schematic diagram of a PFC circuit according to an embodiment of the present invention. The rectification circuit is a bridge rectification circuit; the Boost converter comprises an inductor (Lp), an MOS (metal oxide semiconductor) tube (Q), an output diode (D), a filter capacitor (C), a load resistor (R), an input sampling circuit (K), a comparator circuit (a hysteresis comparison circuit), an output voltage sampling circuit (H), an error amplifier circuit (VA) and a multiplier (M).
The output end of the rectifying circuit is connected in series with an inductor, the other end of the inductor is respectively connected with the D pole of the MOS tube and the anode of the output diode, and the cathode of the output diode is connected with the filter capacitor and the load resistor; one end of the load resistor is the output end Vo of the PFC circuit, and the other end of the load resistor, the cathode of the filter capacitor and the source S of the MOS tube are connected to the output cathode of the rectifying circuit; the grid of the MOS tube is connected with the output end of the hysteresis comparator; the two ends of the input voltage sampling circuit are respectively connected with the rectifying circuit and the multiplier, the non-inverting input end of the hysteresis comparator is connected with the multiplier, and the inverting input end of the hysteresis comparator is connected with the output anode of the rectifying circuit; the output sampling circuit is connected with the inverting input end of the error amplifying circuit, and the non-inverting input end of the error amplifying circuit is a preset reference voltage.
The working principle of the PFC circuit in one implementation is as follows: the output voltage Vo is compared with the reference voltage Vf after passing through the voltage sampling voltage H, the voltage output quantity X is obtained after calculation of the error operational amplifier, the voltage output quantity X enters a multiplier M and is multiplied by an input voltage sampling circuit K of the Boost to obtain a reference current Z, and the reference current Z is multiplied by a current I passing through an MOS (metal oxide semiconductor) tube Q s The duty ratio signal d of the MOS tube is obtained after detection and comparison, and the on-off of the MOS tube is controlled after the duty ratio signal d passes through the driving circuit, so that the input current i L Substantially in accordance with the rectified voltage waveform.
It can be known from the above control and schematic diagrams that when the voltage obtained by the output voltage through the output voltage sampling circuit H is smaller than the reference voltage Vf, the output X of the error amplifier VA increases, the reference current Z passing through the multiplier M increases, and the duty ratio of the MOS transistor Q is increased under the action of the hysteresis comparator, so that the output voltage Vo is adjusted upward.
Referring to fig. 3, fig. 3 is a schematic diagram of a rectified waveform according to an embodiment of the present invention. FIG. 3 shows the input voltage waveform V corrected by the PFC circuit dc And V i Corrected inductor current i L The waveform of (2). Input current I i And (4) waveform. As can be seen from the left side of fig. 3Input current I i The pulse waveform is modulated by the PWM frequency to be converted into a waveform that approximates a sine wave (including a high-frequency ripple). FIG. 3 shows that during a switching cycle, when the MOS transistor Q is turned on, i o =0，i L =I s To I s =0，i L =i o The waveform of the current (with high-frequency ripple current component) flowing through the MOS tube is averaged for each switching period to obtain an approximate smooth sine curve.
In an embodiment, referring to fig. 4, fig. 4 is a circuit schematic diagram of an LLC full-bridge circuit provided in the embodiment of the present invention, where the inverting network includes: main power MOS tube Q 1 、Q 2 、Q 3 And Q 4 ，Q 1 、Q 2 、Q 3 And Q 4 Respectively corresponding body diodes D 1 、D 2 、D 3 And D 4 ，Q 1 、Q 2 、Q 3 And Q 4 Parasitic capacitance C between the corresponding drain and source electrodes 1 、C 2 、C 3 And C 4 (ii) a The rectifier network comprises; main power transformer Tr and output rectifier diode D R1 And D R2 An output filter capacitor C f Load resistance R ld (ii) a The rectification network and the resonant network form an LLC resonant cavity.
Based on any control method of the full-bridge LLC soft-switching resonant charger with power factor correction, referring to fig. 5, fig. 5 is a flowchart of a control method of the full-bridge LLC soft-switching resonant charger with power factor correction provided in an embodiment of the present invention. The method comprises the following steps:
s501, obtaining a resonant inductor L r And an excitation inductor L m And a resonance capacitor C r .
S502, according to the resonance inductance L r And a resonance capacitor C r Calculating a first resonant frequency, resonant inductance L r And an excitation inductor L m And a resonance capacitor C r A second resonant frequency is calculated.
And S503, determining a target switching frequency according to the first resonant frequency and the second resonant frequency, so that the target switching frequency is greater than the second resonant frequency and not greater than the first resonant frequency.
S504, controlling the first switch group and the second switch group to be alternately and complementarily conducted at a target switching frequency; the first switch group comprises Q 1 And Q 4 The second switch group comprises Q 2 And Q 3 。
In one implementation, the first resonant frequency is calculated according to equation (1):
calculating a second resonant frequency according to equation (2):
in one implementation, the working principle of the full-bridge LLC resonant circuit is as follows:
the LLC resonant converter is used for adjusting the energy output by changing the switching frequency in a frequency modulation working mode. According to switching frequency f s To the resonance frequency f r ，f m The magnitude relation of (2) can divide the LLC resonant converter into three working modes. Referring to fig. 6, fig. 6 is a waveform diagram illustrating three operation modes of the LLC resonant converter according to the embodiment of the present invention.
In the operation mode 1,fs < fr, the main operation waveforms of the LLC resonant converter are as shown in fig. 6 (a) below. In this mode, the inductor current i is due to resonance Lr Can resonate to the exciting inductance current i Lm Equal when L m Participate in resonance due to i Lr And i Lm The primary side current is 0 due to the equality, so that the secondary side rectifier diode ZCS (zero current shutoff) can be turned off, the secondary side rectifier diode works in an intermittent state, and the secondary side diode does not have the problem of reverse recovery.
The operation mode 2,fs = fr, in which the main operation waveform of the LLC resonant converter is as shown in fig. 6 (b) m Not participating in resonance, the voltage across it is clamped to (Np/Ns) Vo, where Ns = Ns1= Ns2, np represents the number of primary turns,ns1 and Ns2 represent the secondary turns. The rectifier diode works in a critical continuous mode state, ZCS turn-off can be realized, and the secondary side diode does not have the problem of reverse recovery.
In the operating mode 3,fs > fr, the main operating waveform of the LLC resonant converter is as shown in fig. 6 (c), in which the resonant inductor Lm does not participate in resonance and the voltage across it is clamped to (Np/Ns) Vo, where Ns = Ns1= Ns2, np represents the number of primary turns, and Ns1 and Ns2 represent the number of secondary turns. The secondary side rectifier diode works in a continuous mode state, and has the problems of reverse recovery and turn-off loss.
From the above analysis, it can be known that both the working mode 1 (fs < fr) and the working mode 2 (fs = fr) can achieve ZVS turn-off of the primary side MOS transistor and ZCS turn-off of the secondary side output rectifier diode, and the total loss (switching loss of the MOS transistor and reverse recovery loss of the secondary side rectifier diode) in these two states is the minimum, and the efficiency of the charger is the highest. Since the switching frequency fs of each charger cannot be the same and the resonance frequency fr (fm) cannot be the same, it is not practical to realize the condition that fs = fr is always equal in mass production, so that fm < fs < fr is the best choice.
In one implementation, referring to fig. 7, fig. 7 is a mode diagram of a full-bridge LLC resonant circuit in working mode 1 in an embodiment of the present invention.
Modal analysis (fm < fs < fr):
mode 1: as above in FIG. 6 (a) [ to front ]]Before the moment to, the MOS transistor Q 2 ，Q 3 Conduction, i lr And i Lm Equal, zero primary current and therefore zero secondary diode, and a secondary rectifier diode D R2 ZVS off is realized, at which time L m Participating in L r And C r A constituent resonant circuit, L m 、L r And C r And co-resonating. At this stage, the output capacitor C f Power is supplied to the load.
Mode 2[ to t1 ]]At time to, MOS transistor Q 2 And Q 3 Off due to excitation inductance L m The reason for the very large and very short duration of this mode can be approximated as resonanceConstant inductance current i Lr =i Lm Feeding C to 2 And C 3 Charging while supplying C 1 And C 4 And (4) discharging. When MOS tube Q 1 And Q 4 Body diode D of 1 And D 4 When conducting, Q 1 And Q 4 The zero voltage turns on.
Mode 2[ t1 ] to [ t2 ]]At time t1, Q 1 And Q 4 Zero voltage is turned on, and the voltage at the two ends of A and B is V in Rectifier diode D R1 Conducting and exciting inductor L m Clamped to (Np/Ns) Vo, where Ns = Ns1= Ns2, np represents the number of primary turns, and Ns1 and Ns2 represent the number of secondary turns. At this time L m The excitation inductance current is only used as a load and does not participate in resonance, and the excitation inductance current is linearly increased. L is r And C r Resonance with voltage across [ Vin- (Np/Ns) Vo]。
Modality 4[ t2 ] to [ t3 ]]At time t2, the resonant inductor current resonates i Lr Co-integration with the excitation inductor current i Lm When the load end of the transformer is equal to the load end of the transformer, the load end of the transformer is separated from the resonant network, the primary side current is zero, and the secondary side rectifier diode D R1 Zero current turn off (ZCS), there is no reverse recovery problem. At this time, the excitation inductance L m Is no longer output by voltage V o Clamped to Np/Ns) V o ，L r ，C r ，L m And the work is coordinated and integrated together. Due to L m General ratio L r The resonance time is much longer and very short, and the resonance current is approximately considered to be kept unchanged in the period of time, the resonance capacitor is charged by constant current, and the voltage V at two ends cr And (4) increasing linearly.
time t3, Q 1 And Q 4 And switching off, and entering the next half working period, wherein the working principle of the converter is similar to the working condition of the first half working period.
While one embodiment of the present invention has been described in detail, the description is only a preferred embodiment of the present invention and should not be taken as limiting the scope of the invention. All equivalent changes and modifications made within the scope of the present invention shall fall within the scope of the present invention.
Claims (4)
1. A full-bridge LLC soft-on Guan Xiezhen charger with power factor correction is characterized by comprising a PFC circuit, an LLC full-bridge circuit and a control module; the control module is respectively connected with the PFC circuit, the LLC full-bridge circuit and the lithium battery to be charged; the input end of the PFC circuit is connected with an external power supply, and the output end of the PFC circuit is connected with the input end of the LLC full-bridge circuit; the output end of the LLC full bridge is connected with the lithium battery;
the control module is used for controlling the PFC circuit and the LLC full-bridge circuit to work to charge the lithium battery;
the PFC circuit is a main power circuit adopting a Boost active power factor corrector and consists of a rectifying circuit and a Boost converter; the rectifying circuit converts the input alternating current with positive and negative polarity into the steamed bun wave-type direct current without negative value; the Boost converter adopts a preset duty ratio, converts the voltage of the steamed bun wave type direct current into a bus direct current voltage, and ensures that the input side inductive current presents a sinusoidal current consistent with the envelope curve of the input voltage waveform;
the LLC full-bridge circuit comprises an inverter network, a resonant network and a rectifier network; the inverter network comprises a main power MOS tube Q 1 、Q 2 、Q 3 And Q 4 ，Q 1 And Q 3 In series, Q 2 And Q 4 In series, and Q 1 And Q 3 And Q 2 And Q 4 Are bridged by the resonant network; the resonant network comprises a series resonant inductor L r And an excitation inductor L m And a resonance capacitor C r 。
2. The full-bridge LLC soft-on Guan Xiezhen charger with power factor correction according to claim 1, wherein said rectifying circuit is a bridge rectifying circuit; the Boost converter comprises an inductor, an MOS (metal oxide semiconductor) tube, an output diode, a filter capacitor, a load resistor, an input sampling circuit, a comparator circuit, an output voltage sampling circuit, an error amplifier circuit and a multiplier;
the output end of the rectifying circuit is connected with the inductor in series, the other end of the inductor is respectively connected with the D pole of the MOS tube and the anode of the output diode, and the cathode of the output diode is connected with the filter capacitor and the load resistor; one end of the load resistor is the output end Vo of the PFC circuit, and the other end of the load resistor, the cathode of the filter capacitor and the source S of the MOS tube are connected to the output cathode of the rectifying circuit; the grid of the MOS tube is connected with the output end of the hysteresis comparator; the two ends of the input voltage sampling circuit are respectively connected with the rectifying circuit and the multiplier, the non-inverting input end of the hysteresis comparator is connected with the multiplier, and the inverting input end of the hysteresis comparator is connected with the output anode of the rectifying circuit; the output sampling circuit is connected with the inverting input end of the error amplifying circuit, and the non-inverting input end of the error amplifying circuit is a preset reference voltage.
3. The full-bridge LLC soft-on Guan Xiezhen charger with power factor correction according to claim 2, wherein said inverting network comprises: main power MOS tube Q 1 、Q 2 、Q 3 And Q 4 ，Q 1 、Q 2 、Q 3 And Q 4 Respectively corresponding body diodes D 1 、D 2 、D 3 And D 4 ，Q 1 、Q 2 、Q 3 And Q 4 Parasitic capacitance C between the drain and source electrodes 1 、C 2 、C 3 And C 4 (ii) a The rectifier network comprises; main power transformer Tr and output rectifier diode D R1 And D R2 An output filter capacitor C f Load resistance R ld (ii) a The rectification network and the resonant network form an LLC resonant cavity.
4. The method for controlling the full-bridge LLC soft-switching resonant charger with power factor correction according to any of claims 1-3, wherein the method comprises:
obtaining the resonant inductance L r The excitation inductor L m And said resonant capacitor C r ；
According to the resonance inductance L r And said resonant capacitor C r Calculating a first resonant frequency, the harmonicVibration inductance L r The excitation inductor L m And said resonant capacitor C r Calculating a second resonant frequency;
determining a target switching frequency according to the first resonant frequency and the second resonant frequency, so that the target switching frequency is greater than the second resonant frequency and not greater than the first resonant frequency;
controlling the first switch group and the second switch group to be alternately conducted in a complementary way at the target switching frequency; the first switch group comprises Q 1 And Q 4 Said second switch group comprises Q 2 And Q 3 。
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| 李勇等: "基于DSP控制的电动汽车充电机模块" * |
| 袁义生等: "一种高效率软开关充电机的研究" * |
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