CN116418238B - Three-switch half-bridge wide-range LLC resonant converter and use method thereof - Google Patents
Three-switch half-bridge wide-range LLC resonant converter and use method thereof Download PDFInfo
- Publication number
- CN116418238B CN116418238B CN202310675529.2A CN202310675529A CN116418238B CN 116418238 B CN116418238 B CN 116418238B CN 202310675529 A CN202310675529 A CN 202310675529A CN 116418238 B CN116418238 B CN 116418238B
- Authority
- CN
- China
- Prior art keywords
- converter
- bridge
- switch tube
- switch
- tube
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
- 238000000034 method Methods 0.000 title claims abstract description 18
- 239000003990 capacitor Substances 0.000 claims description 17
- 230000005284 excitation Effects 0.000 claims description 5
- 230000000295 complement effect Effects 0.000 claims description 4
- 238000010586 diagram Methods 0.000 description 16
- 230000003071 parasitic effect Effects 0.000 description 9
- 238000004088 simulation Methods 0.000 description 7
- 238000010248 power generation Methods 0.000 description 4
- 230000008859 change Effects 0.000 description 3
- 238000013461 design Methods 0.000 description 3
- 238000002955 isolation Methods 0.000 description 3
- 230000007423 decrease Effects 0.000 description 2
- 230000005484 gravity Effects 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
- 230000004048 modification Effects 0.000 description 2
- 238000010606 normalization Methods 0.000 description 2
- 230000008569 process Effects 0.000 description 2
- OKTJSMMVPCPJKN-UHFFFAOYSA-N Carbon Chemical compound [C] OKTJSMMVPCPJKN-UHFFFAOYSA-N 0.000 description 1
- 230000009286 beneficial effect Effects 0.000 description 1
- 229910052799 carbon Inorganic materials 0.000 description 1
- 238000006243 chemical reaction Methods 0.000 description 1
- 230000003247 decreasing effect Effects 0.000 description 1
- 238000011161 development Methods 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 238000005286 illumination Methods 0.000 description 1
- 230000000670 limiting effect Effects 0.000 description 1
- 238000004519 manufacturing process Methods 0.000 description 1
- 230000036961 partial effect Effects 0.000 description 1
- 230000000737 periodic effect Effects 0.000 description 1
- 238000002360 preparation method Methods 0.000 description 1
- 238000012545 processing Methods 0.000 description 1
- 230000002829 reductive effect Effects 0.000 description 1
- 238000011160 research Methods 0.000 description 1
- 230000002441 reversible effect Effects 0.000 description 1
- 238000003860 storage Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33571—Half-bridge at primary side of an isolation transformer
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/01—Resonant DC/DC converters
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
A three-switch half-bridge wide-range LLC resonant converter and a use method thereof relate to the field of electronic circuits and comprise a resonant cavity and a transformer T which are connected together, wherein the input end of the resonant cavity and the output end of the transformer are respectively connected with a primary side three-switch half-bridge inverter circuit and a secondary side full-bridge rectifier circuit; compared with the traditional half-bridge LLC resonant converter, the invention improves the voltage gain by one time, and reduces the turn-off loss of a switching tube and the circuit circulation damage in application; higher efficiency can be ensured over a wide range of output voltages. Compared with the existing wide-range LLC resonant converter topology, the converter provided by the invention has only one transformer and three switching tubes, and has advantages in hardware cost and power density.
Description
Technical Field
The invention relates to the technical field of electronic circuits, in particular to a three-switch half-bridge wide-range LLC resonant converter and a use method thereof.
Background
The traditional fossil energy power generation has the disadvantages of more carbon emission, serious pollution and the like, the specific gravity of fossil energy in the energy structure of China is gradually reduced in recent years, the specific gravity of renewable energy sources such as wind power, photovoltaics and the like is continuously increased, and a distributed power generation system is continuously developed. In the new energy power generation technology, the new energy output voltage has wide range fluctuation under the influence of factors such as illumination, wind power, room temperature and the like, so that a wide range converter needs to be connected in grid connection. The market share of new energy automobiles is continuously improved, and meanwhile, a wide-range converter is also required in the electric automobile charging pile due to the self charging characteristics of the storage batteries and the production standards of different manufacturers.
The DC-DC converter can be divided into isolation and non-isolation, has the advantages of electric isolation, high safety performance and the like, and is widely applied to new energy power generation. The LLC resonant converter is used as an isolated DC-DC converter, has natural soft switching characteristics, and is in line with the development trend of high efficiency, high power density and low electromagnetic interference of the power electronic converter. However, in a wide range of application scenarios, in order to increase the gain range of the converter, the conventional LLC converter can widen the operating frequency of the converter, which is not beneficial to the design of the magnetic element; or by reducing the excitation inductance of the transformer in the resonant cavityLThe method of m increases the gain range of the converter, which increases the current peak value in the resonant cavity, brings more line loss and turn-off damage of the switching tube, and affects the efficiency of the converter. Research is therefore required from the new topology of the LLC converter in order to improve the performance of conventional LLC resonant converters in a wide range of applications.
Disclosure of Invention
Aiming at the problems, the invention provides the three-switch half-bridge wide-range LLC resonant converter and the use method thereof, which widen the voltage gain range of the converter, improve the performance in a wide-range application scene and realize three different working modes under the condition of having the advantages of high efficiency, high power density and the like of the traditional half-bridge LLC resonant converter.
The invention adopts the following technical scheme:
the three-switch half-bridge wide-range LLC resonant converter comprises a resonant cavity and a transformer T which are connected together, wherein the input end of the resonant cavity and the output end of the transformer are respectively connected with a primary side three-switch half-bridge inverter circuit and a secondary side full-bridge rectifier circuit;
the primary side three-switch half-bridge inverter circuit comprises an input inductorL 1 Input capacitanceC 1 And a series switching tube S 1 Switch tube S 2 Switch tube S 3 The switch tube S 1 Switch tube S 2 Through input inductanceL 1 Connecting an input power supplyV in Switch tube S 1 Drain electrode of (d) and switching tube S 3 The sources of (a) are respectively connected with the input capacitorC 1 Two ends, switch tube S 2 Switch tube S 3 And the resonant cavity is connected between the two.
Preferably, the resonant cavity comprises a resonant inductorL r Resonant capacitorC r The transformer T comprises an excitation inductanceL m The exciting inductanceL m Through resonant inductance at one end of (a)L r Connecting switch tube S 3 The other end passes through the resonance capacitorC r Is connected with a switch tube S 1 Switch tube S 2 Between them.
Preferably, the secondary side full bridge rectifier circuit comprises a diode D 1 Diode D 2 Diode D 3 And diode D 4 Rectifier bridge and output capacitor connected with output end of rectifier bridgeC o Output loadR o 。
The application method of the three-switch half-bridge wide-range LLC resonant converter comprises the following working modes:
1) Operating in low gain mode: the switch tube S 1 Constant conduction and switch tube S 2 And a switch tube S 3 With a duty cycle of 0.5 conducting complementarily, the converter is now equivalent to a conventional half-bridge LLC resonant converter; in the low gain mode, the converter adjusts the converter gain by adjusting the switching frequency;
2) Operating in medium gain mode: the switch tube S 3 On with a duty cycle of 0.5, switch tube S 1 And a switch tube S 2 Conducting in a complementary further 0.5 duty cycle; in addition, a switching tube S 1 At S 3 The on period introduces an extra on duty cycleDSwitch tube S 2 In the switching tube S 3 The conduction period introduces an additional duty cycle of 1-DThe method comprises the steps of carrying out a first treatment on the surface of the In medium gain mode, the switching frequency of the converter is constant by adjusting the duty cycleDThereby adjusting the converter gain.
3) Operating in high gain mode: the switching tube S2 is constantly conducted, the switching tube S1 and the switching tube S3 are complementarily conducted at a duty ratio of 0.5, and the converter is equivalent to a boost converter and a half-bridge LLC cascade converter; in the high gain mode, the converter adjusts the converter gain by adjusting the switching frequency.
Preferably, the voltage of the capacitor C1 satisfies the expression:
in the middle ofV 1 For inputting capacitanceC 1 V;V in v is the input voltage;Dis a switching tube S 1 Is dimensionless.
Preferably, in the high gain mode, the input inductanceL 1 The following expression needs to be satisfied:
Pfor converter power, W;I AV for input average current, a;f s is the switching frequency Hz.
Preferably, in the medium gain mode, the input inductanceL 1 The following expression needs to be satisfied:
Pfor converter power, W;I AV for input average current, a;Dis a switching tube S 1 Is dimensionless.
Advantageous effects
1. Compared with the traditional half-bridge LLC resonant converter, the invention improves the voltage gain by one time, and reduces the turn-off loss of a switching tube and the circuit circulation damage in application; higher efficiency can be ensured over a wide range of output voltages. Compared with the existing wide-range LLC resonant converter topology, the converter provided by the invention has only one transformer and three switching tubes, and has advantages in hardware cost and power density;
2. the invention adopts the mixed control of frequency conversion and duty ratio variation, the duty ratio is fixed in the high gain mode and the low gain mode, the switching frequency is fixed in the medium gain mode, each mode has only one control quantity, and the converter is simple to control and easy to realize.
3. Compared with partial wide-range LLC resonant converter, the converter provided by the invention can realize ZVS conduction in the whole range of the switching tube, and reduces the conduction loss of the switching tube.
Drawings
In order to more clearly illustrate the embodiments of the invention or the technical solutions in the prior art, the drawings that are required in the embodiments or the description of the prior art will be briefly described, it being obvious that the drawings in the following description are only some embodiments of the invention, and that other drawings may be obtained according to these drawings without inventive effort for a person skilled in the art.
FIG. 1 is a topology of an embodiment of the present invention;
FIG. 2 is a diagram of the inverter driving signals according to the present invention;
FIG. 3 is a low gain mode equivalent topology of the present invention;
FIG. 4 is a high gain mode equivalent topology of the present invention;
FIG. 5 is a graph of gain over the full range of the present invention;
fig. 6 is a diagram of a medium gain operating mode of the present invention, wherein:
(a) Is [ t ] 0 -t 1 ]A running modal map of the time period;
(b) Is [ t ] 1 -t 2 ]A running modal map of the time period;
(c) Is [ t ] 2 -t 3 ]A running modal map of the time period;
(d) Is [ t ] 3 -t 4 ]A running modal map of the time period;
(e) Is [ t ] 4 -t 5 ]A running modal map of the time period;
(f) Is [ t ] 5 -t 6 ]A running modal map of the time period;
FIG. 7 is a waveform diagram of steady state simulation at 160V input voltage according to the present invention, wherein:
(a) A driving waveform diagram of the switching tubes S1 and S3;
(b) The voltage waveform diagram of the port of the three-switch half-bridge resonant cavity;
(c) A current waveform diagram of the input inductor L1;
(d) A waveform diagram of the resonant current iLr and the exciting inductance current iLm;
FIG. 8 is a waveform diagram of steady state simulation at an input 300V voltage according to the present invention, wherein:
(a) The driving waveform diagrams of the switching tubes S1 and S2;
(b) The voltage waveform diagram of the port of the three-switch half-bridge resonant cavity;
(c) A current waveform diagram of the input inductor L1;
(d) A waveform diagram of the resonant current iLr and the exciting inductance current iLm;
FIG. 9 is a waveform diagram of steady state simulation at an input 440V voltage according to the present invention, wherein:
(a) The driving waveform diagram of the switching tubes S2 and S3;
(b) The voltage waveform diagram of the port of the three-switch half-bridge resonant cavity;
(c) A current waveform diagram of the input inductor L1;
(d) The waveform of the resonant current iLr and the exciting inductance current iLm.
Detailed Description
Embodiments of the present invention are described in detail below, examples of which are illustrated in the accompanying drawings, wherein like or similar reference numerals refer to like or similar elements or elements having like or similar functions throughout. The embodiments described below by referring to the drawings are illustrative and intended to explain the present invention and should not be construed as limiting the invention.
As shown in figure 1 of the drawings,
the three-switch half-bridge wide-range LLC resonant converter comprises a resonant cavity and a transformer T which are connected together, wherein the input end of the resonant cavity and the output end of the transformer are respectively connected with a primary side three-switch half-bridge inverter circuit and a secondary side full-bridge rectifier circuit of a secondary side;
the primary side three-switch half-bridge inverter circuit comprises an input inductorL 1 Input capacitanceC 1 And a series switching tube S 1 Switch tube S 2 Switch tube S 3 I.e. switching tube S 1 Source electrode of (C) is connected with switch tube S 2 Drain electrode of (d), switch tube S 2 Source electrode of (C) is connected with switch tube S 3 Is a drain electrode of the switching tube S 1 Switch tube S 2 Through input inductanceL 1 Connecting an input power supplyV in Positive electrode of (a) power supplyV in Negative electrode of (2) and input capacitanceC 1 Is connected with the negative pole of the switch tube S 1 Drain electrode of (d) and switching tube S 3 The sources of (a) are respectively connected with the input capacitorC 1 Two ends, switch tube S 2 Switch tube S 3 And the resonant cavity is connected between the two. The design mainly utilizes the principle of volt-second balance and adjusts the extra duty ratioDCan adjust the input voltageV in And input capacitanceC 1 Relationship of voltage.
The resonant cavity comprises a resonant inductorL r Resonant capacitorC r The transformer T comprises an excitation inductanceL m The exciting inductanceL m Through resonant inductance at one end of (a)L r Connecting switch tube S 3 The other end passes through the resonance capacitorC r Is connected with a switch tube S 1 Switch tube S 2 Between them.
The secondary side full-bridge rectifying circuit of the secondary side comprises a diode D 1 Diode D 2 Diode D 3 And diode D 4 Rectifier bridge and output capacitor connected with output end of rectifier bridgeC o Output loadR o 。
As shown in FIG. 2, the driving waveforms of the switching tubes of the present invention are shown when the duty cycle is increasedDWhen equal to 0.3, the switch tube S 3 Square wave with 0.5 duty cycle is used as driving waveform in the switching tube S 3 In the other half of the turn-off period, the switching tube S 1 And a switch tube S 2 The switching tube is turned on, and in addition the switching tube S 1 Additional duty cycleDSwitch tube S 2 Additional duty cycle 0.5-D；
Input capacitor voltageV 1 The expression of (2) is:
in the middle ofV 1 For inputting capacitanceC 1 V;V in v is the input voltage;Dis a switching tube S 1 Is dimensionless;
wherein the resonant frequency of the transducerf r The method comprises the following steps:
in the method, in the process of the invention,L r is resonant inductance, H;C r is the resonance capacitance, F.
Switching frequency of converterf s And carrying out normalization processing, wherein the converter gain expression is as follows:
in the method, in the process of the invention,Dthe converter is provided with an extra duty ratio and is dimensionless;kfor exciting inductanceL m And resonant inductanceL r Is dimensionless;fthe normalized switching frequency is dimensionless;Qis a quality factor of the converter and has no dimension.
As shown in the figure 3 of the drawings,
to achieve a wide range, the switching frequency can be changed and the duty cycle can be additionally adjustedDThe invention has three working modes, extra duty cycleDWhen=0.5, the invention works in low gain mode, when the switchTube S 1 Constant conduction and switch tube S 2 And a switch tube S 3 Complementary turn-on at a duty cycle of 0.5; in this mode, the extra duty cycle of the present inventionDConstant equal to 0.5 by varying the switching frequency of the converterf s To achieve a change in gain, the gain expression is:
additional duty cycleDBetween 0 and 0.5, the invention operates in a medium gain mode, in which the switching tube S 3 Is a square wave with a duty cycle of 0.5, switching tube S 1 The duty cycle of the driving waveform is 0.5+DThe duty ratio of the driving waveform of the switching tube S2 is 1-DIn this mode, the switching frequency of the present inventionf s Operating at resonant frequency, after normalizationfConstant 1, by varying the converter extra duty cycleDTo achieve a change in gain, the gain expression is:
as shown in figure 4 of the drawings,
additional duty cycleDWhen=0, the invention works in the high gain mode, and the switching tube S 2 Constant conduction and switch tube S 1 And a switch tube S 3 Complementary turn-on at a duty cycle of 0.5; in this mode, the extra duty cycle of the converterDConstant equal to 0 by varying the switching frequency of the inventionf s To achieve a change in gain, the gain expression is:
as shown in fig. 5, the gain curves of the present invention in three modes are shown, and in a wide range of applications, the present invention ensures continuous gain and a wide gain range by switching the three gain modes.
For ease of understanding, the periodic modes of operation of the converter are analyzed, wherein the high gain and low gain modes can be considered as special modes of medium gain, and therefore only the 6 modes of operation of the medium gain down-converter are analyzed, as shown in fig. 6.
As shown in FIG. 6 (a), the mode of operation [t 0 -t 1 ]Is att 0 At the moment, switch tube S 2 Begin to conduct but due to resonant inductor current at this timei Lr The number of the groups does not exceed 0,i Lr through a switching tube S 2 Parasitic diode freewheeling of (a), thus switching tube S 2 May be approximately 0, which is att 0 ZVS conduction is achieved at the moment. At this point, flow throughL r The current of (2) starts to increase in a sine rule and flows throughL m The current of the secondary side full bridge rectifier circuit on the secondary side can be considered to be increased linearly, and uncontrolled rectification is performed. The resonant current passing through the switching tube S 2 Freewheeling untilt 1 At the moment, flow throughL r Is equal to the current flowing throughL m Is set in the above-described range).i L1 At the position oft 1 Beyond 0 point before the moment, the current direction starts to reverse, and the mode ends.
As shown in FIG. 6 (b), the mode of operation [t 1 -t 2 ]Is att 1 At the moment, switch tube S 1 Turn-off, due to operation in quasi-resonant state, at this timei Lr Equal toi Lm The high-frequency transformer has no current, the secondary full-bridge rectifying circuit current of the secondary side becomes zero at this point, and the freewheeling diode (diode D) of the secondary full-bridge rectifying circuit of the secondary side 1 Diode D 2 Diode D 3 And diode D 4 ) The ZCS of the secondary side full-bridge rectifying circuit is turned off naturally because the current is zero. In the switching tube S 1 After the shutdown, dead time is entered. At the beginning of this mode, resonant inductanceL r Excitation inductanceL m The current of (2) still maintains the original flow direction, and the switch tubeS 1 The parasitic capacitance of (1) starts to charge and the switch tubeS 3 The parasitic capacitance of (1) starts to discharge until it is openedClosing tubeS 1 The drain-source voltage of (2) is changed from 0 toV 1 Switch tube S 3 From V 1 To 0, preparation is made for ZVS opening for the next phase, and this mode ends. In this mode, care needs to be taken that the dead time is designed reasonably so that the parasitic capacitance can be charged and discharged during the dead time to ensure ZVS can be achieved.
As shown in FIG. 6 (c), the mode of operation [t 2 -t 3 ]Is att 2 At the moment, the parasitic capacitance charge and discharge have been completed, due toi Lr The current flowing through the resonant unit needs to pass through the switching tube S 3 Freewheeling due to the switching tube S 3 The parallel parasitic capacitance is discharged at this moment, the voltage is approximately 0, and the switch tube S is realized 3 Is turned on. The secondary side full-bridge rectifying circuit current of the secondary side carries out uncontrolled rectification output, and in the period, voltage is input toL 1 The charging is performed such that the battery is charged,i L1 and linearly rises.
As shown in FIG. 6 (d), the operation mode [t 3 -t 4 ]Is att 3 At the moment, the resonant cavity still works in the negative half period, and the switching tube S 2 Turn off, enter dead time, during which,i L1 completion of switch tube S 1 Switch tube S 2 Is charged and discharged, and then used for a switching tube S 1 Is circulated through the parasitic diode of (1)t 4 Before the moment, switch tube S 1 Is approximately 0.
As shown in FIG. 6 (e), the mode of operation [t 4 -t 5 ]Is att 4 At the moment, the resonant cavity still works in the negative half period, and the switching tube S 1 ZVS is achieved, during which time the input voltageV in Through inductanceL 1 Feed capacitorC 1 The charging is performed such that the battery is charged,i L1 during which time the linear decrease occurs.
As shown in FIG. 6 (f), the operation mode [t 5 -t 6 ]Is att 5 At the moment, switch tube S 3 Turn off, during which time the resonant inductor currenti Lm Complete the switching tube S 2 Switch tube S 3 Charge and discharge of parasitic capacitance of (2) so that current flows from the switching tube S 2 Through the parasitic diode of (2) so that the switching tube S 2 The drain-source voltage of (2) is approximately 0, providing for ZVS at its next moment; at the same time due to thisi Lr Equal toi Lm The high-frequency transformer has no current, the current of the secondary side full-bridge rectifying circuit also becomes zero at the moment, and the freewheeling diode of the secondary side full-bridge rectifying circuit is naturally turned off due to the zero current, so that the ZCS turn-off of the secondary side full-bridge rectifying circuit is realized.
In this example, specific parameters of the present invention are shown in table 1:
TABLE 1 Main Circuit design parameters
And according to parameters in the table, under the condition of outputting rated 110V, simulating in a simulink software platform.
When the input voltage is 160V, the converter equivalent gain is 2.81. The steady-state simulation waveform of the converter is shown in FIG. 7, when the converter is in high gain mode, as shown in FIG. 7 (a), S 1 S and S 3 The switching tube is complementarily conducted by 50% driving, and the additional duty ratio is thatD0,S of a shape of 0,S 2 At this time, the constant conduction is achieved. As shown in figure 7 (b) of the drawings,V ab the input voltage is twice the voltage of the port voltage of the three-switch half-bridge resonant cavity. As shown in FIG. 7 (c)，i L1 To input inductor current, the current is at S 3 The conduction period linearly rises, at S 1 The conduction period decreases linearly. As shown in figure 7 (d) of the drawings,i Lr for the resonant inductor current to be present,i Lm the exciting inductor current is operated in an under-resonance state.
When the input voltage is 300V, the converter equivalent gain is 1.5. The steady-state simulation waveform of the converter is shown in FIG. 8, when the converter is in medium gain mode, as shown in FIG. 8 (a), S 1 S and S 2 The driving waveform of the switching tube is related to an additional duty cycleD0.15, S 3 Is a 50% square wave. As shown in figure 8 (b) of the drawings,V ab the voltage is the voltage of the three-switch half-bridge port, and the voltage is in accordance with the voltage of the input capacitorV 1 Is an expression of (2). As shown in figure 8 (c) of the drawings,i L1 to input inductor current, the current is at S 2 S and S 3 The switch tubes are all on and linearly rise, S 1 The switching tube is linearly decreased when it is turned on. As shown in figure 8 (d) of the drawings,i Lr for the resonant inductor current to be present,i Lm the exciting inductor current is operated in a quasi-resonance state.
The converter equivalent gain is 1.02 when the input voltage is 440V. The steady-state simulation waveform of the converter is shown in FIG. 9, when the converter is in low gain mode, as shown in FIG. 9 (a), S 2 S and S 3 The switching tube is complementarily conducted by 50% driving, and the additional duty ratio is thatD0.5, S 2 The switching tube is constantly conducting at this time. As shown in figure 9 (b) of the drawings,V ab the voltage is equal to the input voltage in terms of the three-switch half-bridge port voltage. As shown in figure 9 (c) of the drawings,i L1 to input the inductor current, the current is at a constant value. As shown in figure 9 (d) of the drawings,i Lr for the resonant inductor current to be present,i Lm the exciting inductor current is operated in an over-resonance state.
From the steady-state simulation waveforms, it can be seen that the converter can maintain a nominal output voltage over a wide input voltage range, with a 3-fold equivalent gain range.
The present invention is not limited to the above-mentioned embodiments, but is intended to be limited to the following embodiments, and any modifications, equivalents and modifications can be made to the above-mentioned embodiments without departing from the scope of the invention.
Claims (7)
1. The three-switch half-bridge wide-range LLC resonant converter is characterized by comprising a resonant cavity and a transformer T which are connected together, wherein the input end of the resonant cavity and the output end of the transformer are respectively connected with a primary side three-switch half-bridge inverter circuit and a secondary side full-bridge rectifier circuit;
the primary side three-switch half-bridge inverter circuit comprises an input inductorL 1 Input capacitanceC 1 And a series switching tube S 1 Switch tube S 2 Switch tube S 3 The switch tube S 1 Switch tube S 2 Through input inductanceL 1 Connecting an input power supplyV in Switch tube S 1 Drain electrode of (d) and switching tube S 3 The sources of (a) are respectively connected with the input capacitorC 1 Two ends, switch tube S 2 Switch tube S 3 And the resonant cavity is connected between the two.
2. A three-switch half-bridge wide range LLC resonant converter in accordance with claim 1, wherein said resonant cavity includes a resonant inductanceL r Resonant capacitorC r The transformer T comprises an excitation inductanceL m The exciting inductanceL m Through resonant inductance at one end of (a)L r Connecting switch tube S 3 The other end passes through the resonance capacitorC r Is connected with a switch tube S 1 Switch tube S 2 Between them.
3. A three-switch half-bridge wide range LLC resonant converter in accordance with claim 1, wherein said secondary side full-bridge rectifier circuit includes a diode D 1 Diode D 2 Diode D 3 And diode D 4 Rectifier bridge and output capacitor connected with output end of rectifier bridgeC o Output loadR o 。
4. A method of using a three-switch half-bridge wide range LLC resonant converter as claimed in any one of claims 1 to 3, comprising the following modes of operation:
1) Operating in low gain mode: the switch tube S 1 Constant conduction and switch tube S 2 And a switch tube S 3 With a duty cycle of 0.5 conducting complementarily, the converter is now equivalent to a conventional half-bridge LLC resonant converter; in the low gain mode, the converter adjusts the converter gain by adjusting the switching frequency;
2) Operating in medium gain mode: the switch tube S 3 On with a duty cycle of 0.5, switch tube S 1 And a switch tube S 2 Conducting in a complementary further 0.5 duty cycle; in addition, a switching tube S 1 At S 3 The on period introduces an extra on duty cycleDSwitch tube S 2 In the switching tube S 3 The conduction period introduces an additional duty cycle of 1-DThe method comprises the steps of carrying out a first treatment on the surface of the In medium gain mode, the switching frequency of the converter is constant by adjusting the duty cycleDThereby adjusting the converter gain;
3) Operating in high gain mode: the switch tube S 2 Constant conduction and switch tube S 1 And a switch tube S 3 With a duty cycle of 0.5 conducting complementarily, the converter is equivalent to a boost converter and a half-bridge LLC cascaded converter; in the high gain mode, the converter adjusts the converter gain by adjusting the switching frequency.
5. The method of using a three-switch half-bridge wide range LLC resonant converter of claim 4, wherein said capacitorC 1 The voltage of (2) satisfies the expression:
in the middle ofV 1 For inputting capacitanceC 1 V;V in v is the input voltage;Dis opened toClosing tube S 1 Is dimensionless.
6. The method of using a three-switch half-bridge wide range LLC resonant converter of claim 4, wherein in high gain mode, said input inductanceL 1 The following expression needs to be satisfied:
Pfor converter power, W;I AV for input average current, a;f s is the switching frequency Hz.
7. The method of using a three-switch half-bridge wide range LLC resonant converter of claim 4, wherein in a medium gain mode, said input inductanceL 1 The following expression needs to be satisfied:
Pfor converter power, W;I AV for input average current, a;Dis a switching tube S 1 Is dimensionless.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202310675529.2A CN116418238B (en) | 2023-06-08 | 2023-06-08 | Three-switch half-bridge wide-range LLC resonant converter and use method thereof |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202310675529.2A CN116418238B (en) | 2023-06-08 | 2023-06-08 | Three-switch half-bridge wide-range LLC resonant converter and use method thereof |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN116418238A CN116418238A (en) | 2023-07-11 |
| CN116418238B true CN116418238B (en) | 2023-08-15 |
Family
ID=87059681
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202310675529.2A Active CN116418238B (en) | 2023-06-08 | 2023-06-08 | Three-switch half-bridge wide-range LLC resonant converter and use method thereof |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN116418238B (en) |
Citations (12)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101630914A (en) * | 2009-08-26 | 2010-01-20 | 广州金升阳科技有限公司 | Stabilized voltage supply convertor with long service life and low electromagnetic interference |
| CN102594152A (en) * | 2012-02-27 | 2012-07-18 | 浙江大学 | Series-type half-bridge DC-DC (direct current) converter |
| WO2017049179A1 (en) * | 2015-09-18 | 2017-03-23 | Murata Manufacturing Co., Ltd. | Converters with hold-up operation |
| CN108832818A (en) * | 2018-07-19 | 2018-11-16 | 山东大学 | Mode of resonance isolation DC-DC converter and modulator approach with Width funtion gain ranging |
| CN110649812A (en) * | 2019-09-06 | 2020-01-03 | 广州金升阳科技有限公司 | Wide-gain-range LLC resonant converter and control method thereof |
| CN111010043A (en) * | 2019-12-25 | 2020-04-14 | 湖北工业大学 | Full-bridge LLC resonant converter fixed-frequency control method |
| CN111049369A (en) * | 2019-12-25 | 2020-04-21 | 湖北工业大学 | Hybrid control method for resonant converter in distributed power system |
| CN111181411A (en) * | 2020-03-10 | 2020-05-19 | 上海科技大学 | Variable/fixed bus voltage ultra-wide gain range bidirectional dc/dc converter |
| CN111262442A (en) * | 2020-01-22 | 2020-06-09 | 湖北工业大学 | Resonance converter based ON ON/OFF control |
| CN112087143A (en) * | 2020-08-21 | 2020-12-15 | 南京理工大学 | Quasi-parallel resonant converter with multi-end input and single-end output |
| CN213243835U (en) * | 2020-11-02 | 2021-05-18 | 陕西科技大学 | Half-bridge bidirectional isolation type AC-DC converter |
| WO2021237503A1 (en) * | 2020-05-26 | 2021-12-02 | 中国科学院电工研究所 | Three-phase cllc bidirectional direct current transformer and control method therefor |
Family Cites Families (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP4643695B2 (en) * | 2008-09-02 | 2011-03-02 | 日立コンピュータ機器株式会社 | Bidirectional DC-DC converter and control method thereof |
| US20140153294A1 (en) * | 2012-12-05 | 2014-06-05 | Infineon Technologies Austria Ag | AC/DC Power Converter Arrangement |
| US11545892B2 (en) * | 2020-03-20 | 2023-01-03 | Delta-Q Technologies Corp. | Apparatus and method for single-phase and three-phase power factor correction |
-
2023
- 2023-06-08 CN CN202310675529.2A patent/CN116418238B/en active Active
Patent Citations (12)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101630914A (en) * | 2009-08-26 | 2010-01-20 | 广州金升阳科技有限公司 | Stabilized voltage supply convertor with long service life and low electromagnetic interference |
| CN102594152A (en) * | 2012-02-27 | 2012-07-18 | 浙江大学 | Series-type half-bridge DC-DC (direct current) converter |
| WO2017049179A1 (en) * | 2015-09-18 | 2017-03-23 | Murata Manufacturing Co., Ltd. | Converters with hold-up operation |
| CN108832818A (en) * | 2018-07-19 | 2018-11-16 | 山东大学 | Mode of resonance isolation DC-DC converter and modulator approach with Width funtion gain ranging |
| CN110649812A (en) * | 2019-09-06 | 2020-01-03 | 广州金升阳科技有限公司 | Wide-gain-range LLC resonant converter and control method thereof |
| CN111010043A (en) * | 2019-12-25 | 2020-04-14 | 湖北工业大学 | Full-bridge LLC resonant converter fixed-frequency control method |
| CN111049369A (en) * | 2019-12-25 | 2020-04-21 | 湖北工业大学 | Hybrid control method for resonant converter in distributed power system |
| CN111262442A (en) * | 2020-01-22 | 2020-06-09 | 湖北工业大学 | Resonance converter based ON ON/OFF control |
| CN111181411A (en) * | 2020-03-10 | 2020-05-19 | 上海科技大学 | Variable/fixed bus voltage ultra-wide gain range bidirectional dc/dc converter |
| WO2021237503A1 (en) * | 2020-05-26 | 2021-12-02 | 中国科学院电工研究所 | Three-phase cllc bidirectional direct current transformer and control method therefor |
| CN112087143A (en) * | 2020-08-21 | 2020-12-15 | 南京理工大学 | Quasi-parallel resonant converter with multi-end input and single-end output |
| CN213243835U (en) * | 2020-11-02 | 2021-05-18 | 陕西科技大学 | Half-bridge bidirectional isolation type AC-DC converter |
Also Published As
| Publication number | Publication date |
|---|---|
| CN116418238A (en) | 2023-07-11 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US11496054B2 (en) | High-gain quasi-resonant DC-DC converter based on voltage doubling rectifier circuit | |
| CN109889047B (en) | Two-stage DC-DC converter suitable for wide input and output voltage range | |
| CN110707931A (en) | LLC resonant converter and control method | |
| CN111245247B (en) | Isolated bidirectional resonant soft-switching DC-DC converter | |
| Zhao et al. | A novel multiresonant DC–DC converter with wide output-voltage range | |
| CN112332674A (en) | LLC resonant converter and wide gain control method | |
| CN111431415B (en) | High-boost isolated DC converter with parallel input and series output | |
| CN109698627B (en) | Full-bridge DC/DC converter based on switched capacitor and modulation strategy thereof | |
| CN111342664A (en) | Integrated DC-DC converter and control method thereof | |
| CN114640255A (en) | Series resonant converter and control method thereof | |
| CN111884521B (en) | Single-stage Boost full-bridge Boost zero-current switch direct-current converter and control method thereof | |
| CN111181411B (en) | Variable/fixed bus voltage ultra-wide gain range bidirectional dc/dc converter | |
| Tseng et al. | Interleaved coupled-inductor boost converter with boost type snubber for PV system | |
| Zhan et al. | A high step-up bidirectional isolated dual-active-bridge converter with three-level voltage-doubler rectifier for energy storage applications | |
| CN115811241A (en) | Single-stage bridgeless staggered parallel Boost-LLC AC-DC converter hybrid control method | |
| CN116418238B (en) | Three-switch half-bridge wide-range LLC resonant converter and use method thereof | |
| CN114079384A (en) | Variable-structure LLC converter with wide output voltage range and method | |
| CN112366946B (en) | Resonant DC-DC converter | |
| Li et al. | Multimode hybrid control strategy of LLC resonant converter in applications with wide input voltage range | |
| Jiang et al. | New control strategy for bidirectional LLC resonant converter in energy storage systems | |
| CN108054923B (en) | Topology combined type multi-resonant-element resonant soft-switching direct-current converter | |
| CN117294149B (en) | Pulse modulation system of improved unidirectional direct-current series resonant converter | |
| Wen et al. | The Hybrid Control Strategy for The Wide Input of The LLC Converter | |
| CN116613986B (en) | quasi-Z source LLC resonant converter and control method thereof | |
| Qin et al. | High Efficiency Resonant Converter with Smooth Frequency Regulation for Wide Input Voltage Applications |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |